RT9248
Preliminary
Multi-Phase PWM Controller for CPU Core Power Supply
General Description
Features
The RT9248 is a multi-phase buck DC/DC controller
integrated with all control functions for GHz CPU VRM.
The RT9248 controls 2 or 3 buck switching stages operating
in interleaved phase set automatically. The multi-phase
architecture provides high output current while maintaining
low power dissipation on power devices and low stress on
input and output capacitors. The high equivalent operating
frequency also reduces the component dimension and the
output voltage ripple in load transient.
z
Multi-Phase Power Conversion with Automatic
Phase Selection
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VRM9 & VRD10 DAC Output with Active Droop
Compensation for Fast Load Transient
Smooth VCORE Transition at VID Jump
Multi-Level VID125 Input for VRM9 & VRD10
Selection
Power Stage Thermal Balance by RDS(ON) Current
Sense
Hiccup Mode Over-Current Protection
Programmable Switching Frequency (50kHz to
400kHz per Phase), Under-Voltage Lockout and
Soft-Start
High Ripple Frequency Times Channel Number
RoHS Compliant and 100% Lead (Pb)-Free
RT9248 controls both voltage and current loops to achieve
good regulation, response & power stage thermal balance.
Precise current loop using RDS(ON) as sense component
builds precise load line for strict VRM DC & transient
specification and also ensures thermal balance of different
power stages. The settings of current sense, droop tuning,
VCORE initial offset and over current protection are
independent to compensation circuit of voltage loop. The
feature greatly facilitates the flexibility of CPU power supply
design and tuning.
The DAC output of RT9248 supports VRM9 & VRD10 by
VID125 multi-level input, precise initial value & smooth
VCORE transient at VID jump. The IC monitors the VCORE
voltage for PGOOD and over-voltage protection. Soft-start,
over-current protection and programmable under-voltage
lockout are also provided to assure the safety of microprocessor and power system.
Ordering Information
RT9248
Package Type
C : TSSOP-28
Operating Temperature Range
P : Pb Free with Commercial Standard
G : Green (Halogen Free with Commercial Standard)
Note :
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z
z
z
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Applications
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z
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Intel® Processors Voltage Regulator: VRM9 and VRD10
Low Output Voltage, High Current DC-DC Converters
Voltage Regulator Modules
Pin Configurations
(TOP VIEW)
VID4
VID3
VID2
VID1
VID0
VID125
SGND
FB
COMP
PGOOD
DVD
SS
RT
VOSS
2
3
4
5
6
7
8
9
10
11
12
13
14
28
27
26
25
24
23
22
21
20
19
18
17
16
15
VCC
PWM1
PWM2
PWM3
ISN1
ISP1
ISP2
ISP3
ISN23
GND
ADJ
VDIF
VSEN
IMAX
TSSOP-28
RichTek Pb-free and Green products are :
`RoHS compliant and compatible with the current requirements of IPC/JEDEC J-STD-020.
`Suitable for use in SnPb or Pb-free soldering processes.
`100% matte tin (Sn) plating.
DS9248-05 March 2007
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1
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2
R2
2.4k
R4
1k
R3
9k
+12V
33pF
C2
PG_VCORE
R5
12k
R6
100k
C3
0.1uF
22nF
C1
R1
15k
VID125
VID0
VID1
VID2
VID3
VID4
14
13
12
11
10
9
8
7
6
5
4
3
2
1
VOSS
RT
SS
DVD
PGOOD
COMP
FB
SGND
VID125
VID0
VID1
VID2
VID3
VID4
VCC
IMAX
VSEN
VDIF
ADJ
GND
ISN23
ISP3
ISP2
ISP1
ISN1
PWM3
PWM2
PWM1
RT9248
R12
12k
15
16
17
18
19
1.5k
3k
21 R10
20 R11
3k
3k
3k
22 R9
23 R8
24 R7
25
26
27
28
C4
1uF
+5V
C15
1uF
R17
10 D3
1N4148
+12V
C10
1uF
R15
10 D2
1N4148
+12V
C5
1uF
R13
10
D1
1N4148
+12V
2
4
1
2
4
1
2
4
1
C11
1uF
6
PGND
DRVL
5
VCC
+12V
IN
VCC
6
PGND
DRVL
SW
5
IPD06N03LA
Q6
IPD09N03LA
IPD06N03LA
Q4
7
5
IPD09N03LA
RT9603
8
BST
DRVH
C16
1uF
6
PGND
DRVL
7
Q3
+12V
IPD06N03LA
Q2
Q5
IN
SW
RT9603
8
BST
DRVH
IN
SW
7
VCC
IPD09N03LA
RT9603
8
BST
DRVH
+12V
Q1
C6
1uF
C7
4.7uF
C17
4.7uF
C12
4.7uF
C19
0.01uF
R18
4.7
L3
1uH
C18
2200uF
C14
0.01uF
R16
4.7
L2
1uH
C13
2200uF
C9
0.01uF
R14
4.7
L1
1uH
C8
2200uF
C25 to C28
2200uF x 4
C20 to C24
2200uF x 5
VCORE
RT9248
Preliminary
Typical Application Circuit
DS9248-05 March 2007
Preliminary
RT9248
Functional Pin Description
VOSS (Pin 14)
VID4 (Pin 1), VID3 (Pin 2), VID2 (Pin 3), VID1 (Pin 4),
VID0 (Pin 5) & VID125 (Pin 6)
VCORE initial value offset. Connect this pin to GND with a
resistor to set the offset value.
DAC voltage identification inputs. Tie VID125 to GND for
VRM9 or to VCC for VRD10. These pins are internally
pulled to 3.3V if left open.
IMAX (Pin 15)
SGND (Pin 7)
VSEN (Pin 16)
VCORE differential sense negative input.
VCORE differential sense positive input.
FB (Pin 8)
VDIF (Pin 17)
Inverting input of the internal error amplifier.
VCORE differential sense output.
COMP (Pin 9)
ADJ (Pin 18)
Output of the error amplifier and input of the PWM
comparator.
Current sense output for active droop adjust. Connect a
resistor from this pin to GND to set the load droop.
PGOOD (Pin 10)
GND (Pin 19)
Power good open-drain output.
IC ground.
DVD (Pin 11)
ISN23 (Pin 20)
Programmable power UVLO detection or converter enable
input.
RDS(ON) current sense inputs from converter 2nd & 3rd phase
channel sense components' GND node.
SS (Pin 12)
ISP1 (Pin 23), ISP2 (Pin 22), ISP3 (Pin 21)
Connect this SS pin to GND with a capacitor to set the
soft-start time interval.
RDS(ON) current sense inputs for individual converter
channels. Tie this pin to the component's sense node.
RT (Pin 13)
ISN1 (Pin 24)
Switching frequency setting. Connect this pin to GND with
a resistor to set the frequency.
RDS(ON) current sense inputs from converter 1st channel
sense component's GND node.
Frequency vs. RRT
450
Over-Current protection set.
PWM1 (Pin 27), PWM2 (Pin 26), PWM3 (Pin 25)
PWM outputs for each driven channel. Connect these pins
to the PWM input of the MOSFET driver. For systems
which use 2 channels, connect PWM3 high.
400
350
f OSC(kHz)
300
250
VCC (Pin 28)
200
IC power supply. Connect this pin to a 5V supply.
150
100
50
0
0
10
20
30
40
50
60
70
RRT (k Ω)
DS9248-05 March 2007
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3
VSEN
SGND
VOSS
Buffer
Amplifier
+
-
Offset Currrent
Source/Sink
VDIF
FB
PG Trip
Point
+
COMP
Error
Amplifier
-
DAC + Droop
OVP Trip
Point
+
SS
SS
Control
-
DAC
GAP
Amplifier
ADJ
INH
GND
Power On Reset
-
+
OCP
Setting
-
+
-
+
-
+
+
-
VID0
VID1
VID2
VID3
VID4
VID125
Oscillator
&
Sawtooth
SUM/M
Current
Correction
+ +
+ +
+ +
INH
PWMCP
INH
PWMCP
INH
PWMCP
-
+
RT
PWM Logic
& Driver
PWM Logic
& Driver
PWM Logic
& Driver
ISP1
ISN23
ISP3
ISP2
ISN1
PWM3
PWM2
PWM1
-
+
-
PGOOD VCC DVD
+
-
+
+
+
-
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4
IMAX
RT9248
Preliminary
Function Block Diagram
DS9248-05 March 2007
RT9248
Preliminary
Table 1. Output Voltage Program
Pin Name
Nominal Output Voltage DACOUT
VID4
VID3
VID2
VID1
VID0
VID125 = H
VID125 = L
1
1
1
1
1
No CPU
No CPU
0
1
0
0
1
0.850V
1.625V
0
1
0
0
0
0.875V
1.650V
0
0
1
1
1
0.900V
1.675V
0
0
1
1
0
0.925V
1.700V
0
0
1
0
1
0.950V
1.725V
0
0
1
0
0
0.975V
1.750V
0
0
0
1
1
1.000V
1.775V
0
0
0
1
0
1.025V
1.800V
0
0
0
0
1
1.050V
1.825V
0
0
0
0
0
1.075V
1.850V
1
1
1
1
0
1.100V
1.100V
1
1
1
0
1
1.125V
1.125V
1
1
1
0
0
1.150V
1.150V
1
1
0
1
1
1.175V
1.175V
1
1
0
1
0
1.200V
1.200V
1
1
0
0
1
1.225V
1.225V
1
1
0
0
0
1.250V
1.250V
1
0
1
1
1
1.275V
1.275V
1
0
1
1
0
1.300V
1.300V
1
0
1
0
1
1.325V
1.325V
1
0
1
0
0
1.350V
1.350V
1
0
0
1
1
1.375V
1.375V
1
0
0
1
0
1.400V
1.400V
1
0
0
0
1
1.425V
1.425V
1
0
0
0
0
1.450V
1.450V
0
1
1
1
1
1.475V
1.475V
0
1
1
1
0
1.500V
1.500V
0
1
1
0
1
1.525V
1.525V
0
1
1
0
0
1.550V
1.550V
0
1
0
1
1
1.575V
1.575V
0
1
0
1
0
1.600V
1.600V
Note: (1) 0: Connected to GND
(2) 1: Open
(3) For VID125, H: VCC, L: GND
DS9248-05 March 2007
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5
RT9248
Preliminary
Absolute Maximum Ratings
z
z
z
z
z
z
z
(Note 1)
Supply Voltage, VCC ------------------------------------------------------------------------------------------Input, Output or I/O Voltage ---------------------------------------------------------------------------------Package Thermal Resistance
TSSOP-28, θJA -------------------------------------------------------------------------------------------------Junction Temperature -----------------------------------------------------------------------------------------Lead Temperature (Soldering, 10 sec.) -------------------------------------------------------------------Storage Temperature Range --------------------------------------------------------------------------------ESD Susceptibility (Note 2)
HBM (Human Body Mode) ----------------------------------------------------------------------------------MM (Machine Mode) -------------------------------------------------------------------------------------------
Recommended Operating Conditions
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7V
GND-0.3V to VCC+0.3V
45°C/W
150°C
260°C
−65°C to 150°C
2kV
200V
(Note 3)
Supply Voltage, VCC ------------------------------------------------------------------------------------------- 5V ± 10%
Ambient Temperature Range --------------------------------------------------------------------------------- 0°C to 70°C
Junction Temperature Range --------------------------------------------------------------------------------- 0°C to 125°C
Electrical Characteristics
(VCC = 5V, TA = 25°C, unless otherwise specified)
Parameter
Symbol
Test Conditions
Min
Typ
Max
Units
--
12
--
mA
4.0
4.2
4.5
V
0.2
0.5
--
V
0.95
1.0
1.05
V
--
70
--
mV
170
200
230
kHz
50
--
400
kHz
--
1.9
--
V
--
1.0
--
V
62
66
75
%
0.55
0.60
0.65
V
VRD10, VDAC ≥ 1V
−1
--
+1
%
VRD10, VDAC < 1V
−10
--
+10
mV
VRM9
−1
--
+1
%
VCC Supply Current
Nominal Supply Current
ICC
PWM 1,2,3 Open
POR Threshold
VCCRTH
VCC Rising
Hysteresis
VCCHYS
Power-On Reset
VDVD Threshold
Trip (Low to High)
VDVDTP
Hysteresis
VDVDHYS
Enable
Oscillator
Free Running Frequency
fOSC
Frequency Adjustable Range
fOSC_ADJ
Ramp Amplitude
ΔVOSC
Ramp Valley
VRV
RRT = 12kΩ
RRT = 12kΩ
Maximum On-Time of Each Channel
RT Pin Voltage
VRT
RRT = 12kΩ
Reference and DAC
DACOUT Voltage Accuracy
DACOUT Voltage Accuracy
ΔVDAC_10
ΔVDAC_9
To be continued
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6
DS9248-05 March 2007
RT9248
Preliminary
Parameter
Symbol
Test Conditions
Min
Typ
Max
Units
DAC (VID0-VID4) Input Low
VILDAC_10
VRD10
--
--
0.4
V
DAC (VID0-VID4) Input High
VIHDAC_10
VRD10
0.8
--
--
V
DAC (VID0-VID4 ) Input Low
VILDAC_9
VRM9
--
--
0.8
V
DAC (VID0-VID4) Input High
VIHDAC_9
VRM9
2.2
--
--
V
VID125 Input for VRM9
VVID125_9
--
--
0.4
V
VID125 Input for VRD10
VVID125_10
0.8
--
--
V
DAC (VID0-VID125) Bias Current
IBIAS_DAC
60
120
180
μA
VOSS Pin Voltage
VVOSS
0.95
1.0
1.05
V
--
85
--
dB
--
10
--
MHz
--
3
--
V/μs
RVOSS = 100kΩ
Error Amplifier
DC Gain
Gain-Bandwidth Product
GBW
Slew Rate
SR
COMP = 10pF
Differential Sense Amplifier
Input Impedance
ZIMP
--
16
--
kΩ
Gain-Bandwidth Product
GBW
--
10
--
MHz
Slew Rate
SR
--
3
--
V/μs
ISP 1,2,3 Full Scale Source Current
IISPFSS
60
--
--
μA
ISP 1,2,3 Current for OCP
IISPOCP
90
--
--
μA
0.55
0.60
0.65
V
--
13
--
μA
--
140
--
%
Current Sense GM Amplifier
Protection
IMAX Voltage
VIMAX
RIMAX = 10k
SS Current
ISS
VSS = 1V
Over-Voltage Trip (VSEN/DACOUT)
ΔOVT
Power Good
Lower Threshold (VSEN/DACOUT)
VPG−
VSEN Rising
--
92
--
%
Output Low Voltage
VPGL
IPG = 4mA
--
--
0.2
V
Note 1. Stresses listed as the above “Absolute Maximum Ratings” may cause permanent damage to the device. These are
for stress ratings. Functional operation of the device at these or any other conditions beyond those indicated in the
operational sections of the specifications is not implied. Exposure to absolute maximum rating conditions for extended
periods may remain possibility to affect device reliability.
Note 2. Devices are ESD sensitive. Handling precaution recommended
Note 3. The device is not guaranteed to function outside its operating conditions.
DS9248-05 March 2007
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7
RT9248
Preliminary
Application Information
RT9248 is a multi-phase DC/DC controller that precisely
regulates CPU core voltage and balances the current of
different power channels. The converter consisting of
RT9248 and its companion MOSFET driver provides high
quality CPU power and all protection functions to meet
the requirement of modern VRM.
Voltage Control
Fault Detection
The chip detects VCORE for over voltage and power good
detection. The “hiccup mode” operation of over-current
protection is adopted to reduce the short circuit current.
The inrush current at the start up is suppressed by the
soft start circuit through clamping the pulse width and output
voltage.
RT9248 senses the CPU VCORE by an precise instrumental
Phase Setting and Converter Start Up
amplifier to minimize the voltage drop on PCB trace at
heavy load. VSEN & SGND are the differential inputs. VDIF
is the output node of the differential voltage & the input for
PGOOD & OVP sense. The internal high accuracy VID
DAC allows selection of either VRM9 or VRD10 compliance
via VID125 pin setting. Control loop consists of error
amplifier, multi-phase pulse width modulator, driver and
power components. Like conventional voltage mode PWM
controller, the output voltage is locked at the VREF of error
amplifier and the error signal is used as the control signal
VC of pulse width modulator. The PWM signals of different
channels are generated by comparison of EA output and
split-phase sawtooth wave. Power stage transforms VIN to
output by PWM signal on-time ratio.
RT9248 interfaces with companion MOSFET drivers (like
RT9600, RT9602 or RT9603 series) for correct converter
initialization. The tri-state PWM output (high, low and high
impedance) pins sense the interface voltage at IC POR
period (both VCC and DVD trip). The channel is enabled if
the pin voltage is 1.2V less than VCC. Please tie the PWM
output to VCC and the current sense pins to GND or left
floating if the channel is unused. For 2-Channel application,
connect PWM3 high.
Current Balance
RT9248 senses the current of low side MOSFET in each
synchronous rectifier when it is conducting for channel
current balance and droop tuning. The differential sensing
GM amplifier converts the voltage on the sense component
(can be a sense resistor or the RDS(ON) of the low side
MOSFET) to current signal into internal balance circuit.
The current balance circuit sums and averages the current
signals then produces the balancing signals injected to
pulse width modulator. If the current of some power channel
is greater than average, the balancing signal reduces the
output pulse width to keep the balance.
Load Droop
The sensed power channel current signals regulate the
reference of DAC to form a output voltage droop proportional
to the load current. The droop or so-called “active voltage
positioning” can reduce the output voltage ripple at load
transient and the LC filter size.
Current Sensing Setting
RT9248 senses the current of low side MOSFET in each
synchronous rectifier when it is conducting for channel
current balance and droop tuning. The differential sensing
GM amplifier converts the voltage on the sense component
(can be a sense resistor or the RDS(ON) of the low side
MOSFET) to current signal into internal circuit (see
Figure 1). Be careful to choose GND sense input ISN23 of
GM amplifier of channel 2 & 3 (tied together by internal
wiring) for effective channel current balance.
IX1
<
<
<
Current
Balance
IX
Droop Tune 2IX
IX
IBP
Sample
&
Hold
GM
+
ISP1
RS
IL
RS
IL
R SN1
IBN
Over-Current
Detection
R SP1
ISN1
IX2
<
Current
Balance
IX
Droop Tune 2IX
<
IX
<
Over-Current
Detection
<
<
<
Current
Balance
GM
+
ISP2
R SP2
IBN
ISN23
IBN
IX
Droop Tune 2IX
IX
Over-Current
Detection
IBP
Sample
&
Hold
+
GM
-
Sample
&
Hold
R SN23
Channel 2 & 3
GND return
ISP3
IBP
R SP3
RS
IL
IX3
Figure 1. Current Sense Circuit
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DS9248-05 March 2007
RT9248
Preliminary
I L × RS
by local feedback.
RSP
RSP = RSN for channel 1 & RSP = 2RSN for channel 2 & 3 (at
3 phase operation) to cancel the voltage drop caused by
GM amplifier input bias current. IX is sampled and held just
before low side MOSFET turns off (See Figure 2).
Therefore,
I L (S/H) × R S
V O T OFF
×
I X (S/H) =
, I L (S/H) = I L (AVG) −
,
R SP
L
2
⎡ V IN − V O ⎤
T OFF = ⎢
⎥ × 5uS for fosc = 200kHz
V IN
⎣
⎦
The sensing circuit gets IX =
I X (S/H)
⎡
⎤
⎡ V IN − V O ⎤
× 5uS ⎥
VO − ⎢
⎢
⎥
RS
V IN
⎣
⎦
⎥×
= ⎢I L(AVG) −
R
SP
2L
⎢
⎥
⎢
⎥
⎣
⎦
Falling Slope = Vo/L
IL
IL(AVG)
IL(S/H)
Inductor Current
Protection and SS Function
For OVP, the RT9248 detects the VCORE by VDIF pin voltage
of the differential amplifier output. Eliminate the delay due
to compensation network (compared to sensing FB voltage)
for fast and accurate detection. The trip point of OVP is
140% of normal output level. The PWM outputs are pulled
low to turn on the low side MOSFET and turn off the high
side MOSFET of the synchronous rectifier at OVP. The
OVP latch can only be reset by VCC or DVD restart power
on reset sequence. The PGOOD detection trip point of
VCORE is 92% lower than the normal level. The PGOOD
open drain output pulls low when VCORE is lower than the
trip point. For VID jumping issue, only power fail conditions
(VCC & DVD are lower than trip point or OVP) reset the
output low.
Soft-start circuit generates a ramp voltage by charging
external capacitor with 13μA current after IC POR acts.
The PWM pulse width and VCORE are clamped by the rising
ramp to reduce the inrush current and protect the power
devices.
PWM Signal & High Side MOSFET Gate Signal
Over-current protection trip point is set by the resistor RIMAX
connected to IMAX pin. OCP is triggered if one channel
⎛ 0 .6 V ⎞
⎟ × 1 .4 . Controller forces
⎝ R IMAX ⎠
S/H current signal IX > ⎜
Low Side MOSFET Gate Signal
Figure 2. Inductor Current and PWM Signal
DAC Offset Voltage & Droop Tuning
The DAC offset voltage is set by compensation network
⎛ 1V ⎞ R f 1
& VOSS pin external resistors by ⎜ R VOSS ⎟ × 4
.
⎝
⎠
The S/H current signals from power channels are injected
to ADJ pin to create droop voltage. VADJ = RADJ× 2 IX
∑
The DAC output voltage decreases by VADJ to form the
VCORE load droop (see Figure 3).
+
Current
Source
Count ==22 COUNT
Count ==33
COUNT
Count ==11 COUNT
VCORE
0V
Overload
Applied
2IX1
2IX2
2IX3
>
1 IVOSS
4
ILOAD
0A
RVOSS
-
VOSS
+
1V
RVOSS
∑
S.S
>
IVOSS =
+
EA
-
VADJ
-
COMP
VDAC
PWM output latched at high impedance to turn off both
high and low side MOSFETs in the power stage and initial
the hiccup mode protection. The SS pin voltage is pulled
low with a 13μA current after it is less than 90% VCC. The
converter restarts after SS pin voltage < 0.2V. Three times
of OCP disable the converter and only release the latch by
POR acts (see Figure 4).
FB
RF1
ADJ
RADJ
T0,T1
T3,T4
T2
TIME
>
Figure 4.
VCORE
Figure 3. DAC Offset Voltage & Droop Tune Circuit
DS9248-05 March 2007
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9
RT9248
Preliminary
3-Phase Converter and Components Function Grouping
12V
VCC
BST
DRVH
SW
RT9603
IN
DRVL
PGND
SGND
VSEN
VDIF
PWM1
12V
VID
ISP1
ISN1
PGOOD
VCC
RT9248
Compensation
& Offset
BST
DRVH
VCORE
SW
COMP
FB
RT9603
PWM2
IN
DRVL
PGND
ADJ
Droop Setting
ISP2
ISN23
12V
Driver Power
UVLO
DVD
12V
VOSS
ISP3
SS
DAC Offset
Voltage Setting
VCC
PWM3
IMAX
SW
GND
OCP Setting
BST
DRVH
RT9603
IN
DRVL
PGND
Current Sense
Components
Design Procedure Suggestion
Voltage Loop Setting
a. Output filter pole and zero (Inductor, output capacitor
value & ESR).
b. Error amplifier compensation & sawtooth wave amplitude (compensation network).
c. Kelvin sense for VCORE.
VRM Load Line Setting
a. Droop amplitude (ADJ pin resistor).
b. No load offset (additional resistor in compensation
network).
c. DAC offset voltage setting (VOSS pin & compensation network resistor).
Current Loop Setting
a. GM amplifier S/H current (current sense component
RDS(ON), ISPx & ISNx pin external resistor value,
keep ISPx current < 60μA at full load condition for
better load line linearity).
b. Over-current protection trip point (IMAX pin resistor,
keep ISPx current < 90μA at OCP condition for
precision issue).
Power Sequence & SS
DVD pin external resistor and SS pin capacitor.
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10
PCB Layout
a. Kelvin sense for current sense GM amplifier input.
b. Refer to layout guide for other item.
DS9248-05 March 2007
RT9248
Preliminary
Design Example
Asymptotic Bode Plot of PWM Loop Gain
100
Given:
80
Apply for three phase converter
60
VCORE = 1.5V
40
Gain (dB)
VIN = 12V
ILOAD (max) = 60A
VDROOP = 120mV at full load
OCP trip point set at 30A for each channel (S/H)
RDS(ON) = 6mΩ of low side MOSFET at 27°C
Uncompensated EA Gain
20
0
Compensated EA Gain
-20
PWM Loop Gain
-40
L = 2μH
Modulator Gain
-60
10
10
COUT = 9,000μF with 2mΩ ESR.
100
100
1K
1000
10K
10000
100K
100000
1M
10M
1000000
10000000
Frequency (Hz)
1. Compensation Setting
a. Modulator Gain, Pole and Zero:
Figure 6.
From the following formula:
V IN
12V
Modulator Gain =
=
= 4.2 (12.46dB)
V RAMP 1.9V × 3
2. Droop & DAC Offset Setting
For each channel the load current is 60A / 3 = 20A
and the ripple current, ΔIL, is given as:
2
5us x
where VRAMP : ramp amplitude of sawtooth wave
1
LC Filter Pole = 2π x LC = 1.2kHz and
ESR Zero =
1
2π x ESR x COUT
C1
= 8.8kHz
R3
C2
C3
R1
> VDIF
COMP
FB
+
R3,C3 are used in type
3 compensation scheme
(left NC in type 2)
DACOUT
Figure 5.
From the following formulas:
1
1
FZ =
, FP =
2π x R 2 x C 1
⎛ C1 × C 2 ⎞
2π x R 2 x ⎜
⎟
R2
⎝ C1 + C 2 ⎠
Middle Band Gain =
R1
By calculation, the FZ = 1kHz, FP = 200kHz and
Middle Band Gain is 10 (i.e 20dB).
The asymptotic bode plot of EA compensation and
PWM loop gain is shown as Figure 6.
DS9248-05 March 2007
ΔIL
= 18.36 A .
2
Using the following formula to select the appropriate
IX (MAX) for the S/H of GM amplifier:
R DS(ON) × 18.36A
I X (MAX) =
R SP
The suggested IX is in the order of 40 to 50μA, select
RSP = RSN = 2.4kΩ, then IX (MAX) will be 45.9μA.
VDROOP = 120mV = 45.9μA × 2 × 3 (phase no.) ×
RADJ, therefore RADJ will be 435Ω.
The RDS(ON) of MOSFET varies with temperature
rise. When the low side MOSFET working at 70°C
and 5000ppm/°C temperature coefficient of RDS(ON),
the RDS(ON) at 70°C is given as:
6mΩ × {1+ (70°C − 27°C) × 5000ppm/°C} = 7.3mΩ.
RADJ at 70°C is given as:
RADJ_27°C × (RDS(ON)_27°C / RDS(ON)_70°C) = 358Ω
The load current, IL, at S/H is 20 A −
b. EA Compensation Network:
Select R1 = 2.4kΩ, R2 = 24kΩ, C1 = 6.6nF,
C2 = 33pF and use the type 2 compensation
scheme shown in Figure 5.
R2
1.5V ⎛ 1.5V ⎞
x ⎜1 −
⎟ = 3.28A
2uH ⎝
12V ⎠
3. Over-Current Protection Setting
OCP trip point set at 30A for each channel,
IX =
RDS(ON) × 30A
0.6V
= 1.4 ×
, RIMAX = 11.2kΩ
RSP
RIMAX
Take the temperature rise into account, the RIMAX at
70°C will be:
RIMAX_27°C × (RDS(ON)_27°C / RDS(ON)_70°C) = 9.2kΩ
4. Soft-Start Capacitor Selection
CSS = 0.1μF is the suitable value for most application.
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11
RT9248
Preliminary
Layout Guide
Place the high-power switching components first, and separate them from sensitive nodes.
1. Most critical path: the current sense circuit is the most sensitive part of the converter. The current sense
resistors tied to ISP1,2,3 and ISN1,ISN23 should be located not more than 0.5 inch from the IC and away
from the noise switching nodes. The PCB trace of sense nodes should be parallel and as short as possible.
Kelvin connection of the sense component (additional sense resistor or MOSFET RDS(ON)) ensures the accurate
stable current sensing.
Keep well Kelvin sense to ensure the stable operation!
2. Switching ripple current path:
a. Input capacitor to high side MOSFET.
b. Low side MOSFET to output capacitor.
c. The return path of input and output capacitor.
d. Separate the power and signal GND.
e. The switching nodes (the connection node of high/low side MOSFET and inductor) is the most noisy points.
Keep them away from sensitive small-signal node.
f. Reduce parasitic R, L by minimum length, enough copper thickness and avoiding of via.
3. MOSFET driver should be closed to MOSFET.
4. The compensation, bypass and other function setting components should be near the IC and away from the noisy
power path.
SW1
L1
VOUT
VIN
RIN
COUT
CIN
RL
V
L2
SW2
Figure 7. Power Stage Ripple Current Path
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DS9248-05 March 2007
RT9248
Preliminary
Next to IC
+12V
CBP
VCC
IN
BST
+12V or +5V
PWM
VOSS
DRVH
LO1
SW
RT9603
CBP
IMAX
CBOOT
+5VIN
VCC
CIN
VCORE
CC
RT9248
COUT
DRVL
Kelvin
Sense
PGND
Next to IC
COMP
RSIP
Locate next
to FB Pin
FB
ISPx
ISNx
RFB
RSIN
Locate near MOSFETs
RC
VSEN
ADJ
GND
For Thermal Couple
Figure 8. Layout Consideration
DS9248-05 March 2007
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13
RT9248
Preliminary
Outline Dimension
D
L
E1
E
e
A2
A
A1
b
Symbol
Dimensions In Millimeters
Dimensions In Inches
Min
Max
Min
Max
A
0.850
1.200
0.033
0.047
A1
0.050
0.152
0.002
0.006
A2
0.800
1.050
0.031
0.041
b
0.178
0.305
0.007
0.012
D
9.601
9.804
0.378
0.386
e
0.650
0.026
E
6.300
6.500
0.248
0.256
E1
4.293
4.496
0.169
0.177
L
0.450
0.762
0.018
0.030
28-Lead TSSOP Plastic Package
Richtek Technology Corporation
Richtek Technology Corporation
Headquarter
Taipei Office (Marketing)
5F, No. 20, Taiyuen Street, Chupei City
8F, No. 137, Lane 235, Paochiao Road, Hsintien City
Hsinchu, Taiwan, R.O.C.
Taipei County, Taiwan, R.O.C.
Tel: (8863)5526789 Fax: (8863)5526611
Tel: (8862)89191466 Fax: (8862)89191465
Email: [email protected]
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14
DS9248-05 March 2007