LINER LT3085EDCB-PBF

LT3085
Adjustable 500mA Single
Resistor Low Dropout
Regulator
DESCRIPTION
FEATURES
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Outputs May be Paralleled for Higher Current and
Heat Spreading
Output Current: 500mA
Single Resistor Programs Output Voltage
1% Initial Accuracy of SET Pin Current
Output Adjustable to 0V
Current Limit Constant with Temperature
Low Output Noise: 40μVRMS (10Hz to 100kHz)
Wide Input Voltage Range: 1.2V to 36V
Low Dropout Voltage: 275mV
< 1mV Load Regulation
< 0.001%/ V Line Regulation
Minimum Load Current: 0.5mA
Stable with Minimum 2.2μF Ceramic Capacitor
Current Limit with Foldback and Overtemperature
Protected
8-Lead MSOP, and 6-Lead 2mm × 3mm DFN Packages
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A key feature of the LT3085 is the capability to supply a
wide output voltage range. By using a reference current
through a single resistor, the output voltage is programmed
to any level between zero and 36V. The LT3085 is stable
with 2.2μF of capacitance on the output, and the IC uses
small ceramic capacitors that do not require additional
ESR as is common with other regulators.
Internal protection circuitry includes current limiting
and thermal limiting. The LT3085 is offered in the 8-lead
MSOP and a low profile (0.75mm) 6-lead 2mm × 3mm
DFN package (both with an Exposed Pad for better thermal
characteristics).
APPLICATIONS
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The LT®3085 is a 500mA low dropout linear regulator that
can be paralleled to increase output current or spread
heat on surface mounted boards. Designed as a precision
current source and voltage follower, this new regulator
finds use in many applications requiring high current,
adjustability to zero, and no heat sink. The device also
brings out the collector of the pass transistor to allow
low dropout operation—down to 275mV—when used
with a second supply.
High Current All Surface Mount Supply
High Efficiency Linear Regulator
Post Regulator for Switching Supplies
Low Parts Count Variable Voltage Supply
Low Output Voltage Power Supplies
L, LT, LTC and LTM are registered trademarks of Linear Technology Corporation. All other
trademarks are the property of their respective owners.
TYPICAL APPLICATION
Variable Output Voltage 500mA Supply
LT3085
IN
VIN
1.2V TO 36V
N = 1676
VCONTROL
+
–
1μF
OUT
VOUT
SET
RSET
VOUT = RSET • 10μA
3085 TA01a
2.2μF
9.80
10.00
10.20
9.90
10.10
SET PIN CURRENT DISTRIBUTION (μA)
3085 TA01b
3085fa
1
LT3085
ABSOLUTE MAXIMUM RATINGS
(Note 1) All Voltages Relative to VOUT
VCONTROL Pin Voltage ..................................... 40V, –0.3V
IN Pin Voltage ................................................ 40V, –0.3V
SET Pin Current (Note 7) .................................... ±15mA
SET Pin Voltage (Relative to OUT) ..........................±10V
Output Short-Circuit Duration .......................... Indefinite
Operating Junction Temperature Range (Notes 2, 10)
E, I Grade ........................................... –40°C to 125°C
MP Grade........................................... –55°C to 125°C
Storage Temperature Range................... –65°C to 150°C
Lead Temperature (Soldering, 10 sec)
MS8E Package Only .......................................... 300°C
PIN CONFIGURATION
TOP VIEW
TOP VIEW
6 IN
OUT 1
OUT 2
7
OUT
OUT
OUT
SET
5 IN
4 VCONTROL
SET 3
1
2
3
4
9
8
7
6
5
IN
IN
NC
VCONTROL
MS8E PACKAGE
8-LEAD PLASTIC MSOP
DCB PACKAGE
6-LEAD (2mm s 3mm) PLASTIC DFN
TJMAX = 125°C, θJA = 73°C/W, θJC = 10.6°C/W
EXPOSED PAD (PIN 7) IS OUT, MUST BE SOLDERED TO VOUT ON PCB
SEE THE APPLICATIONS INFORMATION SECTION
TJMAX = 125°C, θJA = 60°C/W, θJC = 10°C/W
EXPOSED PAD (PIN 9) IS OUT, MUST BE SOLDERED TO VOUT ON PCB
SEE THE APPLICATIONS INFORMATION SECTION
ORDER INFORMATION
LEAD FREE FINISH
TAPE AND REEL
PART MARKING*
PACKAGE DESCRIPTION
TEMPERATURE RANGE
LT3085EDCB#PBF
LT3085EDCB#TRPBF
LDQQ
6-Lead (2mm × 3mm) Plastic DFN
–40°C to 125°C
LT3085EMS8E#PBF
LT3085EMS8E#TRPBF
LTDQP
8-Lead Plastic MSOP
–40°C to 125°C
LT3085IDCB#PBF
LT3085IDCB#TRPBF
LDQQ
6-Lead (2mm × 3mm) Plastic DFN
–40°C to 125°C
LT3085IMS8E#PBF
LT3085IMS8E#TRPBF
LTDQP
8-Lead Plastic MSOP
–40°C to 125°C
LT3085MPMS8E#PBF
LT3085MPMS8E#TRPBF
LTDWQ
8-Lead Plastic MSOP
–55°C to 125°C
LEAD BASED FINISH
TAPE AND REEL
PART MARKING*
PACKAGE DESCRIPTION
TEMPERATURE RANGE
LT3085EDCB
LT3085EDCB#TR
LDQQ
6-Lead (2mm × 3mm) Plastic DFN
–40°C to 125°C
LT3085EMS8E
LT3085EMS8E#TR
LTDQP
8-Lead Plastic MSOP
–40°C to 125°C
LT3085IDCB
LT3085IDCB#TR
LDQQ
6-Lead (2mm × 3mm) Plastic DFN
–40°C to 125°C
LT3085IMS8E
LT3085IMS8E#TR
LTDQP
8-Lead Plastic MSOP
–40°C to 125°C
LT3085MPMS8E
LT3085MPMS8E#TR
LTDWQ
8-Lead Plastic MSOP
–55°C to 125°C
Consult LTC Marketing for parts specified with wider operating temperature ranges. *The temperature grade is identified by a label on the shipping container.
For more information on lead free part marking, go to: http://www.linear.com/leadfree/
For more information on tape and reel specifications, go to: http://www.linear.com/tapeandreel/
3085fa
2
LT3085
ELECTRICAL CHARACTERISTICS
The l denotes the specifications which apply over the full operating
temperature range, otherwise specifications are at TA = 25°C (Note 2).
PARAMETER
CONDITIONS
MIN
TYP
MAX
UNITS
10
10
10.1
10.2
μA
μA
1.5
3
mV
mV
–1
nA
mV
SET Pin Current
ISET VIN = 1V, VCONTROL = 2V, ILOAD = 1mA, TJ = 25°C
VIN ≥ 1V, VCONTROL ≥ 2V, 1mA ≥ ILOAD ≥ 500mA (Note 9)
l
9.9
9.8
Output Offset Voltage (VOUT – VSET)
VOS VIN = 1V, VCONTROL = 2V, ILOAD = 1mA, TJ = 25°C
VIN = 1V, VCONTROL = 2V, ILOAD = 1mA
l
–1.5
–3
Load Regulation
Line Regulation
ΔISET ΔILOAD = 1mA to 500mA
ΔVOS ΔILOAD = 1mA to 500mA (Note 8)
–0.1
–0.6
l
ΔISET ΔVIN = 1V to 36V, ΔVCONTROL = 1V to 36V, ILOAD = 1mA
ΔVOS ΔVIN = 1V to 36V, ΔVCONTROL = 1V to 36V, ILOAD = 1mA
0.1
0.003
0.5
nA/V
mV/V
300
500
1
μA
mA
Minimum Load Current (Notes 3, 9)
VIN = VCONTROL = 10V
VIN = VCONTROL = 36V
l
l
VCONTROL Dropout Voltage (Note 4)
ILOAD = 100mA
ILOAD = 500mA
l
1.2
1.35
1.6
V
V
VIN Dropout Voltage (Note 4)
ILOAD = 100mA
ILOAD = 500mA
l
l
85
275
150
450
mV
mV
VCONTROL Pin Current (Note 5)
ILOAD = 100mA
ILOAD = 500mA
l
l
3
8
6
15
mA
mA
Current Limit (Note 9)
VIN = 5V, VCONTROL = 5V, VSET = 0V, VOUT = -0.1V
l
Error Amplifier RMS Output Noise (Note 6)
ILOAD = 500mA, 10Hz≤f≤100kHz, COUT=10μF, CSET=0.1μF
650
mA
33
μVRMS
Reference Current RMS Output Noise (Note 6) 10Hz≤f≤100kHz
0.7
nARMS
Ripple Rejection
f=120Hz, VRIPPLE=0.5VP-P, ILOAD=0.1A, CSET=0.1μF, COUT=2.2μF
f=10kHz
f=1MHz
90
75
20
dB
dB
dB
Thermal Regulation, ISET
10ms Pulse
Note 1: Stresses beyond those listed under Absolute Maximum Ratings
may cause permanent damage to the device. Exposure to any Absolute
Maximum Rating condition for extended periods may affect device
reliability and lifetime.
Note 2. Unless otherwise specified, all voltages are with respect to VOUT.
The LT3085 is tested and specified under pulse load conditions such that
TJ ≅ TA. The LT3085E is 100% tested at TA = 25°C. Performance of the
LT3085E over the full –40°C to 125°C operating junction temperature
range is assured by design, characterization, and correlation with
statistical process controls. The LT3085I regulators are guaranteed
over the full –40°C to 125°C operating junction temperature range. The
LT3085 (MP grade) is 100% tested and guaranteed over the –55°C to
125°C operating junction temperature range.
Note 3. Minimum load current is equivalent to the quiescent current of
the part. Since all quiescent and drive current is delivered to the output
of the part, the minimum load current is the minimum current required to
maintain regulation.
Note 4. For the LT3085, dropout is caused by either minimum control
voltage (VCONTROL) or minimum input voltage (VIN). Both parameters are
specified with respect to the output voltage. The specifications represent
the minimum input-to-output differential voltage required to maintain
regulation.
500
0.003
%/W
Note 5. The VCONTROL pin current is the drive current required for the
output transistor. This current will track output current with roughly a 1:60
ratio. The minimum value is equal to the quiescent current of the device.
Note 6. Output noise is lowered by adding a small capacitor across the
voltage setting resistor. Adding this capacitor bypasses the voltage setting
resistor shot noise and reference current noise; output noise is then equal
to error amplifier noise (see Applications Information section).
Note 7. The SET pin is clamped to the output with diodes through 1k
resistors. These resistors and diodes will only carry current under
transient overloads.
Note 8. Load regulation is Kelvin sensed at the package.
Note 9. Current limit includes foldback protection circuitry. Current limit
decreases at higher input-to-output differential voltages. See the Typical
Performance Characteristics graphs for more information.
Note 10. This IC includes over-temperature protection that is intended
to protect the device during momentary overload conditions. Junction
temperature will exceed the maximum operating junction temperature
when over-temperature protection is active. Continuous operation above
the specified maximum operating junction temperature may impair device
reliability.
3085fa
3
LT3085
TYPICAL PERFORMANCE CHARACTERISTICS
Set Pin Current
Set Pin Current Distribution
Offset Voltage (VOUT – VSET)
10.20
2.0
N = 1676
1.5
10.10
OFFSET VOLTAGE (mV)
SET PIN CURRENT (μA)
10.15
10.05
10.00
9.95
9.90
9.85
1.0
0.5
0
–0.5
–1.0
–1.5
9.80
–50 –25
0
9.80
25 50 75 100 125 150
TEMPERATURE (°C)
–2.0
–50 –25
10.00
10.20
9.90
10.10
SET PIN CURRENT DISTRIBUTION (μA)
0
25 50 75 100 125 150
TEMPERATURE (°C)
3085 G02
3085 G01
Offset Voltage Distribution
3085 G03
Offset Voltage
Offset Voltage
1.00
0.25
ILOAD = 1mA
N = 1676
0.75
0
0.50
–0.25
OFFSET VOLTAGE (mV)
OFFSET VOLTAGE (mV)
TJ = 25°C
0.25
0
–0.25
–0.50
–0.75
–1.00
2
6
24
30
18
INPUT-TO-OUTPUT VOLTAGE (V)
0
12
0
–0.3
–10
–0.4
–20
–0.5
–30
(VOUT – VSET)
–0.6
–40
–50
CHANGE IN OFFSET VOLTAGE
–60
25 50 75 100 125 150
TEMPERATURE (°C)
3085 G07
MINIMUM LOAD CURRENT (mA)
10
CHANGE IN REFERENCE CURRENT
0
–1.75
0 50 100 150 200 250 300 350 400 450 500
LOAD CURRENT (mA)
3085 G06
Dropout Voltage
(Minimum IN Voltage)
400
0.8
CHANGE IN REFERENCE CURRENT
WITH LOAD (nA)
CHANGE IN OFFSET VOLTAGE WITH LOAD (mV)
20
ΔILOAD = 1mA TO 500mA
VIN – VOUT = 2V
–0.8
–50 –25
36
Minimum Load Current
0
–0.7
–1.25
3085 G05
Load Regulation
–0.2
–1.00
–1.50
3085 G04
–0.1
TJ = 125°C
–0.75
0.7
MINIMUM IN VOLTAGE (VIN – VOUT) (mV)
0
–1
1
VOS DISTRIBUTION (mV)
–2
–0.50
VIN, CONTROL – VOUT = 36V
0.6
0.5
0.4
VIN, CONTROL – VOUT = 1.5V
0.3
0.2
0.1
0
–50 –25
350
TJ = 125°C
300
250
200
TJ = 25°C
150
100
50
0
0
25
50
75
100 125 150
TEMPERATURE (°C)
3085 G08
0
50 100 150 200 250 300 350 400 450 500
LOAD CURRENT (mA)
3085 G09
3085fa
4
LT3085
TYPICAL PERFORMANCE CHARACTERISTICS
Dropout Voltage
(Minimum IN Voltage)
1.6
1.6
1.4
MINIMUM CONTROL VOLTAGE
(VCONTROL – VOUT) (V)
350
ILOAD = 500mA
300
250
200
150
ILOAD = 100mA
100
1.2
1.0
TJ = 125°C
0.8
TJ = 25°C
0.6
0.4
0.2
50
0
25 50 75 100 125 150
TEMPERATURE (°C)
Current Limit
700
600
600
200
500
400
200
0
0
25 50 75 100 125 150
TEMPERATURE (°C)
5
10 15 20 25 30 35
INPUT-TO-OUTPUT DIFFERENTIAL (V)
Load Transient Response
OUTPUT VOLTAGE
DEVIATION (mV)
OUTPUT VOLTAGE
DEVIATION (mV)
0
IN/CONTROL
VOLTAGE (V)
LOAD CURRENT
(mA)
–100
VIN = VCONTROL = 3V
VOUT = 1.5V
CSET = 0.1μF
0
VOUT = 1.5V
ILOAD = 10mA
COUT = 2.2μF
CERAMIC
CSET = 0.1μF
CERAMIC
–50
6
4
2
0
0 10
20 30 40 50 60 70 80 90 100
TIME (μs)
3085 G16
COUT = 10μF CERAMIC
COUT = 2.2μF CERAMIC
200
100
0
0
20 40 60 80 100 120 140 160 180 200
TIME (μs)
3085 G15
Turn-On Response
50
–100
COUT = 2.2μF CERAMIC
250
–20
Line Transient Response
50
0
40
100
150
500
0
3085 G14
3085 G13
–50
20
–40
100
COUT = 10μF CERAMIC
VOUT = 1.5V
CSET = 0.1μF
VIN = VCONTROL = 3V
40
300
100
100
25 50 75 100 125 150
TEMPERATURE (°C)
Load Transient Response
LOAD CURRENT
(mA)
300
0
3085 G12
OUTPUT VOLTAGE
DEVIATION (mV)
CURRENT LIMIT (mA)
CURRENT LIMIT (mA)
VIN = 7V
VOUT = 0V
0
0.4
60
TJ = 25°C
0
–50 –25
0.6
Current Limit
700
400
0.8
3085 G11
3085 G10
500
ILOAD = 100mA
1.0
0
–50 –25
0 50 100 150 200 250 300 350 400 450 500
LOAD CURRENT (mA)
0
10 20 30 40 50 60 70 80 90 100
TIME (μs)
3085 G17
OUTPUT VOLTAGE (V)
0
1.2
0.2
1.5
1
COUT = 2.2μF
CERAMIC
RSET = 100k
CSET = 0
RLOAD = 2Ω
0.5
0
8
IN/CONTROL
VOLTAGE (V)
0
–50 –25
ILOAD = 500mA
1.4
TJ = –50°C
MINIMUM CONTROL VOLTAGE
(VCONTROL – VOUT) (V)
400
MINIMUM IN VOLTAGE (VIN – VOUT) (mV)
Dropout Voltage (Minimum
VCONTROL Pin Voltage)
Dropout Voltage (Minimum
VCONTROL Pin Voltage)
6
4
2
0
0
2
4
6
8 10 12 14 16 18 20
TIME (μs)
3085 G18
3085fa
5
LT3085
TYPICAL PERFORMANCE CHARACTERISTICS
VCONTROL Pin Currrent
8
18
800
VIN = VCONTROL = 2V
VIN = VOUT = 1V
CONTROL PIN CURRENT (mA)
7
16
14
ILOAD = 500mA
12
10
DEVICE IN
CURRENT LIMIT
8
6
4
TJ = –50°C
6
TJ = 25°C
5
4
TJ = 125°C
3
2
VOUT
VIN = 20V
RTEST
500
400
VIN = 10V
300
VIN = 5V
200
100
ILOAD = 1mA
0
0
0
30
12
18
24
6
INPUT-TO-OUTPUT DIFFERENTIAL (V)
0
0
36
0.1
0.2
0.3
LOAD CURRENT (A)
0.4
100
90
90
80
80
RIPPLE REJECTION (dB)
ILOAD = 100mA
60
50
40
30
VIN = VCONTROL = VOUT (NOMINAL) +2V
RIPPLE = 50mVP–P
COUT = 2.2μF CERAMIC
CSET = 0.1μF CERAMIC
20
10
0
10
100
1k
10k
FREQUENCY (Hz)
100k
2k
Ripple Rejection - Dual Supply
- IN Pin
100
90
ILOAD = 100mA
70
60
ILOAD = 500mA
50
40
VIN = VOUT (NOMINAL) + 1V
VCONTROL = VOUT (NOMINAL) +2V
RIPPLE = 50mVP–P
COUT = 2.2μF CERAMIC
CSET = 0.1μF CERAMIC
30
20
10
70
60
ILOAD = 500mA
50
40
VIN = VCONTROL +2V
VCONTROL = VOUT (NOMINAL) +2V
RIPPLE = 50mVP–P
COUT = 2.2μF CERAMIC
CSET = 0.1μF CERAMIC
30
20
10
0
1M
ILOAD = 100mA
80
RIPPLE REJECTION (dB)
100
ILOAD = 500mA
1k
RTEST (Ω)
3085 G21
Ripple Rejection - Dual Supply
- VCONTROL Pin
Ripple Rejection - Single Supply
70
0
0.5
3085 G20
3085 G19
RIPPLE REJECTION (dB)
VIN
600
1
2
SET PIN = 0V
700
OUTPUT VOLTAGE (mV)
20
CONTROL PIN CURRENT (mA)
Residual Output Voltage with
Less Than Minimum Load
VCONTROL Pin Current
0
10
100
1k
10k
FREQUENCY (Hz)
100k
3085 G22
1M
10
100
10k
1k
FREQUENCY (Hz)
100k
3085 G23
Ripple Rejection (120Hz)
3085 G24
Noise Spectral Density
85
1M
Output Voltage Noise
10k
1k
1k
100
ERROR AMPLIFIER NOISE
SPECTRAL DENSITY (nV/√Hz)
83
82
81
80
79
78
SINGLE SUPPLY OPERATION
VIN = VOUT (NOMINAL) +2V
RIPPLE = 50mVP–P, f = 120Hz
ILOAD = 0.1A
COUT = 2.2μF, CSET = 0.1μF
77
–50 –25
0
25 50 75 100 125 150
FREQUENCY (Hz)
3085 G25
100
10
10
1
10
1.0
100
1k
10k
FREQUENCY (Hz)
REFERENCE CURRENT NOISE
SPECTRAL DENSITY (pA/ √Hz)
RIPPLE REJECTION (dB)
84
VOUT
100μV/DIV
TIME 1ms/DIV
3085 G27
VOUT = 1V
RSET = 100k
CSET = O.1μF
COUT = 10μF
ILOAD = 1.1A
0.1
100k
3085 G26
3085fa
6
LT3085
TYPICAL PERFORMANCE CHARACTERISTICS
Error Amplifier Gain and Phase
Ripple Rejection - SET Pin Current
150
144
135
15
72
120
12
0
ILOAD = 500mA
9
–72
ILOAD = 100mA
6
–144
ILOAD = 500mA
3
–216
0
–288
–3
ILOAD = 100mA
–6
–9
PHASE (deg)
GAIN (dB)
18
10
100
10k
1k
FREQUENCY (Hz)
100k
90
75
CSET = 0
60
45
30
–432
15
–504
1M
CSET = 0.1μF
105
–360
3085 G28
PIN FUNCTIONS
RIPPLE REJECTION (dB)
216
21
0
10
RSET = 100k
VIN = VCONTROL = VOUT (NOMINAL) +2V
RIPPLE = 50mVP–P
100
1k
10k
FREQUENCY (Hz)
100k
1M
3085 G29
(DCB/MS8E)
VCONTROL (Pin 4/Pin 5): This pin is the supply pin for the
control circuitry of the device. The current flow into this
pin is about 1.7% of the output current. For the device to
regulate, this voltage must be more than 1.2V to 1.35V
greater than the output voltage (see VCONTROL Dropout
Voltage in the Electrical Characteristics table and graphs
in the Typical Performance Characteristics). The LT3085
requires a bypass capacitor at VCONTROL if more than six
inches away from the main input filter capacitor. The output
impedance of a battery rises with frequency, so include
a bypass capacitor in battery-powered circuits. A bypass
capacitor in the range of 1μF to 10μF suffices.
IN (Pins 5, 6/Pins 7, 8): This is the collector to the power
device of the LT3085. The output load current is supplied
through this pin. For the device to regulate, the voltage at
this pin must be more than 0.1V to 0.5V greater than the
output voltage (see VIN Dropout Voltage in the Electrical
Characteristics table and graphs in the Typical Performance Characteristics). The LT3085 requires a bypass
capacitor at IN if more than six inches away from the main
input filter capacitor. The output impedance of a battery
rises with frequency, so include a bypass capacitor in
battery-powered circuits. A bypass capacitor in the range
of 1μF to 10μF suffices.
NC (NA/Pin 6): No Connection. The No Connect pin has
no connection to internal circuitry and may be tied to VIN,
VCONTROL, VOUT, GND, or floated.
OUT (Pins 1, 2/Pins 1, 2, 3): This is the power output
of the device. There must be a minimum load current of
1mA or the output may not regulate. A minimum 2.2μF
output capacitor is required for stability.
SET(Pin 3/Pin 4): This pin is the non-inverting input to the
error amplifier and the regulation set point for the device.
A fixed current of 10μA flows out of this pin through a
single external resistor, which programs the output voltage
of the device. Output voltage range is zero to the absolute
maximum rated output voltage. Transient performance can
be improved and output noise can be decreased by adding
a small capacitor from the SET pin to ground.
Exposed Pad (Pin 7/Pin 9): OUT. Tie directly to Pins 1, 2/
Pins 2, 3 directly at the PCB.
3085fa
7
LT3085
BLOCK DIAGRAM
IN
VCONTROL
10μA
+
–
3085 BD
SET
OUT
APPLICATIONS INFORMATION
The LT3085 regulator is easy to use and has all the protection features expected in high performance regulators.
Included are short-circuit protection and safe operating
area protection, as well as thermal shutdown.
The LT3085 is especially well suited to applications needing
multiple rails. The new architecture adjusts down to zero
with a single resistor, handling modern low voltage digital
IC’s as well as allowing easy parallel operation and thermal
management without heat sinks. Adjusting to “zero” output
allows shutting off the powered circuitry and when the
input is pre-regulated – such as a 5V or 3.3V input supply
– external resistors can help spread the heat.
A precision “0” TC 10μA internal current source is connected
to the non-inverting input of a power operational amplifier.
The power operational amplifier provides a low impedance
buffered output to the voltage on the non-inverting input.
A single resistor from the non-inverting input to ground
sets the output voltage and if this resistor is set to zero,
zero output results. As can be seen, any output voltage
can be obtained from zero up to the maximum defined by
the input power supply.
What is not so obvious from this architecture are the benefits of using a true internal current source as the reference
as opposed to a bootstrapped reference in older regulators.
A true current source allows the regulator to have gain
and frequency response independent of the impedance on
the positive input. Older adjustable regulators, such as the
LT1086, have a change in loop gain with output voltage
as well as bandwidth changes when the adjustment pin
is bypassed to ground. For the LT3085, the loop gain is
unchanged by changing the output voltage or bypassing.
Output regulation is not fixed at a percentage of the output
voltage but is a fixed fraction of millivolts. Use of a true
current source allows all the gain in the buffer amplifier
to provide regulation and none of that gain is needed to
amplify up the reference to a higher output voltage.
The LT3085 has the collector of the output transistor
connected to a separate pin from the control input. Since the
dropout on the collector (IN pin) is only 275mV, two supplies
can be used to power the LT3085 to reduce dissipation: a
higher voltage supply for the control circuitry and a lower
voltage supply for the collector. This increases efficiency and
reduces dissipation. To further spread the heat, a resistor
can be inserted in series with the collector to move some
of the heat out of the IC and spread it on the PC board.
3085fa
8
LT3085
APPLICATIONS INFORMATION
The LT3085 can be operated in two modes. Three terminal
mode has the control pin connected to the power input pin
which gives a limitation of 1.35V dropout. Alternatively, the
“control” pin can be tied to a higher voltage and the power
IN pin to a lower voltage giving 275mV dropout on the
IN pin and minimizing the power dissipation. This allows
for a 500mA supply regulating from 2.5VIN to 1.8VOUT or
1.8VIN to 1.2VOUT with low dissipation.
With the low level current used to generate the reference
voltage, leakage paths to or from the SET pin can create
errors in the reference and output voltages. High quality
insulation should be used (e.g., Teflon, Kel-F); cleaning
of all insulating surfaces to remove fluxes and other residues will probably be required. Surface coating may be
necessary to provide a moisture barrier in high humidity
environments.
Setting Output Voltage
Table 1. 1% Resistors for Common Output Voltages
The LT3085 generates a 10μA reference current that flows
out of the SET pin. Connecting a resistor from SET to
ground generates a voltage that becomes the reference
point for the error amplifier (see Figure 1). The reference
voltage is a straight multiplication of the SET pin current
and the value of the resistor. Any voltage can be generated
and there is no minimum output voltage for the regulator.
Table 1 lists many common output voltages and standard
1% resistor values used to generate that output voltage.
A minimum load current of 1mA is required to maintain
regulation regardless of output voltage. For true zero
voltage output operation, this 1mA load current must be
returned to a negative supply voltage.
LT3085
IN
VCONTROL
10μA
+
VIN
+
–
+
VCONTROL
OUT
VOU
SET
COU
RSET
CSET
3085 F01
VOUT = RSET • 10μA
Figure 1. Basic Adjustable Regulator
VOUT
RSET
1V
100k
1.2V
121k
1.5V
150k
1.8V
182k
2.5V
249k
3.3V
332k
5V
499k
Board leakage can be minimized by encircling the SET
pin and circuitry with a guardring operated at a potential
close to itself; the guardring should be tied to the OUT pin.
Guarding both sides of the circuit board is required. Bulk
leakage reduction depends on the guard ring width. Ten
nanoamperes of leakage into or out of the SET pin and
associated circuitry creates a 0.1% error in the reference
voltage. Leakages of this magnitude, coupled with other
sources of leakage, can cause significant offset voltage and
reference drift, especially over a wide temperature range.
If guardring techniques are used, this bootstraps any
stray capacitance at the SET pin. Since the SET pin is
a high impedance node, unwanted signals may couple
into the SET pin and cause erratic behavior. This will
be most noticeable when operating with minimum
output capacitors at full load current. The easiest way
to remedy this is to bypass the SET pin with a small
amount of capacitance from SET to ground, 10pF to
20pF is sufficient.
3085fa
9
LT3085
APPLICATIONS INFORMATION
Input Capacitance and Stability
The LT3085 is designed to be stable with a minimum
capacitance of 1μF at each input pin. Ceramic capacitors
with low ESR are available for use to bypass these pins,
but in cases where long wires connect the LT3085 inputs
to a power supply (and also from ground of the LT3085
circuitry back to power supply ground), this causes instabilities. This happens due to the wire inductance forming
an LC tank circuit with the input capacitor and not as a
result of instability on the LT3085.
The self-inductance, or isolated inductance, of a wire is
directly proportional to its length. The diameter does not
have a major influence on its self-inductance. As an example, the self-inductance of a 2-AWG isolated wire with a
diameter of 0.26in. is approximately half the self-inductance
of a 30-AWG wire with a diameter of 0.01in. One foot of
30-AWG wire has 465nH of self-inductance.
The overall self-inductance of a wire is reduced in one of
two ways. One is to divide the current flowing towards
the LT3085 between two parallel conductors. In this
case, the farther apart the wires are from each other, the
more the self-inductance is reduced, up to a 50% reduction when placed a few inches apart. Splitting the wires
basically connects two equal inductors in parallel, but
placing them in close proximity gives the wires mutual
inductance adding to the self-inductance. The second
and most effective way to reduce overall inductance is to
place both forward- and return-current conductors (the
wire for the input and the wire for ground) in very close
proximity. Two 30-AWG wires separated by only 0.02in.
used as forward- and return-current conductors reduce
the overall self-inductance to approximately one-fifth that
of a single isolated wire.
If the LT3085 is powered by a battery mounted in close
proximity on the same circuit board, a 2.2μF input capacitor is sufficient for stability. When powering from distant
supplies, use a larger input capacitor based on a guideline of 1μF plus another 1μF per 8 inches of wire length.
As power supply impedance does vary, the amount of
capacitance needed to stabilize your application will also
vary. Extra capacitance placed directly on the output of
the power supply requires an order of magnitude more
capacitance as opposed to placing extra capacitance close
to the LT3085.
Using series resistance between the power supply and
the input of the LT3085 also stabilizes the application.
As little as 0.1Ω to 0.5Ω, often less, is all that is needed
to provide damping in the circuit. If the extra impedance
between the power supply and the input is unacceptable,
placing the resistors in series with the capacitors will provide damping to prevent the LC resonance from causing
full-blown oscillation.
Stability and Output Capacitance
The LT3085 requires an output capacitor for stability. It
is designed to be stable with most low ESR capacitors
(typically ceramic, tantalum or low ESR electrolytic). A
minimum output capacitor of 2.2μF with an ESR of 0.5Ω
or less is recommended to prevent oscillations. Larger
values of output capacitance decrease peak deviations
and provide improved transient response for larger load
current changes. Bypass capacitors, used to decouple
individual components powered by the LT3085, increase
the effective output capacitor value.
3085fa
10
LT3085
APPLICATIONS INFORMATION
BOTH CAPACITORS ARE 16V,
1210 CASE SIZE, 10μF
0
CHANGE IN VALUE (%)
Extra consideration must be given to the use of ceramic
capacitors. Ceramic capacitors are manufactured with a
variety of dielectrics, each with different behavior across
temperature and applied voltage. The most common
dielectrics used are specified with EIA temperature
characteristic codes of Z5U, Y5V, X5R and X7R. The Z5U and
Y5V dielectrics are good for providing high capacitances
in a small package, but they tend to have strong voltage
and temperature coefficients as shown in Figures 2
and 3. When used with a 5V regulator, a 16V 10μF Y5V
capacitor can exhibit an effective value as low as 1μF to
2μF for the DC bias voltage applied and over the operating
temperature range. The X5R and X7R dielectrics result in
more stable characteristics and are more suitable for use
as the output capacitor. The X7R type has better stability
across temperature, while the X5R is less expensive and is
available in higher values. Care still must be exercised when
using X5R and X7R capacitors; the X5R and X7R codes
only specify operating temperature range and maximum
capacitance change over temperature. Capacitance change
due to DC bias with X5R and X7R capacitors is better than
Y5V and Z5U capacitors, but can still be significant enough
to drop capacitor values below appropriate levels. Capacitor
DC bias characteristics tend to improve as component
case size increases, but expected capacitance at operating
voltage should be verified.
20
X5R
–20
–40
–60
Y5V
–80
–100
0
2
4
14
8
6
10 12
DC BIAS VOLTAGE (V)
16
3085 F02
Figure 2. Ceramic Capacitor DC Bias Characteristics
40
20
CHANGE IN VALUE (%)
For improvement in transient performance, place a capacitor across the voltage setting resistor. Capacitors up to
1μF can be used. This bypass capacitor reduces system
noise as well, but start-up time is proportional to the time
constant of the voltage setting resistor (RSET in Figure 1)
and SET pin bypass capacitor.
X5R
0
–20
–40
Y5V
–60
–80
BOTH CAPACITORS ARE 16V,
1210 CASE SIZE, 10μF
–100
–50 –25
50
25
75
0
TEMPERATURE (°C)
100
125
3085 F03
Figure 3. Ceramic Capacitor Temperature Characteristics
3085fa
11
LT3085
APPLICATIONS INFORMATION
Voltage and temperature coefficients are not the only
sources of problems. Some ceramic capacitors have a
piezoelectric response. A piezoelectric device generates
voltage across its terminals due to mechanical stress,
ceramic capacitor the stress can be induced by vibrations
in the system or thermal transients.
Paralleling Devices
LT3085’s may be paralleled with other LT308X devices to
obtain higher output current. The SET pins are tied together
and the IN pins are tied together. This is the same whether
it’s in three terminal mode or has separate input supplies.
The outputs are connected in common using a small piece
of PC trace as a ballast resistor to equalize the currents.
PC trace resistance in milliohms/inch is shown in Table
1. Only a tiny area is needed for ballasting.
Of course, more than two LT308X’s can be paralleled for
even higher output current. They are spread out on the
PC board, spreading the heat. Input resistors can further
spread the heat if the input-to-output difference is high.
Thermal Performance
In this example, two LT3085 2mm × 3mm DFN devices
are mounted on a 1oz copper 4-layer PC board. They are
placed approximately 1.5 inches apart and the board is
mounted vertically for convection cooling. Two tests were
set up to measure the cooling performance and current
sharing of these devices.
VIN
LT3080
VCONTROL
+
–
Table 1. PC Board Trace Resistance
WEIGHT (oz)
10 mil WIDTH
20 mil WIDTH
1
54.3
27.1
2
27.1
13.6
Trace resistance is measured in mΩ/in
The worst-case offset between the SET pin and the output
of only ±1.5mV allows very small ballast resistors to be
used. As shown in Figure 4, the two devices have a small
10mΩ and 20mΩ ballast resistors, which at full output
current gives better than 80% equalized sharing of the
current. The external resistance of 20mΩ (6.6mΩ for the
two devices in parallel) only adds about 10mV of output
regulation drop at an output of 1.5A. Even with an output
voltage as low as 1V, this only adds 1% to the regulation.
OUT 10mΩ
SET
VIN
4.8V TO 28V
VIN
LT3085
VCONTROL
+
–
1μF
OUT 20mΩ
SET
VOUT
3.3V
1.5A
10μF
165k
3085 F04
Figure 4. Parallel Devices
3085fa
12
LT3085
APPLICATIONS INFORMATION
The first test was done with approximately 1.6V
input- to-output and 0.5A per device. This gave a 800mW
dissipation in each device and a 1A output current. The
temperature rise above ambient is approximately 28°C
and both devices were within plus or minus 1°C. Both the
thermal and electrical sharing of these devices is excellent. The thermograph in Figure 5 shows the temperature
distribution between these devices and the PC board
reaches ambient temperature within about a half an inch
from the devices.
Both at low power and relatively high power levels devices can be paralleled for higher output current. Current
sharing and thermal sharing is excellent, showing that
acceptable operation can be had while keeping the peak
temperatures below excessive operating temperatures on
a board. This technique allows higher operating current
linear regulation to be used in systems where it could
never be used before.
The power is then increased with 3.4V across each device.
This gives 1.7 watts dissipation in each device and a device
temperature of about 90°C, about 65°C above ambient
as shown in Figure 6. Again, the temperature matching
between the devices is within 2°C, showing excellent
tracking between the devices. The board temperature has
reached approximately 40°C within about 0.75 inches of
each device.
The LT3085 offers numerous advantages when it comes
to dealing with noise. There are several sources of noise
in a linear regulator. The most critical noise source for any
LDO is the reference; from there, the noise contribution
from the error amplifier must be considered, and the gain
created by using a resistor divider cannot be forgotten.
While 90°C is an acceptable operating temperature for these
devices, this is in 25°C ambient. For higher ambients, the
temperature must be controlled to prevent device temperature from exceeding 125°C. A 3-meter-per-second airflow
across the devices will decrease the device temperature
about 20°C providing a margin for higher operating ambient temperatures.
Figure 5. Temperature Rise at 800mW Dissipation
Quieting the Noise
Traditional low noise regulators bring the voltage reference out to an external pin (usually through a large value
resistor) to allow for bypassing and noise reduction of
reference noise. The LT3085 does not use a traditional
voltage reference like other linear regulators, but instead
uses a reference current. That current operates with typical noise current levels of 2.3pA/√Hz (0.7nARMS over the
10Hz to 100kHz bandwidth). The voltage noise of this is
equal to the noise current multiplied by the resistor value.
Figure 6. Temperature Rise at 1.7W Dissipation
3085fa
13
LT3085
APPLICATIONS INFORMATION
The resistor generates spot noise equal to√4kTR (k =
Boltzmann’s constant, 1.38 • 10-23 J/°K, and T is absolute
temperature) which is RMS summed with the reference
current noise. To lower reference noise, the voltage setting resistor may be bypassed with a capacitor, though
this causes start-up time to increase as a factor of the RC
time constant.
The LT3085 uses a unity-gain follower from the SET pin
to drive the output, and there is no requirement to use
a resistor to set the output voltage. Use a high accuracy
voltage reference placed at the SET pin to remove the errors in output voltage due to reference current tolerance
and resistor tolerance. Active driving of the SET pin is
acceptable; the limitations are the creativity and ingenuity
of the circuit designer.
One problem that a normal linear regulator sees with reference voltage noise is that noise is gained up along with the
output when using a resistor divider to operate at levels
higher than the normal reference voltage. With the LT3085,
the unity-gain follower presents no gain whatsoever from
the SET pin to the output, so noise figures do not increase
accordingly. Error amplifier noise is typically 100nV/√Hz
(33μVRMS over the 10Hz to 100kHz bandwidth); this is
another factor that is RMS summed in to give a final noise
figure for the regulator.
Curves in the Typical Performance Characteristics show
noise spectral density and peak-to-peak noise characteristics for both the reference current and error amplifier
over the 10Hz to 100kHz bandwidth.
Overload Recovery
Like many IC power regulators, the LT3085 has safe operating area (SOA) protection. The SOA protection decreases
current limit as the input-to-output voltage increases and
keeps the power dissipation at safe levels for all values
of input-to-output voltage. The LT3085 provides some
output current at all values of input-to-output voltage up
to the device breakdown. See the Current Limit curve in
the Typical Performance Characteristics.
When power is first turned on, the input voltage rises and
the output follows the input, allowing the regulator to start
into very heavy loads. During start-up, as the input voltage
is rising, the input-to-output voltage differential is small,
allowing the regulator to supply large output currents.
With a high input voltage, a problem can occur wherein
removal of an output short will not allow the output voltage to recover. Other regulators, such as the LT1085 and
LT1764A, also exhibit this phenomenon so it is not unique
to the LT3085.
The problem occurs with a heavy output load when the
input voltage is high and the output voltage is low. Common situations are immediately after the removal of a
short circuit. The load line for such a load may intersect
the output current curve at two points. If this happens,
there are two stable operating points for the regulator.
With this double intersection, the input power supply may
need to be cycled down to zero and brought up again to
make the output recover.
Load Regulation
Because the LT3085 is a floating device (there is no ground
pin on the part, all quiescent and drive current is delivered
to the load), it is not possible to provide true remote load
sensing. Load regulation will be limited by the resistance
of the connections between the regulator and the load.
The data sheet specification for load regulation is Kelvin
sensed at the pins of the package. Negative side sensing
is a true Kelvin connection, with the bottom of the voltage
setting resistor returned to the negative side of the load
(see Figure 7). Connected as shown, system load regulation
will be the sum of the LT3085 load regulation and the
parasitic line resistance multiplied by the output current.
It is important to keep the positive connection between
the regulator and load as short as possible and use large
wire or PC board traces.
3085fa
14
LT3085
APPLICATIONS INFORMATION
IN
LT3085
VCONTROL
PARASITIC
RESISTANCE
+
–
OUT
SET RSET
RP
RP
LOAD
RP
3085 F07
Figure 7. Connections for Best Load Regulation
Internal Parasitic Diodes and Protection Diodes
In normal operation, the LT3085 does not require protection
diodes. Older three-terminal regulators require protection
diodes between the VOUT pin and the input pin or between
the ADJ pin and the VOUT pin to prevent die overstress.
On the LT3085, internal resistors and diodes limit current
paths on the SET pin. Even with bypass capacitors on the
SET pin, no protection diode is needed to ensure device
safety under short-circuit conditions. The SET pin handles
±10V (either transient or DC) with respect to OUT without
any device degradation.
Internal parasitic diodes exist between OUT and the two
inputs. Negative input voltages are transferred to the output
and may damage sensitive loads. Reverse-biasing either
input to OUT will turn on these parasitic diodes and allow
current flow. This current flow will bias internal nodes
of the LT3085 to levels that possibly cause errors when
suddenly returning to normal operating conditions and
expecting the device to start and operate. Prediction of
results of a bias fault is impossible, immediate return to
normal operating conditions can be just as difficult after
a bias fault. Suffice it to say that extra wait time, power
cycling, or protection diodes may be needed to allow the
LT3085 to return to a normal operating mode as quickly
as possible.
Protection diodes are not otherwise needed between
the OUT pin and IN pin. The internal diodes can handle
microsecond surge currents of up to 50A. Even with
large output capacitors, obtaining surge currents of those
magnitudes is difficult in normal operation. Only with large
output capacitors, such as 1000μF to 5000μF, and with
IN instantaneously shorted to ground will damage occur.
A crowbar circuit at IN is capable of generating those
levels of currents, and then protection diodes from OUT
to IN are recommended. Normal power supply cycling or
system “hot plugging and unplugging” does not do any
damage.
A protection diode between OUT and VCONTROL is usually
not needed. The internal parasitic diode on VCONTROL of
the LT3085 handles microsecond surge currents of 1A to
10A. Again, this only occurs when using crowbar circuits
with large value output capacitors. Since the VCONTROL
pin is usually a low current supply, this is unlikely. Still,
a protection diode is recommended if VCONTROL can be
instantaneously shorted to ground. Normal power supply
cycling or system “hot plugging and unplugging” does
not do any damage.
If the LT3085 is configured as a three-terminal (single supply)
regulator with IN and VCONTROL shorted together, the internal
diode of the IN pin will protect the VCONTROL pin.
Like any other regulator, exceeding the maximum inputto-output differential causes internal transistors to break
down and then none of the internal protection circuitry
is functional.
Thermal Considerations
The LT3085 has internal power and thermal limiting circuitry designed to protect it under overload conditions.
For continuous normal load conditions, maximum junction temperature must not be exceeded. It is important
to give consideration to all sources of thermal resistance
3085fa
15
LT3085
APPLICATIONS INFORMATION
from junction to ambient. This includes junction-to-case,
case-to-heat sink interface, heat sink resistance or circuit
board-to-ambient as the application dictates. Additional
heat sources nearby must also be considered.
For surface mount devices, heat sinking is accomplished
by using the heat spreading capabilities of the PC board
and its copper traces. Surface mount heat sinks and
plated through-holes can also be used to spread the heat
generated by power devices. Boards specified in thermal
resistance tables have no vias on plated through-holes
from topside to backside.
Junction-to-case thermal resistance is specified from
the IC junction to the bottom of the case directly below
the die. This is the lowest resistance path for heat flow.
Proper mounting is required to ensure the best possible
thermal flow from this area of the package to the heat
sinking material. Note that the Exposed Pad is electrically
connected to the output.
The following tables list thermal resistance for several
different copper areas given a fixed board size. All measurements were taken in still air on two-sided 1/16” FR-4
board with one ounce copper.
PCB layers, copper weight, board layout and thermal vias
affect the resultant thermal resistance. Although Tables
2 and 3 provide thermal resistance numbers for 2-layer
board with 1 ounce copper, modern multi-layer PCBs
provide better performance than found in these tables.
For example, a 4-layer, 1 ounce copper PCB board with
5 thermal vias from the DFN or MSOP exposed backside
pad to inner layers (connected to VOUT) achieves 40°C/W
thermal resistance. Demo circuit 1401A’s board layout
achieves this 40°C/W performance. This is approximately
a 45% improvement over the numbers shown in Tables
2 and 3.
Table 2. MSE Package, 8-Lead MSOP
COPPER AREA
TOPSIDE*
BACKSIDE
BOARD AREA
THERMAL RESISTANCE
(JUNCTION-TO-AMBIENT)
2500mm2
2500mm2
2500mm2
55°C/W
1000mm2
2500mm2
2500mm2
57°C/W
225mm2
2500mm2
2500mm2
60°C/W
100mm2
2500mm2
2500mm2
65°C/W
*Device is mounted on topside
Table 3. DCB Package, 6-Lead DFN
COPPER AREA
TOPSIDE*
BACKSIDE
BOARD AREA
THERMAL RESISTANCE
(JUNCTION-TO-AMBIENT)
2500mm2
2500mm2
2500mm2
68°C/W
1000mm2
2500mm2
2500mm2
70°C/W
225mm2
2500mm2
2500mm2
73°C/W
100mm2
2500mm2
2500mm2
78°C/W
*Device is mounted on topside
For future information on the thermal resistance and using thermal
information, refer to JEDEC standard JESD51, notably JESD51-12.
Calculating Junction Temperature
Example: Given an output voltage of 0.9V, a VCONTROL
voltage of 3.3V ±10%, an IN voltage of 1.5V ±5%, output
current range from 1mA to 0.5A and a maximum ambient temperature of 50°C, what will the maximum junction
temperature be for the DFN package on a 2500mm2 board
with topside copper area of 500mm2?
The power in the drive circuit equals:
PDRIVE = (VCONTROL – VOUT)(ICONTROL)
where ICONTROL is equal to IOUT/60. ICONTROL is a function
of output current. A curve of ICONTROL vs IOUT can be found
in the Typical Performance Characteristics curves.
3085fa
16
LT3085
APPLICATIONS INFORMATION
The power in the output transistor equals:
POUTPUT = (VIN – VOUT)(IOUT)
The total power equals:
PTOTAL = PDRIVE + POUTPUT
The current delivered to the SET pin is negligible and can
be ignored.
VCONTROL(MAX CONTINUOUS) = 3.630V (3.3V + 10%)
Reducing Power Dissipation
In some applications it may be necessary to reduce
the power dissipation in the LT3085 package without
sacrificing output current capability. Two techniques are
available. The first technique, illustrated in Figure 8, employs a resistor in series with the regulator’s input. The
voltage drop across RS decreases the LT3085’s IN-to-OUT
differential voltage and correspondingly decreases the
LT3085’s power dissipation.
VIN(MAX CONTINUOUS) = 1.575V (1.5V + 5%)
VOUT = 0.9V, IOUT = 0.5A, TA = 50°C
VIN
C1
VCONTROL
LT3085
RS
IN
VINa
Power dissipation under these conditions is equal to:
PDRIVE = (VCONTROL – VOUT)(ICONTROL)
I
0.5A
ICONTROL = OUT =
= 8.3mA
60
60
PDRIVE = (3.630V – 0.9V)(8.3mA) = 23mW
+
–
OUT
SET
RSET
VOUT
C2
3085 F08
POUTPUT = (VIN – VOUT)(IOUT)
POUTPUT = (1.575V – 0.9V)(0.5A) = 337mW
Figure 8. Reducing Power Dissipation Using a Series Resistor
Total Power Dissipation = 360mW
Junction Temperature will be equal to:
TJ = TA + PTOTAL • θJA (approximated using tables)
TJ = 50°C + 360mW • 73°C/W = 76°C
As an example, assume: VIN = VCONTROL = 5V, VOUT = 3.3V
and IOUT(MAX) = 0.5A. Use the formulas from the Calculating
Junction Temperature section previously discussed.
In this case, the junction temperature is below the maximum
rating, ensuring reliable operation.
3085fa
17
LT3085
APPLICATIONS INFORMATION
Without series resistor RS, power dissipation in the LT3085
equals:
⎛ 0.5A ⎞
+ ( 5V – 3.3V ) • 0.5A
PTOTAL = ( 5V – 3.3V ) • ⎜
⎝ 60 ⎟⎠
= 0.86W
If the voltage differential (VDIFF) across the NPN pass
transistor is chosen as 0.5V, then RS equals:
RS =
5V – 3.3V − 0.5V
= 2.4Ω
0.5A
Power dissipation in the LT3085 now equals:
⎛ 0.5A ⎞
PTOTAL = ( 5V – 3.3V ) • ⎜
+ ( 0.5V ) • 0.5A = 0.26W
⎝ 60 ⎟⎠
The LT3085’s power dissipation is now only 30% compared
to no series resistor. RS dissipates 0.6W of power. Choose
appropriate wattage resistors to handle and dissipate the
power properly.
The second technique for reducing power dissipation,
shown in Figure 9, uses a resistor in parallel with the
LT3085. This resistor provides a parallel path for current
flow, reducing the current flowing through the LT3085.
This technique works well if input voltage is reasonably
constant and output load current changes are small. This
technique also increases the maximum available output
current at the expense of minimum load requirements.
As an example, assume: VIN = VCONTROL = 5V, VIN(MAX) =
5.5V, VOUT = 3.3V, VOUT(MIN) = 3.2V, IOUT(MAX) = 0.5A and
IOUT(MIN) = 0.35A. Also, assuming that RP carries no more
than 90% of IOUT(MIN) = 630mA.
Calculating RP yields:
5.5V – 3.2V
= 7.30Ω
315mA
(5% Standard value = 7.Ω)
RP =
The maximum total power dissipation is (5.5V – 3.2V) •
0.5A = 1.2W. However the LT3085 supplies only:
0.5A –
5.5V – 3.2V
= 0.193A
7.5Ω
Therefore, the LT3085’s power dissipation is only:
PDIS = (5.5V – 3.2V) • 0.193A = 0.44W
RP dissipates 0.71W of power. As with the first technique,
choose appropriate wattage resistors to handle and dissipate the power properly. With this configuration, the
LT3085 supplies only 0.36A. Therefore, load current can
increase by 0.3A to 0.143A while keeping the LT3085 in
its normal operating range.
VIN
C1
VCONTROL
LT3085
IN
RP
+
–
OUT
SET
RSET
VOUT
C2
3085 F09
Figure 9. Reducing Power Dissipation Using a Parallel Resistor
3085fa
18
LT3085
TYPICAL APPLICATIONS
Higher Output Current
MJ4502
VIN
6V
50Ω
LT3085
IN
VCONTROL
+
+
–
100μF
1μF
VOUT
3.3V
5A
OUT
+
SET
4.7μF
100μF
332k
3085 TA02
Current Source
LT3085
IN
VIN
10V
VCONTROL
+
–
1μF
OUT 2Ω
0.5W
SET
IOUT
0A TO 0.5A
4.7μF
100k
3085 TA03
Power Oscillator
VIN
LT3085
IN
VCONTROL
+
–
VOUT
400Hz
4VACP-P
OUT
SET
10μF
6.3V, 150mA
LIGHT BULB #47
47nF
2.21k
4.7μF
8.45k
20Ω
499k
8.45k
220n
47nF
121Ω
3085 TA22
3085fa
19
LT3085
TYPICAL APPLICATIONS
Adding Shutdown
VIN
LT3085
IN
VIN
Low Dropout Voltage LED Driver
C1
LT3085
VCONTROL
+
–
3085 TA04
SET
ON OFF
IN
OUT
Q2*
VN2222LL
R1
100mA
D1
+
–
OUT
VOUT
Q1
VN2222LL
VCONTROL
SET
R1
24.9k
SHUTDOWN
R2
2.49Ω
3085 TA05
*Q2 INSURES ZERO OUTPUT
IN THE ABSENCE OF ANY
OUTPUT LOAD.
Using a Lower Value SET Resistor
IN
VIN
12V
LT3085
VCONTROL
C1
1μF
+
–
OUT
SET
R1
49.9k
1%
1mA
VOUT
0.5V TO 10V
R2
499Ω
1%
VOUT = 0.5V + 1mA • RSET
COUT
4.7μF
RSET
10k
3085 TA06
3085fa
20
LT3085
TYPICAL APPLICATIONS
Adding Soft-Start
LT3085
IN
VIN
4.8V to 28V
VCONTROL
C1
1μF
+
–
D1
1N4148
OUT
SET
C2
0.01μF
VOUT
3.3V
0.5A
COUT
4.7μF
R1
332k
3085 TA07
Coincident Tracking
LT3085
IN
VCONTROL
IN
LT3085
+
–
VCONTROL
VIN
7V TO 28V
IN
LT3085
+
–
VCONTROL
C1
1.5μF
OUT
SET
169k
OUT
+
–
OUT
SET
R1
249k
SET
R2
80.6k
C2
4.7μF
C3
4.7μF
VOUT2
3.3V
0.5A
VOUT3
5V
0.5A
4.7μF
3085 TA08
VOUT1
2.5V
0.5A
3085fa
21
LT3085
TYPICAL APPLICATIONS
Lab Supply
LT3085
IN
VIN
12V TO 18V
LT3085
IN
VCONTROL
VCONTROL
+
–
+
15μF
+
–
1Ω
OUT 0.25W
OUT
+
SET
50k
0A TO 0.5A
+
SET
15μF
VOUT
0V TO 10V
4.7μF
R4
1M
100μF
3085 TA09
High Voltage Regulator
6.1V
10k
VIN
50V
1N4148
IN
LT3085
BUZ11
VCONTROL
+
+
–
10μF
OUT
SET
RSET
2M
+
15μF
VOUT
0.5A
4.7μF
VOUT = 20V
VOUT = 10μA • RSET
3085 TA10
Ramp Generator
IN
VIN
5V
LT3085
VCONTROL
+
–
1μF
OUT
VOUT
SET
VN2222LL
1μF
VN2222LL
4.7μF
3085 TA12
3085fa
22
LT3085
TYPICAL APPLICATIONS
Reference Buffer
LT3085
IN
VIN
VCONTROL
+
–
OUT
VOUT*
C2
4.7μF
INPUT
SET
OUTPUT
LT1019
C1
1μF
GND
3085 TA11
*MIN LOAD 0.5mA
Ground Clamp
LT3085
IN
VIN
VEXT
VCONTROL
20Ω
+
–
OUT
1μF
SET
VOUT
1N4148
4.7μF
5k
3085 TA13
Boosting Fixed Output Regulators
IN
LT3085
VCONTROL
+
–
OUT
20mΩ
SET
20mΩ
5V
3.3VOUT
2A
LT1963-3.3
10μF
42Ω*
47μF
3085 TA20
33k
*4mV DROP ENSURES LT3085 IS
OFF WITH NO LOAD
MULTIPLE LT3085’S CAN BE USED
3085fa
23
LT3085
TYPICAL APPLICATIONS
Low Voltage, High Current Adjustable High Efficiency Regulator*
0.47μH
2.7V TO 5.5V†
100μF
×2
+
2.2MEG
100k
PVIN
SW
SVIN
ITH
LTC3414
10k
+
12.1k
RT
470pF
294k
PGOOD
100μF
×2
2N3906
LT3085
IN
VCONTROL
RUN/SS
+
–
VFB
1000pF
OUT
78.7k
SGND
PGND
20mΩ
SET
SYNC/MODE
124k
LT3085
IN
VCONTROL
+
–
*DIFFERENTIAL VOLTAGE ON LT3085
IS 0.6V SET BY THE VBE OF THE 2N3906 PNP.
OUT
†MAXIMUM OUTPUT VOLTAGE IS 1.5V
BELOW INPUT VOLTAGE
20mΩ
SET
0V TO 4V†
2A
LT3085
IN
VCONTROL
+
–
OUT
20mΩ
SET
LT3085
IN
VCONTROL
+
–
OUT
3085 TA18
SET
100k
20mΩ
+
100μF
3085fa
24
LT3085
TYPICAL APPLICATIONS
Adjustable High Efficiency Regulator*
CMDSH-4E
4.5V TO 25V†
VIN
10μF
1μF
100k
BOOST
LT3493
SHDN
0.1μF
10μH
0.1μF
MBRM140
LT3085
IN
SW
68μF
VCONTROL
TP0610L
GND
+
–
FB
OUT
10k
3085 TA19
SET
0V TO 10V†
0.5A
4.7μF
1MEG
*DIFFERENTIAL VOLTAGE ON LT3085
≈ 1.4V SET BY THE TPO610L P-CHANNEL THRESHOLD.
†MAXIMUM OUTPUT VOLTAGE IS 2V
BELOW INPUT VOLTAGE
10k
2 Terminal Current Source
CCOMP*
IN
LT3085
VCONTROL
+
–
OUT
R1
SET
100k
3085 TA21
IOUT =
1V
R1
*CCOMP
R1 ≤ 10Ω 10μF
R1 ≥ 10Ω 2.2μF
3085fa
25
LT3085
PACKAGE DESCRIPTION
DCB Package
6-Lead Plastic DFN (2mm × 3mm)
(Reference LTC DWG # 05-08-1698)
0.70 p0.05
3.55 p0.05
1.65 p0.05
(2 SIDES)
2.15 p0.05
PACKAGE
OUTLINE
0.25 p0.05
0.50 BSC
1.35 p0.05
(2 SIDES)
RECOMMENDED SOLDER PAD PITCH AND DIMENSIONS
R = 0.115
TYP
R = 0.05
TYP
2.00 p0.10
(2 SIDES)
3.00 p0.10
(2 SIDES)
0.40 p0.10
4
6
1.65 p0.10
(2 SIDES)
PIN 1 NOTCH
R0.20 OR 0.25
s 45° CHAMFER
PIN 1 BAR
TOP MARK
(SEE NOTE 6)
3
0.200 REF
0.75 p0.05
1
(DCB6) DFN 0405
0.25 p0.05
0.50 BSC
1.35 p0.10
(2 SIDES)
0.00 – 0.05
BOTTOM VIEW—EXPOSED PAD
NOTE:
1. DRAWING TO BE MADE A JEDEC PACKAGE OUTLINE M0-229 VARIATION OF (TBD)
2. DRAWING NOT TO SCALE
3. ALL DIMENSIONS ARE IN MILLIMETERS
4. DIMENSIONS OF EXPOSED PAD ON BOTTOM OF PACKAGE DO NOT INCLUDE
MOLD FLASH. MOLD FLASH, IF PRESENT, SHALL NOT EXCEED 0.15mm ON ANY SIDE
5. EXPOSED PAD SHALL BE SOLDER PLATED
6. SHADED AREA IS ONLY A REFERENCE FOR PIN 1 LOCATION ON THE
TOP AND BOTTOM OF PACKAGE
3085fa
26
LT3085
PACKAGE DESCRIPTION
MS8E Package
8-Lead Plastic MSOP
(Reference LTC DWG # 05-08-1662)
BOTTOM VIEW OF
EXPOSED PAD OPTION
2.06 p 0.102
(.081 p .004)
1
5.23
(.206)
MIN
1.83 p 0.102
(.072 p .004)
0.889 p 0.127
(.035 p .005)
2.794 p 0.102
(.110 p .004)
2.083 p 0.102 3.20 – 3.45
(.082 p .004) (.126 – .136)
8
0.42 p 0.038
(.0165 p .0015)
TYP
3.00 p 0.102
(.118 p .004)
(NOTE 3)
0.65
(.0256)
BSC
8
7 6 5
0.52
(.0205)
REF
RECOMMENDED SOLDER PAD LAYOUT
0.254
(.010)
3.00 p 0.102
(.118 p .004)
(NOTE 4)
4.90 p 0.152
(.193 p .006)
DETAIL “A”
0° – 6° TYP
GAUGE PLANE
1
0.53 p 0.152
(.021 p .006)
DETAIL “A”
2 3
4
1.10
(.043)
MAX
0.86
(.034)
REF
0.18
(.007)
SEATING
PLANE
0.22 – 0.38
(.009 – .015)
TYP
0.65
(.0256)
BSC
0.1016 p 0.0508
(.004 p .002)
MSOP (MS8E) 0307 REV D
NOTE:
1. DIMENSIONS IN MILLIMETER/(INCH)
2. DRAWING NOT TO SCALE
3. DIMENSION DOES NOT INCLUDE MOLD FLASH, PROTRUSIONS OR GATE BURRS.
MOLD FLASH, PROTRUSIONS OR GATE BURRS SHALL NOT EXCEED 0.152mm (.006") PER SIDE
4. DIMENSION DOES NOT INCLUDE INTERLEAD FLASH OR PROTRUSIONS.
INTERLEAD FLASH OR PROTRUSIONS SHALL NOT EXCEED 0.152mm (.006") PER SIDE
5. LEAD COPLANARITY (BOTTOM OF LEADS AFTER FORMING) SHALL BE 0.102mm (.004") MAX
3085fa
Information furnished by Linear Technology Corporation is believed to be accurate and reliable.
However, no responsibility is assumed for its use. Linear Technology Corporation makes no representation that the interconnection of its circuits as described herein will not infringe on existing patent rights.
27
LT3085
TYPICAL APPLICATION
Paralleling Regulators
IN
LT3080
VCONTROL
+
–
OUT 10mΩ
SET
IN
VIN
4.8V TO 36V
LT3085
VCONTROL
+
–
1μF
OUT 20mΩ
VOUT
3.3V
1.5A
SET
10μF
165k
3085 TA14
RELATED PARTS
PART NUMBER
DESCRIPTION
COMMENTS
1.5A Low Dropout Regulator
Fixed 2.85V, 3.3V, 3.6V, 5V and 12V Output
LDOs
LT1086
LT1763
500mA, Low Noise LDO
300mV Dropout Voltage, Low Noise = 20μVRMS, VIN: 1.8V to 20V, SO-8 Package
LT3021
500mA VLDO Regulator
LT3080
1.1A, Parallelable, Low Noise,
Low Dropout Linear Regulator
LT3080-1
Parallelable 1.1A Adjustable Single
Resistor Low Dropout Regulator
(with Internal Ballast R)
LT1963A
1.5A Low Noise, Fast Transient
Response LDO
1.1A Low Noise LDO
VIN: 0.9V to 10V, Dropout Voltage = 190mV, VADJ = 200mV, 5mm × 5mm DFN-16,
SO-8 Packages
300mV Dropout Voltage (2-Supply Operation), Low Noise = 40μVRMS, VIN: 1.2V to 36V,
VOUT : 0V to 35.7V, Current-Based Reference with 1-Resistor VOUT Set, Directly Parallelable
(No Op Amp Required), Stable with Ceramic Capacitors, TO-220, SOT-223, MSOP and
3mm × 3mm DFN Packages
300mV Dropout Voltage (2-Supply Operation), Low Noise = 40μVRMS, VIN: 1.2V to 36V,
VOUT : 0V to 35.7V, Current-Based Reference with 1-Resistor VOUT Set, Directly Parallelable
(No Op Amp Required), Stable with Ceramic Capacitors, TO-220, SOT-223, MSOP and
3mm × 3mm DFN Packages. LT3080-1 Version Has Integrated Ballast Resistor
340mV Dropout Voltage, Low Noise = 40μVRMS, VIN: 2.5V to 20V, TO-220, DD, SOT-223
and SO-8 Packages
290mV Dropout Voltage, Low Noise = 40μVRMS, VIN: 1.8V to 20V, VOUT : 1.2V to 19.5V,
Stable with Ceramic Caps TO-220, DDPak, MSOP and 3mm × 3mm DFN Packages
VIN: 1.14V to 3.5V (Boost Enabled), 1.14V to 5.5V (with External 5V), VDO = 0.1V,
IQ = 950μA, Stable with 10μF Ceramic Capacitors, 10-Lead MSOP and DFN Packages
LT1965
LTC®3026
1.5A Low Input Voltage VLDOTM
Regulator
Switching Regulators
High Voltage, 1.5A Step-Down
f = 200kHz, IQ = 100μA, TSSOP-16E Package
Switching Regulator
95% Efficiency, VIN: 2.25V to 5.5V, VOUT(MIN) = 0.8V, TSSOP Package
LTC3414
4A (IOUT), 4MHz Synchronous
Step-Down DC/DC Converter
LTC3406/LTC3406B 600mA (IOUT), 1.5MHz Synchronous 95% Efficiency, VIN: 2.5V to 5.5V, VOUT(MIN) = 0.6V, IQ = 20μA, ISD < 1μA,
Step-Down DC/DC Converter
ThinSOT TM Package
95% Efficiency, VIN: 2.5V to 5.5V, VOUT(MIN) = 0.8V, IQ = 60μA, ISD < 1μA, 10-Lead MS or
LTC3411
1.25A (IOUT), 4MHz Synchronous
Step-Down DC/DC Converter
DFN Packages
VLDO and ThinSOT are trademarks of Linear Technology Corporation.
LT1976
3085fa
28 Linear Technology Corporation
LT 1008 REV A • PRINTED IN USA
1630 McCarthy Blvd., Milpitas, CA 95035-7417
(408) 432-1900 ● FAX: (408) 434-0507
●
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© LINEAR TECHNOLOGY CORPORATION 2008