TI LM1203-N

LM1203
LM1203 RGB Video Amplifier System
Literature Number: SNOSC07A
LM1203 RGB Video Amplifier System
General Description
Features
The LM1203 is a wideband video amplifier system intended
for high resolution RGB color monitor applications. In addition to three matched video amplifiers, the LM1203 contains
three gated differential input black level clamp comparators
for brightness control and three matched attenuator circuits
for contrast control. Each video amplifier contains a gain set
or ‘‘Drive’’ node for setting maximum system gain (Av e 4
to 10) as well as providing trim capability. The LM1203 also
contains a voltage reference for the video inputs. For high
resolution monochrome monitor applications see the
LM1201 Video Amplifier System datasheet.
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Three wideband video amplifiers (70 MHz @ b3dB)
Inherently matched ( g 0.1 dB or 1.2%) attenuators for
contrast control
Three externally gated comparators for brightness control
Provisions for independent gain control (Drive) of each
video amplifier
Video input voltage reference
Low impedance output driver
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Block and Connection Diagram
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TL/H/9178 – 1
FIGURE 1
Order Number LM1203N
See NS Package Number NA28F
C1996 National Semiconductor Corporation
TL/H/9178
RRD-B30M56/Printed in U. S. A.
LM1203 RGB Video Amplifier System
January 1996
Absolute Maximum Ratings
Storage Temperature Range, TSTG
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales
Office/Distributors for availability and specifications.
b 65§ C to a 150§ C
Lead Temperature, (Soldering, 10 sec.)
265§ C
ESD susceptibility
1 kV
Human body model: 100 pF discharged through a 1.5 kX
resistor
Supply Voltage, VCC Pins 1, 13, 23, 28
(Note 1)
13.5V
Voltage at Any Input Pin, VIN
VCC t VIN t GND
Video Output Current, I16, 20 or 25
28 mA
2.5W
Power Dissipation, PD
(Above 25§ C) Derate Based on iJA and TJ
Thermal Resistance, iJA
50§ C/W
Junction Temperature, TJ
150§ C
Operating Ratings (Note 9)
0§ C to 70§ C
10.8V s VCC s 13.2V
Temperature Range
Supply Voltage (VCC)
Electrical Characteristics See Test Circuit (Figure 2) , TA e 25§ C; VCC1 e VCC2 e 12V
DC Static Tests S17, 21, 26 Open; V12 e 6V; V14 e 0V; V15 e 2.0V unless otherwise stated
Conditions
Is
Supply Current
V11
Video Input Reference Voltage
Typ
VCC 1 only
73
Design
Limit (Note 3)
90.0
2.4
lb
Video Input Bias Current
Any One Amplifier
V14 l
Clamp Gate Low Input Voltage
Clamp Comparators On
V14 h
Clamp Gate High Input Voltage
Clamp Comparators Off
I14 l
Clamp Gate Low Input Current
V14 e 0V
Units
(Limits)
mA(max)
2.2
V(min)
2.6
V(max)
5.0
20
mA(max)
1.2
0.8
V(max)
1.6
2.0
V(min)
b 0.5
b 5.0
mA(max)
1
mA(max)
I14 h
Clamp Gate High Input Current
lclamp a
Clamp Cap Charge Current
V5, 8 or 10 e 0V
0.005
850
500
mA(min)
lclampb
Clamp Cap Discharge Current
V5, 8 or 10 e 5V
b 850
b 500
mA(min)
Vol
Video Output Low Voltage
V5, 8 or 10 e 0V
0.9
1.25
V(max)
Voh
Video Output High Voltage
V5, 8 or 10 e 5V
8.9
8.2
V(min)
DVo(2V)
Video Output Offset Voltage
Between Any Two Amplifiers
V15 e 2V
g 0.5
g 50
mV(max)
DVo(4V)
Video Output Offset Voltage
Between Any Two Amplifiers
V15 e 4V
g 0.5
g 50
mV(max)
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V14 e 12V
Tested
Limit (Note 2)
e
Parameter
et
Label
AC Dynamic Tests S17, 21, 26 Closed; V14 e 0V; V15 e 4V; unless otherwise stated
Parameter
Conditions
O
Symbol
Av max
Video Amplifier Gain
V12 e 12V, VIN e 560 mVp-p
DAv 5V
Typ
Tested
Limit (Note 2)
6.0
4.5
Design
Limit (Note 3)
Units
(Limits)
V/V(min)
Attenuation
@
5V
Ref: Av max, V12 e 5V
b 10
DAv 2V
Attenuation
@
2V
Ref: Av max, V12 e 2V
b 40
dB
Av match
Absolute gain match
V12 e 12V (Note 5)
g 0.5
dB
DAv track1
Gain change between amplifiers
V12 e 5V (Notes 5, 8)
g 0.1
g 0.5
dB(max)
DAv track2
Gain change between amplifiers
V12 e 2V (Notes 5, 8)
g 0.3
g 0.7
dB(max)
THD
Video Amplifier Distortion
V12 e 3V, VO e 1 Vp-p
0.5
%
f (b3 dB)
Video Amplifier Bandwidth
(Notes 4, 6)
V12 e 12V,
VO e 100 mVrms
70
MHz
tr
Output Rise Time (Note 4)
VO e 4 Vp-p
5
ns
tf
Output Fall Time (Note 4)
VO e 4 Vp-p
7
ns
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@
Av max
2
dB
AC Dynamic Tests S17, 21, 26 Closed; V14 e 0V; V15 e 4V; unless otherwise stated (Continued)
Symbol
Parameter
Conditions
Vsep
10 kHz
Video Amplifier 10 kHz Isolation
V12 e 12V (Note 7)
Vsep
10 MHz
Video Amplifier 10 MHz Isolation
V12 e 12V (Notes 4, 7)
Typ
Tested
Limit (Note 2)
Design
Limit (Note 3)
Units
b 65
dB
b 46
dB
Note 1: VCC supply pins 1, 13, 23, 28 must be externally wired together to prevent internal damage during VCC power on/off cycles.
Note 2: These parameters are guaranteed and 100% production tested.
Note 3: Design limits are guaranteed (but not 100% production tested). These limits are not used to calculate outgoing quality levels.
Note 4: When measuring video amplifier bandwidth or pulse rise and fall times, a double sided full ground plane printed circuit board without socket is recommended. Video Amplifier 10 MHz isolation test also requires this printed circuit board.
Note 5: Measure gain difference between any two amplifiers. VIN e 1 Vp-p.
Note 6: Adjust input frequency from 10 kHz (Avmax ref level) to the b 3 dB corner frequency (f b 3 dB).
Note 7: Measure output levels of the other two undriven amplifiers relative to driven amplifier to determine channel separation. Terminate the undriven amplifier
inputs to simulate generator loading. Repeat test at fIN e 10 MHz for Vsep e 10 MHz.
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Note 8: DAv track is a measure of the ability of any two amplifiers to track each other and quantifies the matching of the three attenuators. It is the difference in
gain change between any two amplifiers with the Contrast Voltage V12 at either 5V or 2V measured relative to an Av max condition V12 e 12V. For example, at
Av max the three amplifiers gains might be 17.4 dB, 16.9 dB, and 16.4 dB and change to 7.3 dB, 6.9 dB, and 6.5 dB respectively for V12 e 5V. This yields the
measured typical g 0.1 dB channel tracking.
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Note 9: Operating Ratings indicate conditions for which the device is functional. See Electrical Specifications for guaranteed performance limits.
*Peaking capacitors. See Frequency Response
using various peaking cups graph on next page.
TL/H/9178 – 2
FIGURE 2. LM1203 Test Circuit
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Typical Performance Characteristics
Contrast vs Frequency
Crosstalk vs Frequency
TL/H/9178–11
TL/H/9178 – 12
Attenuation vs Contrast Voltage
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Frequency Response Using
Various Peaking Caps
TL/H/9178–13
Pulse Response
Rise & Fall Times
Vert. e 1V/Div.
Horiz. e 10 ns/Div.
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TL/H/9178 – 15
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TL/H/9178 – 14
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FIGURE 3. LM1203 Typical Application
* 30X resistors are added to the input pins for protection against current surges coming through the 10 mF input capacitors. By increasing these resistors to well
over 100X the rise and fall times of the LM1203 can be increased for EMI considerations.
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Applications Information
Figure 4 shows the block diagram of a typical analog RGB
color monitor. The RGB monitor is used with CAD/CAM
work stations, PC’s, arcade games and in a wide range of
other applications that benefit from the use of color display
terminals. The RGB color monitor characteristics may differ
in such ways as sweep rates, screen size, CRT color trio
spacing (dot pitch), or in video amplifier bandwidths but will
still be generally configured as shown in Figure 4 . Separate
horizontal and vertical sync signals may be required or they
may be contained in the green video input signal. The video
input signals are usually supplied by coax cable which is
terminated in 75X at the monitor input and internally ac cou-
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pled to the video amplifiers. These input signals are approximately 1 volt peak to peak in amplitude and at the input of
the high voltage video section, approximately 6V peak to
peak. At the cathode of the CRT the video signals can be as
high as 60V peak to peak. One important requirement of the
three video amplifiers is that they match and track each
other over the contrast and brightness control range. The
Figure 4 block labeled ‘‘VIDEO AMPLIFICATION WITH
GAIN AND DC CONTROL’’ describes the function of the
LM1203 which contains the three matched video amplifiers,
contrast control and brightness control.
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FIGURE 4. Typical RGB Color Monitor Block Diagram
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TL/H/9178 – 4
Circuit Description
Figure 5 is a block diagram of one of the video amplifiers
along with the contrast and brightness controls. The contrast control is a dc-operated attenuator which varies the ac
gain of all three amplifiers simultaneously while not introducing any signal distortions or tracking errors. The brightness
control function requires a ‘‘sample and hold’’ circuit (black
level clamp) which holds the dc bias of the video amplifiers
and CRT cathodes constant during the black level reference
portion of the video waveform. The clamp comparator,
when gated on during this reference period, will charge or
discharge the clamp capacitor until the plus input of the
clamp comparator matches that of the minus input voltage
which was set by the brightness control.
Figure 6 is a simplified schematic of one of the three video
amplifiers along with the recommended external components. The IC pin numbers are circled with all external components shown outside of the dashed line. The video input
is applied to pin 6 via the 10 mF coupling capacitor. DC bias
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to the video input is through the 10 kX resistor which is
connected to the 2.4V reference at pin 11. The low frequency roll-off of the amplifier is set by these two components.
Transistor Q1 buffers the video signal to the base of Q2.
The Q2 collector current is then directed to the VCC 1 supply directly or through the 1k load resistor depending upon
the differential DC voltage at the bases of Q3 and Q4. The
Q3 and Q4 differential base voltage is determined by the
contrast control circuit which is described below. RF decoupling capacitors are required at pins 2 and 3 to insure high
frequency isolation between the three video amplifiers
which share these common connections. The black level dc
voltage at the collector of Q4 is maintained by Q5 and Q6
which are part of the black level clamp circuit also described
below. The video signal appearing at the collector of Q4 is
then buffered by Q7 and level shifted down by Z1 and Q8 to
the base of Q9 which will then provide additional system
gain.
TL/H/9178 – 5
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FIGURE 5. Block Diagram of LM1203 Video Amplifier with Contrast and Black Level Control
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FIGURE 6. Simplified LM1203 Video Amplifier Section with Recommended External Components
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TL/H/9178 – 6
Circuit Description (Continued)
Circuit Description (Continued)
10 mA. The system gain will also increase slightly because
less signal will be lost across the internal 40X resistor. Precautions must be taken to prevent the video output pin from
going below ground because IC substrate currents may
cause erratic operation. The collector currents from the video output transistors are returned to the power supply at
VCC 2 pin 23. When making power dissipation calculations
note that the data sheet specifies only the VCC 1 supply
current at 12V. The IC power dissipation contribution of
VCC 2 is dependent upon the video output emitter pull down
load.
In applications that require video amplifier shut down because of fault conditions detected by monitor protection circuits, pin 11 and the wiper arms of the contrast and brightness controls can be grounded without harming the IC. This
assumes some series resistance between the top of the
control pots and VCC.
Figure 7 shows the internal construction of the pin 11 2.4V
reference circuit which is used to provide temperature and
supply voltage tracking compensation for the video amplifier
inputs. The value of the external DC biasing resistors should
not be larger than 10 kX because minor differences in input
bias currents to the individual video amplifiers may cause
offsets in gain.
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The ‘‘Drive’’ pin will allow the user to trim the Q9 gain of
each amplifier to correct for differences in the CRT and high
voltage cathode driver gain stages. A small capacitor
(33 pF) at this pin will extend the high frequency gain of the
video amplifier by compensating for some of the internal
high frequency roll off. To use this capacitor and still provide
variable gain adjustment, the 51X and series 100X pot
should be used with the red and green drive pins. The 91X
resistor used with the blue drive pin will set the system gain
to approximately 6.2 and allow adjustment of the red and
green gains to 6.2 plus or minus 25%. The video signal at
the collector of Q9 is buffered and level shifted down by
Q10 and Q11 to the base of the output emitter follower Q12.
Between the emitter of Q12 and the video output pin is a
40X resistor which was included to prevent spurious oscillations when driving capacitive loads. An external emitter resistor must be added between the video output pin and
ground. The value of this resistor should not be less than
390X or package power limitations may be exceeded when
worst case (high supply, max supply current, max temp) calculations are made. If negative going pulse slewing is a
problem because of high capacitive loads (l10 pF), a more
efficient method of emitter pull down would be to connect a
suitable resistor to a negative supply voltage. This has the
effect of a current source pull down when the minus supply
voltage is b12V and the emitter current is approximately
TL/H/9178 – 7
FIGURE 7. LM1203 Video Input Voltage Reference and Contrast Control Circuits
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Circuit Description (Continued)
Figure 7 also shows how the contrast control circuit is configured. Resistors R23, 24, diodes D3, 4 and transistor Q13
are used to establish a low impedance zero TC half supply
voltage reference at the base of Q14. The differential amplifier formed by Q15, 16 and feedback transistor Q17 along
with resistors R27, 28 establish a diferential base voltage
for Q3 and Q4 in Figure 6 . When externally adding or subtracting current from the collector of Q16, a new differential
voltage is generated that reflects the change in the ratio of
currents in Q15 and Q16. To provide voltage control of the
Q16 current, resistor R29 is added between the Q16 collector and pin 12. A capacitor should be added from pin 12 to
ground to prevent noise from the contrast control pot from
entering the IC.
Figure 8 is a simplified schematic of the clamp gate and
clamp comparator sections of the LM1203. The clamp gate
circuit consists of a PNP input buffer transistor (Q18), a PNP
emitter coupled pair referenced on one side to 2.1V (Q19,
20) and an output switch (Q21). When the clamp gate input
at pin 14 is high (l1.5V) the Q21 switch is on and shunts
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the I1 850 mA current to ground. When pin 14 is low ( k1.3V)
the Q21 switch is off and the I1 850 mA current source is
mirrored or ‘‘turned around’’ by reference diode D5 and Q26
to provide a 850 mA current source for the clamp comparator(s). The inputs to the comparator are similar to the clamp
gate input except that an NPN emitter coupled pair is used
to control the current which will charge or discharge the
clamp capacitors at pins 5, 8, or 10. PNP transistors are
used at the inputs because they offer a number of advantages over NPNs. PNPs will operate with base voltages at or
near ground and will usually have a greater reverse emitter
base breakdown voltage (BVebo). Because the differential
input voltage to the clamp comparator during the video scan
period could be greater than the BVebo of NPN transistors a
resistor (R34) with a value one half that of R33 or R35 is
connected between the bases of Q23 and Q27. This resistor will limit the maximum differential input to Q24, 25 to
approximately 350 mV. The clamp comparator common
mode range is from ground to approximately 9V and the
maximum differential input voltage is VCC and ground.
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FIGURE 8. Simplified Schematic of LM1203 Clamp Gate and Clamp Comparator Circuits
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TL/H/9178 – 8
Additional Applications of the LM1203
Figure 9 shows how the LM1203 can be set up as a video
buffer which could be used in low cost video switcher applications. Pin 14 is tied high to turn off the clamp comparators. The comparator input pins should be grounded as
shown. Sync tip (black level if sync is not included) clamping
is provided by diodes at the amplifier inputs. Note that the
clamp cap pins are tied to the Pin 11 2.4V reference. This
was done, along with the choice of 200X for the drive pin
resistor, to establish an optimum DC output voltage. The
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contrast control (Pin 12) will provide the necessary gain or
attenuation required for channel balancing. Changing the
contrast control setting will cause minor DC shifts at the
amplifier output which will not be objectionable as the output is AC coupled to the load. The dual NPN/PNP emitter
follower will provide a low impedance output drive to the AC
coupled 75X output impedance setting resistor. The dual
500 mF capacitors will set the low frequency response to
approximately 4 Hz.
TL/H/9178 – 9
FIGURE 9. RGB Video Buffer with Diode Sync Tip Clamps and 75X Cable Driver
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Additional Applications of the LM1203 (Continued)
Figure 10 shows the configuration for a three channel high
frequency amplifier with non gated DC feedback. Pin 14 is
tied low to turn on the clamp comparators (feedback amplifiers). The inverting inputs (Pins 17, 21, 26) are connected to
the amplifier outputs from a low pass filter. Additional low
frequency filtering is provided by the clamp caps. The drive
resistors can be made variable or fixed at values between 0
and 300X. Maximum output swings are achieved when the
DC output is set to approximately 4V. The high frequency
response will be dependent upon external peaking at the
drive pins.
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When diode D4 at Pin 11 is switched to ground the input
video signals will be DC shifted down and clamped at a
voltage near ground (approximately 250 mV). This will disable the video amplifiers and force the output DC level low.
The DC outputs from other similarly configured LM1203s
could overide this lower DC level and provide the output
signals to the 75X cable drivers. In this case any additional
LM1203s would share the same 390X output resistor. The
maximum DC plus peak white output voltage should not be
allowed to exceed 7V because the ‘‘off’’ amplifier output
stage could suffer internal zener damage. See Figure 3 and
text for a description of the internal configuration of the video amplifier.
TL/H/9178 – 10
FIGURE 10. Three Channel High Frequency Amplifier with Non-gated DC Feedback (Non-video Applications)
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FIGURE 11. LM1203/LM1881 Application Circuit for PC Board
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PC Board with Components
TL/H/9178 – 17
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Lit. Ý 107315
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LM1203 RGB Video Amplifier System
Physical Dimensions inches (millimeters) unless otherwise noted
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28-Lead Molded Dual-In-Line Package (N)
Order Number LM1203N
NS Package Number NA28F
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