Datasheet - International Rectifier

April 26, 2011
IRS2336(D)
IRS23364D
HIGH VOLTAGE 3 PHASE GATE DRIVER IC
Features
•
•
•
•
•
•
•
•
•
•
•
•
•
•
•
•
•
•
•
Drives up to six IGBT/MOSFET power devices
Gate drive supplies up to 20 V per channel
Integrated bootstrap functionality (IRS2336(4)D)
Over-current protection
Over-temperature shutdown input
Advanced input filter
Integrated deadtime protection
Shoot-through (cross-conduction) protection
Undervoltage lockout for VCC & VBS
Enable/disable input and fault reporting
Adjustable fault clear timing
Separate logic and power grounds
3.3 V input logic compatible
Tolerant to negative transient voltage
Designed for use with bootstrap power supplies
Matched propagation delays for all channels
-40°C to 125°C operating range
RoHS compliant
Lead-Free
Product Summary
Topology
3 Phase
VOFFSET
≤ 600 V
IRS2336(D)
10 V – 20 V
IRS23364D
11.5 V – 20 V
VOUT
Io+ & I o- (typical)
200 mA & 350 mA
tON & tOFF (typical)
530 ns & 530 ns
Deadtime (typical)
275 ns
Package Options
28-Lead PDIP
28-Lead SOIC Wide Body
Typical Applications
•
•
•
•
Appliance motor drives
Servo drives
Micro inverter drives
General purpose three phase inverters
48-Lead MLPQ7X7
(without 14 leads)
44-Lead PLCC
(without 12 leads)
Typical Connection Diagram
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© 2009 International Rectifier
IRS2336x(D) Family
Table of Contents
Page
Description
3
Feature Comparison
3
Simplified Block Diagram
4
Typical Application Diagram
4
Qualification Information
5
Absolute Maximum Ratings
6
Recommended Operating Conditions
7
Static Electrical Characteristics
8-9
Dynamic Electrical Characteristics
10
Functional Block Diagram
11-12
Input/Output Pin Equivalent Circuit Diagram
13-14
Lead Definitions
15-16
Lead Assignments
17
Application Information and Additional Details
18-35
Parameter Temperature Trends
36-39
Package Details
40-43
Tape and Reel Details
44-46
Part Marking Information
47
Ordering Information
48
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© 2009 International Rectifier
2
IRS2336x(D) Family
Description
The IRS2336xD are high voltage, high speed, power MOSFET and IGBT gate drivers with three high-side and
three low-side referenced output channels for 3-phase applications. This IC is designed to be used with low-cost
bootstrap power supplies; the bootstrap diode functionality has been integrated into this device to reduce the
component count and the PCB size. Proprietary HVIC and latch immune CMOS technologies have been
implemented in a rugged monolithic structure. The floating logic input is compatible with standard CMOS or
LSTTL outputs (down to 3.3 V logic). A current trip function which terminates all six outputs can be derived from
an external current sense resistor. Enable functionality is available to terminate all six outputs simultaneously.
An open-drain FAULT signal is provided to indicate that a fault (e.g., over-current, over-temperature, or
undervoltage shutdown event) has occurred. Fault conditions are cleared automatically after a delay
programmed externally via an RC network connected to the RCIN input. The output drivers feature a high-pulse
current buffer stage designed for minimum driver cross-conduction. Shoot-through protection circuitry and a
minimum deadtime circuitry have been integrated into this IC. Propagation delays are matched to simplify the
HVIC’s use in high frequency applications. The floating channels can be used to drive N-channel power
MOSFETs or IGBTs in the high-side configuration, which operate up to 600 V.
Feature Comparison: IRS2336xD Family
Part Number
Input Logic
UVLO
VIT,TH
tON, tOFF
VOUT
IRS2336(D)
HIN/N, LIN/N
8.9 V/ 8.2 V
0.46 V
530 ns, 530 ns
10 V – 20 V
IRS23364D
HIN, LIN
11.1 V/ 10.9 V
0.46 V
530 ns, 530 ns
11.5 V – 20 V
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© 2009 International Rectifier
3
IRS2336x(D) Family
Simplified Block Diagram
Typical Application Diagram
DC Bus ≤ 600 V
+
To
Load
Input
Voltage
-
IRS2336xD
VCC
Control Inputs,
EN, & FAULT
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© 2009 International Rectifier
4
IRS2336x(D) Family
†
Qualification Information
††
Industrial
Qualification Level
Comments: This family of ICs has passed JEDEC’s
Industrial qualification. IR’s Consumer qualification level is
granted by extension of the higher Industrial level.
†††
SOIC28W
MSL3 , 260°C
(per IPC/JEDEC J-STD-020)
MLPQ7X7
†††
Moisture Sensitivity Level
PLCC44
MSL3 , 245°C
(per IPC/JEDEC J-STD-020)
Not applicable
(non-surface mount package style)
Class 1C
(per JEDEC standard JESD22-A114)
Class B
(per EIA/JEDEC standard EIA/JESD22-A115)
Class IV
(per JEDEC standard JESD22-C101)
Class I, Level A
(per JESD78)
Yes
PDIP28
Human Body Model
ESD
Machine Model
Charged Device Model
††††
IC Latch-Up Test
RoHS Compliant
†
††
Qualification standards can be found at International Rectifier’s web site http://www.irf.com/
Higher qualification ratings may be available should the user have such requirements. Please contact your
International Rectifier sales representative for further information.
†††
Higher MSL ratings may be available for the specific package types listed here. Please contact your
International Rectifier sales representative for further information.
†††† Charged Device Model classification is based on SOIC28W package.
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© 2009 International Rectifier
5
IRS2336x(D) Family
Absolute Maximum Ratings
Absolute maximum ratings indicate sustained limits beyond which damage to the device may occur. All voltage
parameters are absolute voltages referenced to VSS unless otherwise stated in the table. The thermal resistance and
power dissipation ratings are measured under board mounted and still air conditions. Voltage clamps are included
between VCC & COM (25 V), VCC & VSS (20 V), and VB & VS (20 V).
Symbol
VCC
VIN
VRCIN
VB
VS
VHO
VLO
VFLT
COM
dVS/dt
PW HIN
PD
RthJA
TJ
TS
TL
†
Definition
Low side supply voltage
IRS2336(D)
IRS23364D
Logic input voltage (HIN, LIN, ITRIP, EN)
RCIN input voltage
High-side floating well supply voltage
High-side floating well supply return voltage
Floating gate drive output voltage
Low-side output voltage
Fault output voltage
Power ground
Allowable VS offset supply transient relative to VSS
High-side input pulse width
28-Lead PDIP
28-Lead
SOICW
Package power dissipation @ TA ≤+25ºC
44-Lead PLCC
48-Lead
MLPQ7X7
28-Lead PDIP
28-Lead
SOICW
Thermal resistance, junction to ambient
44-Lead PLCC
48-Lead
MLPQ7X7
Junction temperature
Storage temperature
Lead temperature (soldering, 10 seconds)
Min
-0.3
VSS-0.3
VSS-0.3
VSS-0.3
-0.3
†
VB-20
VS-0.3
COM-0.3
VSS-0.3
VCC-25
—
500
—
Max
†
20
VSS+5.2
VCC+0.3
VCC+0.3
†
620
VB+0.3
VB+0.3
VCC+0.3
VCC+0.3
VCC+0.3
50
—
1.5
—
1.6
—
2.0
—
2.0
—
83
—
78
—
63
—
63
—
-55
—
150
150
300
Units
V
V/ns
ns
W
ºC/W
ºC
All supplies are tested at 25 V. An internal 20 V clamp exists for each supply.
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© 2009 International Rectifier
6
IRS2336x(D) Family
Recommended Operating Conditions
For proper operation, the device should be used within the recommended conditions. All voltage parameters are
absolute voltages referenced to VSS unless otherwise stated in the table. The offset rating is tested with supplies of
(VCC-COM) = (VB-VS) = 15 V.
Symbol
VCC
Low-side supply voltage
VIN
HIN, LIN, & EN input voltage
VB
High-side floating well supply voltage
VS
VS(t)
VHO
VLO
COM
VFLT
VRCIN
VITRIP
TA
†
††
Definition
IRS2336(D)
IRS23364D
IRS2336(D)
IRS23364D
IRS2336(D)
IRS23364D
†
High-side floating well supply offset voltage
††
Transient high-side floating supply voltage
Floating gate drive output voltage
Low-side output voltage
Power ground
FAULT output voltage
RCIN input voltage
ITRIP input voltage
Ambient temperature
Min
10
11.5
VSS
VS+10
VS+11.5
COM-8
-50
Vs
COM
-5
VSS
VSS
VSS
-40
Max
20
20
VSS+5
VCC
VS+20
VS+20
600
600
VB
VCC
5
VCC
VCC
VSS+5
125
Units
V
ºC
Logic operation for VS of –8 V to 600 V. Logic state held for VS of –8 V to –VBS. Please refer to Design Tip
DT97-3 for more details.
Operational for transient negative VS of VSS - 50 V with a 50 ns pulse width. Guaranteed by design. Refer to
the Application Information section of this datasheet for more details.
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© 2009 International Rectifier
7
IRS2336x(D) Family
Static Electrical Characteristics
o
(VCC-COM) = (VB-VS) = 15 V. TA = 25 C unless otherwise specified. The VIN and IIN parameters are referenced to VSS
and are applicable to all six channels. The VO and IO parameters are referenced to respective VS and COM and are
applicable to the respective output leads HO or LO. The VCCUV parameters are referenced to VSS. The VBSUV
parameters are referenced to VS.
Symbol
Definition
VCC supply undervoltage positive
IRS2336(D)
IRS23364D
going threshold
VCC supply undervoltage negative IRS2336(D)
IRS23364D
going threshold
IRS2336(D)
VCC supply undervoltage
hysteresis
IRS23364D
VBS supply undervoltage positive
IRS2336(D)
IRS23364D
going threshold
VBS supply undervoltage negative
IRS2336(D)
IRS23364D
going threshold
IRS2336(D)
VBS supply undervoltage
hysteresis
IRS23364D
High-side floating well offset supply leakage
Quiescent VBS supply current
IRS2336
Quiescent VCC supply current
IR2336(4)D
High level output voltage drop, VBIAS-VO
Low level output voltage drop, VO
Min
8
10.4
7.4
10.2
0.3
—
8
10.4
7.4
10.2
0.3
—
—
—
—
—
—
—
Typ
8.9
11.1
8.2
10.9
0.7
0.2
8.9
11.1
8.2
10.9
0.7
0.2
—
70
2
3
0.90
0.40
Max
9.8
11.6
9
11.4
—
—
9.8
11.6
9
11.4
—
—
50
120
3
4
1.4
0.6
Io+
Output high short circuit pulsed current
120
200
—
Io-
Output low short circuit pulsed current
250
350
—
2.5
—
—
—
—
0.8
IRS2336(D)
4.8
5.2
5.65
IIN = 100 µA
IRS2336(D)
IRS23364D
IRS2336(D)
IRS23364D
IRS2336(D)
IRS23364D
IRS2336(D)
IRS23364D
—
—
—
—
—
—
—
—
—
—
—
—
150
120
110
—
150
120
110
—
8
3
—
50
200
165
150
1
200
165
150
1
—
—
1
100
VIN = 0 V
VCCUV+
VCCUVVCCUVHY
VBSUV+
VBSUVVBSUVHY
ILK
IQBS
IQCC
VOH
VOL
VIH
VIL
VIN,CLAMP
IHIN+
Logic “0” input voltage
Logic “1” input voltage
Logic “1” input voltage
Logic “0” input voltage
Input voltage clamp
(HIN, LIN, ITRIP and EN)
Input bias current (HO = High)
IHIN-
Input bias current (HO = Low)
ILIN+
Input bias current (LO = High)
ILIN-
Input bias current (LO = Low)
VRCIN,TH
VRCIN,HY
IRCIN
RON,RCIN
RCIN positive going threshold
RCIN hysteresis
RCIN input bias current
RCIN low on resistance
Units
Test Conditions
V
NA
µA
mA
VB = VS = 600 V
All inputs are in the
off state
V
V
IO= 20 mA
mA
VO=0 V,VIN=0 V,
PW ≤ 10 µs
VO=15 V,VIN=5 V,
PW ≤ 10 µs
NA
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V
VIN = 4 V
µA
VIN = 0 V
VIN = 4 V
VIN = 0 V
V
NA
µA
Ω
VRCIN = 0 V or 15 V
I = 1.5 mA
© 2009 International Rectifier
8
IRS2336x(D) Family
Static Electrical Characteristics (continued)
Symbol
VIT,TH+
Definition
ITRIP positive going threshold
VIT,TH-
ITRIP negative going threshold
Min
0.37
—
Typ
0.46
0.4
Max
0.55
—
—
0.07
—
5
5
—
20
40
1
VIT,HYS
ITRIP hysteresis
IITRIP+
“High” ITRIP input bias current
IITRIP-
“Low” ITRIP input bias current
—
—
—
VEN,TH+
Enable positive going threshold
—
—
2.5
VEN,TH-
Enable negative going threshold
—
IEN+
“High” enable input bias current
IEN-
“Low” enable input bias current
5
120
—
—
20
165
1
FAULT low on resistance
0.8
—
—
—
—
50
100
Internal BS diode Ron
—
200
—
RON,FLT
RBS
IRS2336(D)
IRS23364D
IRS2336(D)
IRS23364D
(IRS2336(4)D)
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Units
Test Conditions
V
NA
µA
VIN = 4 V
VIN = 0 V
V
µA
NA
VIN = 4 V
VIN = 0 V
Ω
I = 1.5 mA
NA
© 2009 International Rectifier
9
IRS2336x(D) Family
Dynamic Electrical Characteristics
o
VCC= VB = 15 V, VS = VSS = COM, TA = 25 C, and CL = 1000 pF unless otherwise specified.
Symbol
tON
tOFF
tR
tF
tFIL,IN
tEN
tFILTER,EN
tFLTCLR
tITRIP
tBL
tFLT
DT
MDT
Definition
Turn-on propagation delay
Turn-off propagation delay
Turn-on rise time
Turn-off fall time
†
Input filter time
(HIN, LIN, ITRIP)
Enable low to output shutdown
propagation delay
Enable input filter time
FAULT clear time
RCIN: R = 2 MΩ, C = 1 nF
ITRIP to output shutdown
propagation delay
ITRIP blanking time
ITRIP to FAULT propagation delay
Deadtime
††
DT matching
MT
Delay matching time (tON, tOFF)
PM
Pulse width distortion
†††
††
Min
400
400
—
—
Typ
530
530
125
50
Max
750
750
190
75
Units
Test Conditions
200
350
510
350
460
650
VIN, VEN = 0 V or 5 V
100
200
—
1.3
1.65
2
NA
VIN = 0 V or 5 V
VITRIP = 0 V
500
750
1200
VITRIP = 5 V
—
400
190
—
400
600
275
—
—
950
420
60
—
—
50
—
—
75
VIN = 0 V or 5 V
VITRIP = 5 V
VIN = 0 V & 5 V without
external deadtime
VIN = 0 V & 5 V with external
deadtime larger than DT
PW input=10 µs
VIN = 0 V & 5 V
ns
ms
ns
†
The minimum width of the input pulse is recommended to exceed 500 ns to ensure the filtering time of the
input filter is exceeded.
†† This parameter applies to all of the channels. Please see the application section for more details.
††† PM is defined as PW IN - PW OUT.
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© 2009 International Rectifier
10
IRS2336x(D) Family
Functional Block Diagram: IRS2336(D)
Note: IRS2336 is without the “Integrated BootFET”
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© 2009 International Rectifier
11
IRS2336x(D) Family
Functional Block Diagram: IRS23364D
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© 2009 International Rectifier
12
IRS2336x(D) Family
Input/Output Pin Equivalent Circuit Diagrams: IRS2336(D)
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© 2009 International Rectifier
13
IRS2336x(D) Family
Input/Output Pin Equivalent Circuit Diagrams: IRS23364D
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© 2009 International Rectifier
14
IRS2336x(D) Family
Lead Definitions: IRS2336(D)
Symbol
Description
VCC
VSS
VB1
VB2
VB3
VS1
VS2
VS3
HIN1/N
HIN2/N
HIN3/N
LIN1/N
LIN2/N
LIN3/N
HO1
HO2
HO3
LO1
LO2
LO3
COM
Low-side supply voltage
Logic ground
High-side gate drive floating supply (phase 1)
High-side gate drive floating supply (phase 2)
High-side gate drive floating supply (phase 3)
High voltage floating supply return (phase 1)
High voltage floating supply return (phase 2)
High voltage floating supply return (phase 3)
Logic inputs for high-side gate driver outputs (phase 1); input is out-of-phase with output
Logic inputs for high-side gate driver outputs (phase 2); input is out-of-phase with output
Logic inputs for high-side gate driver outputs (phase 3); input is out-of-phase with output
Logic inputs for low-side gate driver outputs (phase 1); input is out-of-phase with output
Logic inputs for low-side gate driver outputs (phase 2); input is out-of-phase with output
Logic inputs for low-side gate driver outputs (phase 3); input is out-of-phase with output
High-side driver outputs (phase 1)
High-side driver outputs (phase 2)
High-side driver outputs (phase 3)
Low-side driver outputs (phase 1)
Low-side driver outputs (phase 2)
Low-side driver outputs (phase 3)
Low-side gate drive return
Indicates over-current, over-temperature (ITRIP), or low-side undervoltage lockout has occurred.
This pin has negative logic and an open-drain output. The use of over-current and overtemperature protection requires the use of external components.
Logic input to shutdown functionality. Logic functions when EN is high (i.e., positive logic). No
effect on FAULT and not latched.
Analog input for over-current shutdown. When active, ITRIP shuts down outputs and activates
FAULT and RCIN low. When ITRIP becomes inactive, FAULT stays active low for an externally
set time tFLTCLR, then automatically becomes inactive (open-drain high impedance).
An external RC network input used to define the FAULT CLEAR delay (tFLTCLR) approximately
equal to R*C. When RCIN > 8 V, the FAULT pin goes back into an open-drain high-impedance
state.
FAULT/N
EN
ITRIP
RCIN
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© 2009 International Rectifier
15
IRS2336x(D) Family
Lead Definitions: IRS23364D
Symbol
Description
VCC
VSS
VB1
VB2
VB3
VS1
VS2
VS3
HIN1
HIN2
HIN3
LIN1
LIN2
LIN3
HO1
HO2
HO3
LO1
LO2
LO3
COM
Low-side supply voltage
Logic ground
High-side gate drive floating supply (phase 1)
High-side gate drive floating supply (phase 2)
High-side gate drive floating supply (phase 3)
High voltage floating supply return (phase 1)
High voltage floating supply return (phase 2)
High voltage floating supply return (phase 3)
Logic inputs for high-side gate driver outputs (phase 1); input is in-phase with output
Logic inputs for high-side gate driver outputs (phase 2); input is in-phase with output
Logic inputs for high-side gate driver outputs (phase 3); input is in-phase with output
Logic inputs for low-side gate driver outputs (phase 1); input is in-phase with output
Logic inputs for low-side gate driver outputs (phase 2); input is in-phase with output
Logic inputs for low-side gate driver outputs (phase 3); input is in-phase with output
High-side driver outputs (phase 1)
High-side driver outputs (phase 2)
High-side driver outputs (phase 3)
Low-side driver outputs (phase 1)
Low-side driver outputs (phase 2)
Low-side driver outputs (phase 3)
Low-side gate drive return
Indicates over-current, over-temperature (ITRIP), or low-side undervoltage lockout has occurred.
This pin has negative logic and an open-drain output. The use of over-current and overtemperature protection requires the use of external components.
Logic input to shutdown functionality. Logic functions when EN is high (i.e., positive logic). No
effect on FAULT and not latched.
Analog input for over-current shutdown. When active, ITRIP shuts down outputs and activates
FAULT and RCIN low. When ITRIP becomes inactive, FAULT stays active low for an externally
set time tFLTCLR, then automatically becomes inactive (open-drain high impedance).
An external RC network input used to define the FAULT CLEAR delay (tFLTCLR) approximately
equal to R*C. When RCIN > 8 V, the FAULT pin goes back into an open-drain high-impedance
state.
FAULT/N
EN
ITRIP
RCIN
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© 2009 International Rectifier
16
IRS2336x(D) Family
Lead Assignments
VB2
HO2
VS2
VB3
HO3
VS3
34
33
32
31
30
29
IRS2336(D)
VS1
1
28
HO1
2
27
n.c.
VB1
3
26
n.c.
25
LO1
24
LO2
23
LO3
34 Lead
MLPQ
n.c.
15
16
17
18
EN
RCIN
n.c.
n.c.
14
VSS
19
n.c.
20
8
ITRIP
7
n.c.
13
HIN3
FAULT
n.c.
12
21
n.c.
6
11
COM
HIN2
LIN3
22
9
5
10
HIN1
LIN2
4
LIN1
VCC
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© 2009 International Rectifier
17
IRS2336x(D) Family
Application Information and Additional Details
Information regarding the following topics are included as subsections within this section of the datasheet.
•
•
•
•
•
•
•
•
•
•
•
•
•
•
•
•
•
•
•
•
•
IGBT/MOSFET Gate Drive
Switching and Timing Relationships
Deadtime
Matched Propagation Delays
Input Logic Compatibility
Undervoltage Lockout Protection
Shoot-Through Protection
Enable Input
Fault Reporting and Programmable Fault Clear Timer
Over-Current Protection
Over-Temperature Shutdown Protection
Truth Table: Undervoltage lockout, ITRIP, and ENABLE
Advanced Input Filter
Short-Pulse / Noise Rejection
Integrated Bootstrap Functionality
Bootstrap Power Supply Design
Separate Logic and Power Grounds
Tolerant to Negative VS Transients
PCB Layout Tips
Integrated Bootstrap FET limitation
Additional Documentation
IGBT/MOSFET Gate Drive
The IRS2336xD HVICs are designed to drive up to six MOSFET or IGBT power devices. Figures 1 and 2 illustrate
several parameters associated with the gate drive functionality of the HVIC. The output current of the HVIC, used to
drive the gate of the power switch, is defined as IO. The voltage that drives the gate of the external power switch is
defined as VHO for the high-side power switch and VLO for the low-side power switch; this parameter is sometimes
generically called VOUT and in this case does not differentiate between the high-side or low-side output voltage.
VB
(or VCC)
VB
(or VCC)
IO+
HO
(or LO)
HO
(or LO)
+
IO-
VHO (or VLO)
VS
(or COM)
-
VS
(or COM)
Figure 1: HVIC sourcing current
Figure 2: HVIC sinking current
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© 2009 International Rectifier
18
IRS2336x(D) Family
Switching and Timing Relationships
The relationship between the input and output signals of the IRS2336(D) and IRS23364D are illustrated below in
Figures 3 and 4. From these figures, we can see the definitions of several timing parameters (i.e., PW IN, PW OUT, tON,
tOFF, tR, and tF) associated with this device.
LINx
(or HINx)
50%
LINx
(or HINx)
50%
50%
50%
PWIN
tON
LOx
(or HOx)
PWIN
tOFF
tR
tF
tON
PWOUT
90%
10%
90%
LOx
(or HOx)
10%
Figure 3: Switching time waveforms (IRS2336(D))
tOFF
tR
tF
PWOUT
90%
10%
90%
10%
Figure 4: Switching time waveforms (IRS23364D)
The following two figures illustrate the timing relationships of some of the functionality of the IRS2336xD; this
functionality is described in further detail later in this document.
During interval A of Figure 5, the HVIC has received the command to turn-on both the high- and low-side switches at
the same time; as a result, the shoot-through protection of the HVIC has prevented this condition and both the highand low-side output are held in the off state.
Interval B of Figures 5 and 6 shows that the signal on the ITRIP input pin has gone from a low to a high state; as a
result, all of the gate drive outputs have been disabled (i.e., see that HOx has returned to the low state; LOx is also
held low), the voltage on the RCIN pin has been pulled to 0 V, and a fault is reported by the FAULT output
transitioning to the low state. Once the ITRIP input has returned to the low state, the output will remain disabled and
the fault condition reported until the voltage on the RCIN pin charges up to VRCIN,TH (see interval C in Figure 6); the
charging characteristics are dictated by the RC network attached to the RCIN pin.
During intervals D and E of Figure 5, we can see that the enable (EN) pin has been pulled low (as is the case when
the driver IC has received a command from the control IC to shutdown); this results in the outputs (HOx and LOx)
being held in the low state until the enable pin is pulled high.
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IRS2336x(D) Family
Figure 5: Input/output timing diagram for the IRS2336xD family
Interval B
Interval C
VIT,TH-
VIT,TH+
ITRIP
FAULT
tFLT
50%
50%
RCIN
VRCIN,TH
tFLTCLR
90%
HOx
tITRIP
Figure 6: Detailed view of B & C intervals
Deadtime
This family of HVICs features integrated deadtime protection circuitry. The deadtime for these ICs is fixed; other ICs
within IR’s HVIC portfolio feature programmable deadtime for greater design flexibility. The deadtime feature inserts
a time period (a minimum deadtime) in which both the high- and low-side power switches are held off; this is done to
ensure that the power switch being turned off has fully turned off before the second power switch is turned on. This
minimum deadtime is automatically inserted whenever the external deadtime is shorter than DT; external deadtimes
larger than DT are not modified by the gate driver. Figure 7 illustrates the deadtime period and the relationship
between the output gate signals.
The deadtime circuitry of the IRS2336xD is matched with respect to the high- and low-side outputs of a given
channel; additionally, the deadtimes of each of the three channels are matched. Figure 7 defines the two deadtime
parameters (i.e., DT1 and DT2) of a specific channel; the deadtime matching parameter (MDT) associated with the
IRS2336xD specifies the maximum difference between DT1 and DT2. The MDT parameter also applies when
comparing the DT of one channel of the IRS2336xD to that of another.
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IRS2336x(D) Family
Figure 7: Illustration of deadtime
Matched Propagation Delays
The IRS2336xD family of HVICs is designed with propagation delay matching circuitry. With this feature, the IC’s
response at the output to a signal at the input requires approximately the same time duration (i.e., tON, tOFF) for both
the low-side channels and the high-side channels; the maximum difference is specified by the delay matching
parameter (MT). Additionally, the propagation delay for each low-side channel is matched when compared to the
other low-side channels and the propagation delays of the high-side channels are matched with each other; the MT
specification applies as well. The propagation turn-on delay (tON) of the IRS2336xD is matched to the propagation
turn-on delay (tOFF).
Input Logic Compatibility
The inputs of this IC are compatible with standard CMOS and TTL outputs. The IRS2336xD family has been
designed to be compatible with 3.3 V and 5 V logic-level signals. The IRS2336(D) features an integrated 5.2 V Zener
clamp on the HIN, LIN, ITRIP, and EN pins; the IRS23364D does not offer this input clamp. Figure 8 illustrates an
input signal to the IRS2336(D) and IRS23364D, its input threshold values, and the logic state of the IC as a result of
the input signal.
Figure 8: HIN & LIN input thresholds
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IRS2336x(D) Family
Undervoltage Lockout Protection
This family of ICs provides undervoltage lockout protection on both the VCC (logic and low-side circuitry) power supply
and the VBS (high-side circuitry) power supply. Figure 9 is used to illustrate this concept; VCC (or VBS) is plotted over
time and as the waveform crosses the UVLO threshold (VCCUV+/- or VBSUV+/-) the undervoltage protection is enabled or
disabled.
Upon power-up, should the VCC voltage fail to reach the VCCUV+ threshold, the IC will not turn-on. Additionally, if the
VCC voltage decreases below the VCCUV- threshold during operation, the undervoltage lockout circuitry will recognize a
fault condition and shutdown the high- and low-side gate drive outputs, and the FAULT pin will transition to the low
state to inform the controller of the fault condition.
Upon power-up, should the VBS voltage fail to reach the VBSUV threshold, the IC will not turn-on. Additionally, if the VBS
voltage decreases below the VBSUV threshold during operation, the undervoltage lockout circuitry will recognize a fault
condition, and shutdown the high-side gate drive outputs of the IC.
The UVLO protection ensures that the IC drives the external power devices only when the gate supply voltage is
sufficient to fully enhance the power devices. Without this feature, the gates of the external power switch could be
driven with a low voltage, resulting in the power switch conducting current while the channel impedance is high; this
could result in very high conduction losses within the power device and could lead to power device failure.
Figure 9: UVLO protection
Shoot-Through Protection
The IRS2336xD family of high-voltage ICs is equipped with shoot-through protection circuitry (also known as crossconduction prevention circuitry). Figure 10 shows how this protection circuitry prevents both the high- and low-side
switches from conducting at the same time. Table 1 illustrates the input/output relationship of the devices in the form
of a truth table. Note that the IRS2336(D) has inverting inputs (the output is out-of-phase with its respective input)
while the IRS23364D has non-inverting inputs (the output is in-phase with its respective input).
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IRS2336x(D) Family
Figure 10: Illustration of shoot-through protection circuitry
IRS2336(D)
IRS23364D
HIN
LIN
HO
LO
HIN
LIN
HO
LO
0
0
0
0
0
0
0
0
0
1
1
0
0
1
0
1
1
0
0
1
1
0
1
0
1
1
0
0
1
1
0
0
Table 1: Input/output truth table for IRS2336D and IRS23364D
Enable Input
The IRS2336xD family of HVICs is equipped with an enable input pin that is used to shutdown or enable the HVIC.
When the EN pin is in the high state the HVIC is able to operate normally (assuming no other fault conditions). When
a condition occurs that should shutdown the HVIC, the EN pin should see a low logic state. The enable circuitry of
the IRS2336xD features an input filter; the minimum input duration is specified by tFILTER,EN. Please refer to the EN
pin parameters VEN,TH+, VEN,TH-, and IEN for the details of its use. Table 2 gives a summary of this pin’s functionality
and Figure 11 illustrates the outputs’ response to a shutdown command.
EN
VEN,TH-
Enable Input
tEN
*
Enable input high
Outputs enabled
Enable input low
Outputs disabled
HOx
(or LOx)
Table 2: Enable functionality truth table
(*assumes no other fault condition)
90%
Figure 11: Output enable timing waveform
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IRS2336x(D) Family
Fault Reporting and Programmable Fault Clear Timer
The IRS2336xD family provides an integrated fault reporting output and an adjustable fault clear timer. There are two
situations that would cause the HVIC to report a fault via the FAULT pin. The first is an undervoltage condition of VCC
and the second is if the ITRIP pin recognizes a fault. Once the fault condition occurs, the FAULT pin is internally
pulled to VSS and the fault clear timer is activated. The fault output stays in the low state until the fault condition has
been removed and the fault clear timer expires; once the fault clear timer expires, the voltage on the FAULT pin will
return to VCC.
The length of the fault clear time period (tFLTCLR) is determined by exponential charging characteristics of the capacitor
where the time constant is set by RRCIN and CRCIN. In Figure 12 where we see that a fault condition has occurred
(UVLO or ITRIP), RCIN and FAULT are pulled to VSS, and once the fault has been removed, the fault clear timer
begins. Figure 13 shows that RRCIN is connected between the VCC and the RCIN pin, while CRCIN is placed between
the RCIN and VSS pins.
Figure 12: RCIN and FAULT pin waveforms
Figure 13: Programming the fault clear timer
The design guidelines for this network are shown in Table 3.
≤1 nF
CRCIN
Ceramic
0.5 MΩ to 2 MΩ
RRCIN
>> RON,RCIN
Table 3: Design guidelines
The length of the fault clear time period can be determined by using the formula below.
-t/RC
vC(t) = Vf(1-e
)
tFLTCLR = -(RRCINCRCIN)ln(1-VRCIN,TH/VCC)
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IRS2336x(D) Family
Over-Current Protection
The IRS2336xD HVICs are equipped with an ITRIP input pin. This functionality can be used to detect over-current
events in the DC- bus. Once the HVIC detects an over-current event through the ITRIP pin, the outputs are
shutdown, a fault is reported through the FAULT pin, and RCIN is pulled to VSS.
The level of current at which the over-current protection is initiated is determined by the resistor network (i.e., R0, R1,
and R2) connected to ITRIP as shown in Figure 14, and the ITRIP threshold (VIT,TH+). The circuit designer will need to
determine the maximum allowable level of current in the DC- bus and select R0, R1, and R2 such that the voltage at
node VX reaches the over-current threshold (VIT,TH+) at that current level.
VIT,TH+ = R0IDC-(R1/(R1+R2))
Figure 14: Programming the over-current protection
For example, a typical value for resistor R0 could be 50 mΩ. The voltage of the ITRIP pin should not be allowed to
exceed 5 V; if necessary, an external voltage clamp may be used.
Over-Temperature Shutdown Protection
The ITRIP input of the IRS2336xD can also be used to detect over-temperature events in the system and initiate a
shutdown of the HVIC (and power switches) at that time. In order to use this functionality, the circuit designer will
need to design the resistor network as shown in Figure 15 and select the maximum allowable temperature.
This network consists of a thermistor and two standard resistors R3 and R4. As the temperature changes, the
resistance of the thermistor will change; this will result in a change of voltage at node VX. The resistor values should
be selected such the voltage VX should reach the threshold voltage (VIT,TH+) of the ITRIP functionality by the time that
the maximum allowable temperature is reached. The voltage of the ITRIP pin should not be allowed to exceed 5 V.
When using both the over-current protection and over-temperature protection with the ITRIP input, OR-ing diodes
(e.g., DL4148) can be used. This network is shown in Figure 16; the OR-ing diodes have been labeled D1 and D2.
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IRS2336x(D) Family
Figure 15: Programming over-temperature protection
Figure 16: Using over-current protection and overtemperature protection
Truth Table: Undervoltage lockout, ITRIP, and ENABLE
Table 4 provides the truth table for the IRS2336xD. The first line shows that the UVLO for VCC has been tripped; the
FAULT output has gone low and the gate drive outputs have been disabled. VCCUV is not latched in this case and
when VCC is greater than VCCUV, the FAULT output returns to the high impedance state.
The second case shows that the UVLO for VBS has been tripped and that the high-side gate drive outputs have been
disabled. After VBS exceeds the VBSUV threshold, HO will stay low until the HVIC input receives a new falling
(IRS2336(D)) or rising (IRS23364D) transition of HIN. The third case shows the normal operation of the HVIC. The
fourth case illustrates that the ITRIP trip threshold has been reached and that the gate drive outputs have been
disabled and a fault has been reported through the fault pin. In the last case, the HVIC has received a command
through the EN input to shutdown; as a result, the gate drive outputs have been disabled.
UVLO VCC
UVLO VBS
Normal operation
ITRIP fault
EN command
VCC
<VCCUV
15 V
15 V
15 V
15 V
VBS
—
<VBSUV
15 V
15 V
15 V
ITRIP
—
0V
0V
>VITRIP
0V
EN
—
5V
5V
5V
0V
RCIN
High
High
High
Low
High
FAULT
0
High impedance
High impedance
0
High impedance
LO
0
LIN
LIN
0
0
HO
0
0
HIN
0
0
Table 4: IRS2336xD UVLO, ITRIP, EN, RCIN, & FAULT truth table
Advanced Input Filter
The advanced input filter allows an improvement in the input/output pulse symmetry of the HVIC and helps to reject
noise spikes and short pulses. This input filter has been applied to the HIN, LIN, and EN inputs. The working
principle of the new filter is shown in Figures 17 and 18.
Figure 17 shows a typical input filter and the asymmetry of the input and output. The upper pair of waveforms
(Example 1) show an input signal with a duration much longer then tFIL,IN; the resulting output is approximately the
difference between the input signal and tFIL,IN. The lower pair of waveforms (Example 2) show an input signal with a
duration slightly longer then tFIL,IN; the resulting output is approximately the difference between the input signal and
tFIL,IN.
Figure 18 shows the advanced input filter and the symmetry between the input and output. The upper pair of
waveforms (Example 1) show an input signal with a duration much longer then tFIL,IN; the resulting output is
approximately the same duration as the input signal. The lower pair of waveforms (Example 2) show an input signal
with a duration slightly longer then tFIL,IN; the resulting output is approximately the same duration as the input signal.
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IRS2336x(D) Family
Figure 17: Typical input filter
Figure 18: Advanced input filter
Short-Pulse / Noise Rejection
Example 2
Example 1
This device’s input filter provides protection against short-pulses (e.g., noise) on the input lines. If the duration of the
input signal is less than tFIL,IN, the output will not change states. Example 1 of Figure 19 shows the input and output in
the low state with positive noise spikes of durations less than tFIL,IN; the output does not change states. Example 2 of
Figure 19 shows the input and output in the high state with negative noise spikes of durations less than tFIL,IN; the
output does not change states.
Figure 19: Noise rejecting input filters
Figures 20 and 21 present lab data that illustrates the characteristics of the input filters while receiving ON and OFF
pulses.
The input filter characteristic is shown in Figure 20; the left side illustrates the narrow pulse ON (short positive pulse)
characteristic while the left shows the narrow pulse OFF (short negative pulse) characteristic. The x-axis of Figure 20
shows the duration of PW IN, while the y-axis shows the resulting PW OUT duration. It can be seen that for a PW IN
duration less than tFIL,IN, that the resulting PW OUT duration is zero (e.g., the filter rejects the input signal/noise). We
also see that once the PW IN duration exceed tFIL,IN, that the PW OUT durations mimic the PW IN durations very well over
this interval with the symmetry improving as the duration increases. To ensure proper operation of the HVIC, it is
suggested that the input pulse width for the high-side inputs be ≥ 500 ns.
The difference between the PW OUT and PW IN signals of both the narrow ON and narrow OFF cases is shown in
Figure 21; the careful reader will note the scale of the y-axis. The x-axis of Figure 21 shows the duration of PW IN,
while the y-axis shows the resulting PW OUT–PW IN duration. This data illustrates the performance and near symmetry
of this input filter.
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Time (ns)
IRS2336x(D) Family
Figure 20: IRS2336xD input filter characteristic
Figure 21: Difference between the input pulse and the output pulse
Integrated Bootstrap Functionality
The new IRS2336xD family features integrated high-voltage bootstrap MOSFETs that eliminate the need of the
external bootstrap diodes and resistors in many applications.
There is one bootstrap MOSFET for each high-side output channel and it is connected between the VCC supply and
its respective floating supply (i.e., VB1, VB2, VB3); see Figure 22 for an illustration of this internal connection.
The integrated bootstrap MOSFET is turned on only during the time when LO is ‘high’, and it has a limited source
current due to RBS. The VBS voltage will be charged each cycle depending on the on-time of LO and the value of the
CBS capacitor, the drain-source (collector-emitter) drop of the external IGBT (or MOSFET), and the low-side freewheeling diode drop.
The bootstrap MOSFET of each channel follows the state of the respective low-side output stage (i.e., the bootstrap
MOSFET is ON when LO is high, it is OFF when LO is low), unless the VB voltage is higher than approximately 110%
of VCC. In that case, the bootstrap MOSFET is designed to remain off until VB returns below that threshold; this
concept is illustrated in Figure 23.
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IRS2336x(D) Family
VB1
VCC
VB2
VB3
Figure 22: Internal bootstrap MOSFET connection
Figure 23: Bootstrap MOSFET state diagram
A bootstrap MOSFET is suitable for most of the PWM modulation schemes and can be used either in parallel with the
external bootstrap network (i.e., diode and resistor) or as a replacement of it. The use of the integrated bootstrap as
a replacement of the external bootstrap network may have some limitations. An example of this limitation may arise
when this functionality is used in non-complementary PWM schemes (typically 6-step modulations) and at very high
PWM duty cycle. In these cases, superior performances can be achieved by using an external bootstrap diode in
parallel with the internal bootstrap network.
Bootstrap Power Supply Design
For information related to the design of the bootstrap power supply while using the integrated bootstrap functionality
of the IRS2336xD family, please refer to Application Note 1123 (AN-1123) entitled “Bootstrap Network Analysis:
Focusing on the Integrated Bootstrap Functionality.” This application note is available at www.irf.com.
For information related to the design of a standard bootstrap power supply (i.e., using an external discrete diode)
please refer to Design Tip 04-4 (DT04-4) entitled “Using Monolithic High Voltage Gate Drivers.” This design tip is
available at www.irf.com.
Separate Logic and Power Grounds
The IRS2336xD has separate logic and power ground pin (VSS and COM respectively) to eliminate some of the noise
problems that can occur in power conversion applications. Current sensing shunts are commonly used in many
applications for power inverter protection (i.e., over-current protection), and in the case of motor drive applications, for
motor current measurements. In these situations, it is often beneficial to separate the logic and power grounds.
Figure 24 shows a HVIC with separate VSS and COM pins and how these two grounds are used in the system. The
VSS is used as the reference point for the logic and over-current circuitry; VX in the figure is the voltage between the
ITRIP pin and the VSS pin. Alternatively, the COM pin is the reference point for the low-side gate drive circuitry. The
output voltage used to drive the low-side gate is VLO-COM; the gate-emitter voltage (VGE) of the low-side switch is the
output voltage of the driver minus the drop across RG,LO.
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IRS2336x(D) Family
DC+ BUS
DBS
VB
(x3)
VCC
CBS
HO
(x3)
HVIC
ITRIP
RG,HO
VS
(x3)
LO
(x3)
VS1
VS3
RG,LO
+
+
VSS
VS2
VGE1
COM
+
VGE2
-
-
VGE3
-
R2
R0
+
VX
R1
-
DC- BUS
Figure 24: Separate VSS and COM pins
Tolerant to Negative VS Transients
A common problem in today’s high-power switching converters is the transient response of the switch node’s voltage
as the power switches transition on and off quickly while carrying a large current. A typical 3-phase inverter circuit is
shown in Figure 25; here we define the power switches and diodes of the inverter.
If the high-side switch (e.g., the IGBT Q1 in Figures 26 and 27) switches off, while the U phase current is flowing to
an inductive load, a current commutation occurs from high-side switch (Q1) to the diode (D2) in parallel with the lowside switch of the same inverter leg. At the same instance, the voltage node VS1, swings from the positive DC bus
voltage to the negative DC bus voltage.
Figure 25: Three phase inverter
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IRS2336x(D) Family
DC+ BUS
Q1
ON
IU
VS1
Q2
OFF
D2
DC- BUS
Figure 26: Q1 conducting
Figure 27: D2 conducting
Also when the V phase current flows from the inductive load back to the inverter (see Figures 28 and 29), and Q4
IGBT switches on, the current commutation occurs from D3 to Q4. At the same instance, the voltage node, VS2,
swings from the positive DC bus voltage to the negative DC bus voltage.
Figure 28: D3 conducting
Figure 29: Q4 conducting
However, in a real inverter circuit, the VS voltage swing does not stop at the level of the negative DC bus, rather it
swings below the level of the negative DC bus. This undershoot voltage is called “negative VS transient”.
The circuit shown in Figure 30 depicts one leg of the three phase inverter; Figures 31 and 32 show a simplified
illustration of the commutation of the current between Q1 and D2. The parasitic inductances in the power circuit from
the die bonding to the PCB tracks are lumped together in LC and LE for each IGBT. When the high-side switch is on,
VS1 is below the DC+ voltage by the voltage drops associated with the power switch and the parasitic elements of the
circuit. When the high-side power switch turns off, the load current momentarily flows in the low-side freewheeling
diode due to the inductive load connected to VS1 (the load is not shown in these figures). This current flows from the
DC- bus (which is connected to the COM pin of the HVIC) to the load and a negative voltage between VS1 and the
DC- Bus is induced (i.e., the COM pin of the HVIC is at a higher potential than the VS pin).
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IRS2336x(D) Family
Figure 30: Parasitic Elements
Figure 31: VS positive
Figure 32: VS negative
In a typical motor drive system, dV/dt is typically designed to be in the range of 3-5 V/ns. The negative VS transient
voltage can exceed this range during some events such as short circuit and over-current shutdown, when di/dt is
greater than in normal operation.
International Rectifier’s HVICs have been designed for the robustness required in many of today’s demanding
applications. The IRS2336xD has been seen to withstand large negative VS transient conditions on the order of -50 V
for a period of 50 ns. An illustration of the IRS2336D’s performance can be seen in Figure 33. This experiment was
conducted using various loads to create this condition; the curve shown in this figure illustrates the successful
operation of the IRS2336D under these stressful conditions. In case of -VS transients greater then -20 V for a period
of time greater than 100 ns; the HVIC is designed to hold the high-side outputs in the off state for 4.5 µs in order to
ensure that the high- and low-side power switches are not on at the same time.
Figure 33: Negative VS transient results for an International Rectifier HVIC
Even though the IRS2336xD has been shown able to handle these large negative VS transient conditions, it is highly
recommended that the circuit designer always limit the negative VS transients as much as possible by careful PCB
layout and component use.
PCB Layout Tips
Distance between high and low voltage components: It’s strongly recommended to place the components tied to the
floating voltage pins (VB and VS) near the respective high voltage portions of the device. The IRS2336xD in the
PLCC44 package has had some unused pins removed in order to maximize the distance between the high voltage
and low voltage pins. Please see the Case Outline PLCC44 information in this datasheet for the details.
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IRS2336x(D) Family
Ground Plane: In order to minimize noise coupling, the ground plane should not be placed under or near the high
voltage floating side.
Gate Drive Loops: Current loops behave like antennas and are able to receive and transmit EM noise (see Figure
34). In order to reduce the EM coupling and improve the power switch turn on/off performance, the gate drive loops
must be reduced as much as possible. Moreover, current can be injected inside the gate drive loop via the IGBT
collector-to-gate parasitic capacitance. The parasitic auto-inductance of the gate loop contributes to developing a
voltage across the gate-emitter, thus increasing the possibility of a self turn-on effect.
Figure 34: Antenna Loops
Supply Capacitor: It is recommended to place a bypass capacitor (CIN) between the VCC and VSS pins.
connection is shown in Figure 35. A ceramic 1 µF ceramic capacitor is suitable for most applications.
component should be placed as close as possible to the pins in order to reduce parasitic elements.
This
This
Vcc
HIN (x3)
VB (x3)
LIN (x3)
HO (x3)
EN
VS (x3)
FAULT
CIN
RCIN
LO (x3)
ITRIP
COM
VSS
Figure 35: Supply capacitor
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IRS2336x(D) Family
Routing and Placement: Power stage PCB parasitic elements can contribute to large negative voltage transients at
the switch node; it is recommended to limit the phase voltage negative transients. In order to avoid such conditions, it
is recommended to 1) minimize the high-side emitter to low-side collector distance, and 2) minimize the low-side
emitter to negative bus rail stray inductance. However, where negative VS spikes remain excessive, further steps
may be taken to reduce the spike. This includes placing a resistor (5 Ω or less) between the VS pin and the switch
node (see Figure 36), and in some cases using a clamping diode between VSS and VS (see Figure 37). See DT04-4
at www.irf.com for more detailed information.
Figure 36: VS resistor
Figure 37: VS clamping diode
Integrated Bootstrap FET limitation
The integrated Bootstrap FET functionality has an operational limitation under the following bias conditions applied to
the HVIC:
•
•
VCC pin voltage = 0V AND
VS or VB pin voltage > 0
In the absence of a VCC bias, the integrated bootstrap FET voltage blocking capability is compromised and a
current conduction path is created between VCC & VB pins, as illustrated in Fig.38 below, resulting in power loss
and possible damage to the HVIC.
Figure 38: Current conduction path between VCC and VB pin
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IRS2336x(D) Family
Relevant Application Situations:
The above mentioned bias condition may be encountered under the following situations:
• In a motor control application, a permanent magnet motor naturally rotating while VCC power is OFF.
In this condition, Back EMF is generated at a motor terminal which causes high voltage bias on VS
nodes resulting unwanted current flow to VCC.
• Potential situations in other applications where VS/VB node voltage potential increases before the
VCC voltage is available (for example due to sequencing delays in SMPS supplying VCC bias)
Application Workaround:
Insertion of a standard p-n junction diode between VCC pin of IC and positive terminal of VCC capacitors (as
illustrated in Fig.39) prevents current conduction “out-of” VCC pin of gate driver IC. It is important not to connect
the VCC capacitor directly to pin of IC. Diode selection is based on 25V rating or above & current capability
aligned to ICC consumption of IC - 100mA should cover most application situations. As an example, Part number
# LL4154 from Diodes Inc (25V/150mA standard diode) can be used.
VCC
VCC
Capacitor
VB
VSS
(or COM)
Figure 39: Diode insertion between VCC pin and VCC capacitor
Note that the forward voltage drop on the diode (VF) must be taken into account when biasing the VCC pin of the
IC to meet UVLO requirements. VCC pin Bias = VCC Supply Voltage – VF of Diode.
Additional Documentation
Several technical documents related to the use of HVICs are available at www.irf.com; use the Site Search
function and the document number to quickly locate them. Below is a short list of some of these documents.
DT97-3: Managing Transients in Control IC Driven Power Stages
AN-1123: Bootstrap Network Analysis: Focusing on the Integrated Bootstrap Functionality
DT04-4: Using Monolithic High Voltage Gate Drivers
AN-978: HV Floating MOS-Gate Driver ICs
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IRS2336x(D) Family
Parameter Temperature Trends
1000
1000
800
800
Exp.
Exp.
600
tOFF (ns)
tON (ns)
Figures 40-61 provide information on the experimental performance of the IRS2336xD HVIC. The line plotted in
each figure is generated from actual lab data. A small number of individual samples were tested at three
temperatures (-40 ºC, 25 ºC, and 125 ºC) in order to generate the experimental (Exp.) curve. The line labeled Exp.
consist of three data points (one data point at each of the tested temperatures) that have been connected together
to illustrate the understood temperature trend. The individual data points on the curve were determined by
calculating the averaged experimental value of the parameter (for a given temperature).
400
600
400
200
200
0
-50
-25
0
25
50
75
100
0
-50
125
-25
0
Temperature (o C)
25
50
75
100
125
Temperature (o C)
Figure 40: tON vs. temperature
Figure 41: tOFF vs. temperature
600
1500
1200
450
tITRIP (ns)
DT (ns)
Exp.
300
Exp.
900
600
150
300
0
-50
-25
0
25
50
75
100
0
-50
125
Temperature (o C)
-25
0
25
50
75
100
125
Temperature (o C)
Figure 42: DT vs. temperature
Figure 43: tITRIP vs. temperature
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© 2009 International Rectifier
36
IRS2336x(D) Family
1200
1000
1000
800
Exp.
tEN (ns)
tFLT (ns)
800
600
600
Exp.
400
400
200
200
0
-50
-25
0
25
50
75
100
0
-50
125
-25
0
Temperature (o C)
Figure 44: tFLT vs. temperature
50
75
100
125
100
125
Figure 45: tEN vs. temperature
60
60
40
MDT (ns)
40
MT (ns)
25
Temperature (o C)
Exp.
20
Exp.
20
0
0
-50
-25
0
25
50
75
100
125
-50
-25
0
Temperature (oC)
25
50
75
Temperature (oC)
Figure 46: MT vs. temperature
Figure 47: MDT vs. temperature
60
16
12
ITRIP+ (µA)
PM (ns)
40
Exp.
8
20
Exp.
4
0
-50
-25
0
25
50
75
100
0
-50
125
Temperature (oC)
-25
0
25
50
75
100
125
Temperature (oC)
Figure 48: PM vs. temperature
Figure 49: IITRIP+ vs. temperature
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© 2009 International Rectifier
37
IRS2336x(D) Family
5
120
100
4
IQBS (µA)
IQCC (mA)
80
3
Exp.
2
60
Exp.
40
1
20
0
-50
-25
0
25
50
75
100
0
-50
125
-25
0
o
25
50
75
100
125
Temperature (o C)
Temperature ( C)
Figure 50: IQCC vs. temperature
Figure 51: IQBS vs. temperature
0.60
0.60
0.40
0.40
IO- (A)
I O+ (A)
Exp.
Exp.
p.
0.20
0.00
-50
0.20
-25
0
25
50
75
100
0.00
-50
125
-25
0
Temperature (oC)
25
50
75
100
125
100
125
Temperature (o C)
Figure 52: IO+ vs. temperature
Figure 53: IO- vs. temperature
12
12
10
10
Exp.
Exp.
8
VCCUV- (V)
VCCUV+ (V)
8
6
6
4
4
2
2
0
-50
-25
0
25
50
75
100
0
-50
125
Temperature (o C)
-25
0
25
50
75
Temperature (o C)
Figure 54: VCCUV+ vs. temperature
Figure 55: VCCUV- vs. temperature
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© 2009 International Rectifier
38
IRS2336x(D) Family
10
10
9
9
Exp.
VBSUV- (V)
VBSUV+ (V)
Exp.
8
7
6
8
7
6
5
-50
-25
0
25
50
75
100
5
-50
125
-25
0
Temperature (oC)
25
50
75
100
125
Temperature (oC)
Figure 56: VBSUV+ vs. temperature
Figure 57: VBSUV- vs. temperature
800
800
600
VIT,TH- (mV)
VIT,TH+ (mV)
600
EXP.
p.
Exp.
400
400
200
0
200
-50
-25
0
25
50
75
100
-50
125
-25
0
Figure 58: VIT,TH+ vs. temperature
50
75
100
125
Figure 59: VIT,TH- vs. temperature
100
100
80
80
RON,FLT (Ω)
RON,RCIN (Ω)
25
Temperature (o C)
Temperature (oC)
60
40
60
Exp.
40
Exp.
20
20
0
-50
-25
0
25
50
75
100
0
-50
125
Temperature (o C)
-25
0
25
50
75
100
125
Temperature (oC)
Figure 60: RON,RCIN vs. temperature
Figure 61: RON,FLT vs. temperature
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© 2009 International Rectifier
39
IRS2336x(D) Family
Package Details: PDIP28
www.irf.com
© 2009 International Rectifier
40
IRS2336x(D) Family
Package Details: SOIC28W
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© 2009 International Rectifier
41
IRS2336x(D) Family
Package Details: PLCC44
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© 2009 International Rectifier
42
IRS2336x(D) Family
Case outline drawing for: MLPQ7X7
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© 2009 International Rectifier
43
IRS2336x(D) Family
Tape and Reel Details: SOIC28W
LOADED TAPE FEED DIRECTION
A
B
H
D
F
C
NOTE : CONTROLLING
DIM ENSION IN M M
E
G
CARRIER TAPE DIMENSION FOR
Metric
Code
Min
Max
A
11.90
12.10
B
3.90
4.10
C
23.70
24.30
D
11.40
11.60
E
10.80
11.00
F
18.20
18.40
G
1.50
n/a
H
1.50
1.60
28SOICW
Imperial
Min
Max
0.468
0.476
0.153
0.161
0.933
0.956
0.448
0.456
0.425
0.433
0.716
0.724
0.059
n/a
0.059
0.062
F
D
C
B
A
E
G
H
REEL DIMENSIONS FOR 28SOICW
Metric
Imperial
Code
Min
Max
Min
Max
A
329.60
330.25
12.976
13.001
B
20.95
21.45
0.824
0.844
C
12.80
13.20
0.503
0.519
D
1.95
2.45
0.767
0.096
E
98.00
102.00
3.858
4.015
F
n/a
30.40
n/a
1.196
G
26.50
29.10
1.04
1.145
H
24.40
26.40
0.96
1.039
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© 2009 International Rectifier
44
IRS2336x(D) Family
Tape and Reel Details: PLCC44
LOADED TAPE FEED DIRECTION
A
B
H
D
F
C
NOTE : CONTROLLING
DIM ENSION IN M M
E
G
CARRIER TAPE DIMENSION FOR 44PLCC
Metric
Imperial
Code
Min
Max
Min
Max
A
23.90
24.10
0.94
0.948
B
3.90
4.10
0.153
0.161
C
31.70
32.30
1.248
1.271
D
14.10
14.30
0.555
0.562
E
17.90
18.10
0.704
0.712
F
17.90
18.10
0.704
0.712
G
2.00
n/a
0.078
n/a
H
1.50
1.60
0.059
0.062
F
D
C
B
A
E
G
H
REEL DIMENSIONS FOR 44PLCC
Metric
Code
Min
Max
A
329.60
330.25
B
20.95
21.45
C
12.80
13.20
D
1.95
2.45
E
98.00
102.00
F
n/a
38.4
G
34.7
35.8
H
32.6
33.1
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Imperial
Min
Max
12.976
13.001
0.824
0.844
0.503
0.519
0.767
0.096
3.858
4.015
n/a
1.511
1.366
1.409
1.283
1.303
© 2009 International Rectifier
45
IRS2336x(D) Family
Tape and Reel Details: MLPQ7X7
LOADED TAPE FEED DIRECTION
A
B
H
D
F
C
NOTE : CONTROLLING
DIMENSION IN MM
E
G
CARRIER TAPE DIMENSION FOR 48MLPQ7X7
Metric
Imperial
Code
Min
Max
Min
Max
A
11.90
12.10
0.474
0.476
B
3.90
4.10
0.153
0.161
C
15.70
16.30
0.618
0.641
D
7.40
7.60
0.291
0.299
E
7.15
7.35
0.281
0.289
F
7.15
7.35
0.281
0.289
G
1.50
n/a
0.059
n/a
H
1.50
1.60
0.059
0.062
F
D
C
B
A
E
G
H
REEL DIMENSIONS FOR 48MLPQ7X7
Metric
Imperial
Code
Min
Max
Min
Max
A
329.60
330.25
12.976
13.001
B
20.95
21.45
0.824
0.844
C
12.80
13.20
0.503
0.519
D
1.95
2.45
0.767
0.096
E
98.00
102.00
3.858
4.015
F
n/a
22.4
n/a
0.881
G
18.5
21.1
0.728
0.83
H
16.4
18.4
0.645
0.724
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© 2009 International Rectifier
46
IRS2336x(D) Family
Part Marking Information
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© 2009 International Rectifier
47
IRS2336x(D) Family
Ordering Information
Standard Pack
Base Part Number
Package Type
Complete Part Number
Form
Quantity
Tube/Bulk
52
Tape and Reel
3000
Tube/Bulk
13
IRS2336DPbF
Tube/Bulk
25
IRS2336DSPbF
Tape and Reel
1000
Tube/Bulk
27
IRS2336DJPbF
Tape and Reel
500
IRS2336DJTRPbF
Tube/Bulk
13
IRS2336PbF
Tube/Bulk
25
Tape and Reel
1000
Tube/Bulk
27
IRS2336JPbF
Tape and Reel
500
IRS2336JTRPbF
Tube/Bulk
13
IRS23364DPbF
Tube/Bulk
25
IRS23364DSPbF
Tape and Reel
1000
Tube/Bulk
27
IRS23364DJPbF
Tape and Reel
500
IRS23364DJTRPbF
IRS2336DMPbF
MLPQ7x7 48L
PDIP28
IRS2336D
SOIC28W
PLCC44
PDIP28
SOIC28W
IRS2336
IRS2336DMTRPbF
IRS2336DSTRPbF
IRS2336SPbF
IRS2336STRPbF
PLCC44
PDIP28
SOIC28W
IRS23364D
PLCC44
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IRS23364DSTRPbF
© 2009 International Rectifier
48
IRS2336x(D) Family
The information provided in this document is believed to be accurate and reliable. However, International Rectifier assumes no responsibility
for the consequences of the use of this information. International Rectifier assumes no responsibility for any infringement of patents or of
other rights of third parties which may result from the use of this information. No license is granted by implication or otherwise under any
patent or patent rights of International Rectifier. The specifications mentioned in this document are subject to change without notice. This
document supersedes and replaces all information previously supplied.
For technical support, please contact IR’s Technical Assistance Center
http://www.irf.com/technical-info/
WORLD HEADQUARTERS:
233 Kansas St., El Segundo, California 90245
Tel: (310) 252-7105
Revision History
Date
09/17/07
01/15/08
01/31/08
02/26/08
4/24/08
5/7/08
5/9/08
16/10/09
26/04/11
Comment
Original document.
Typo correction
Added MLPQ7x7 package style
Corrected ESD & Latch-up Classification, added note for CDM classification, added ordering
information for MLPQ7x7
Added non-D version (not done)
Added non-D version in Ordering information (p47)
Reviewed and updated all specifications in accordance with DR3 limits tables.
Pag 17: IRS2336DMPbF pin assignment changed
Pag 42: IRS2336DMPbF package drawing changed
Updated ESD HBM
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© 2009 International Rectifier
49