BW9910/A High Brightness LED Driver

BW9910/A High Brightness LED Driver
Features
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Product Description
Efficiency > 90%
Universal rectified 85VAC to 265VAC input range
Constant current LED driver
Applications from a few mA to more than 1.0A
LED string from one to hundreds of diodes
PWM low-frequency dimming via PWM_D pin
Input voltage surge ratings up to 500V
Internal over temperature protection (OTP)
7.5V MOSFET drive – BW9910
10V MOSFET drive – BW9910A
Typical Applications
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AC/DC or DC/DC LED Driver applications
RGB backlighting LED Driver
Backlighting of flat panel displays
General purpose constant current source
Signage and decorative LED lighting
Buck/Buck-Boost/Boost LED driver
T8/T9/T10 LED tubes
E26/E27 LED bulbs
The BW9910/BW9910A is a PWM high-efficiency LED
driver control IC. It allows efficient operation of high
brightness (HB) LEDs from voltage sources ranging from
85VAC up to 265VAC. The BW9910/BW9910A controls an
external MOSFET at fixed switching frequency up to
300kHz. The frequency can be programmed using a single
resistor. The LED string is driven at constant current rather
than constant voltage, thus providing constant light output
and enhanced reliability. The output current can be
programmed between a few mA and up to more than 1.0A.
The BW9910/BW9910A uses a rugged high voltage
junction isolated process that can withstand an input
voltage surge of up to 500V. Output current to an LED
string can be programmed to any value between zero and
its maximum value by applying an external control voltage
at
the
linear
dimming
control
input
of
the
BW9910/BW9910A. The BW9910/BW9910A provides a
low-frequency PWM dimming input that can accept an
external control signal with a duty ratio of 0%~100% and a
frequency of up to a few kHz.
The BW9910A allows wider range of external MOSFET
which has lower RDS(ON) (drain-source on resistance) at
higher VGS. The BW9910/BW9910A is available in SOP-8
and SO8-EP packages.
Typical Application Circuit
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BW9910/A High Brightness LED Driver
Pin Assignments and Ordering Information
Device
VCS Tolerance
Packaging
Quantity of Tape & Reel
BW9910 MST
±10%
SOP-8
3000
BW9910 MPT
±10%
SO8-EP
3000
BW9910A MST
±10%
SOP-8
3000
BW9910A MPT
±10%
SO8-EP
3000
Pin Descriptions
SOP-8
SO8-EP
Pin Name
1
1
VIN
2
2
CS
3
3
GND
4
4
GATE
Function
Input voltage pin.
DC input supply voltage.
Current sensing input pin.
Senses LED string current.
Ground pin.
Device ground.
Gate driver output pin.
Drives the gate of the external MOSFET.
PWM dimming input pin.
5
5
PWM_D
Low frequency PWM dimming pin, also enable input. Internal 200kΩ pull-down
resistor to GND.
Internal/External supply voltage pin.
6
6
VDD
7
7
LD
8
8
ROSC
N/A
EP
EP Pad
Internally regulated supply voltage. 7.5V nominal for the BW9910 and 10V
nominal for the BW9910A. This pin can supply up to 1.0mA for external circuitry. A
sufficient storage capacitor is used to provide storage when the rectified AC input
is near the zero crossings.
Linear dimming input pin.
© 2012 Bruckewell Technology Corp., Ltd.
Linear dimming by changing the current limit threshold at current sensing
comparator.
Oscillator control pin.
A resistor connected between this pin and GND sets the PWM frequency.
Exposed pad.
Package bottom. Connect to GND directly underneath the package.
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BW9910/A High Brightness LED Driver
Absolute Maximum Ratings (Note 1)
Symbol
Parametar
Ratings
Unit
VINDC
DC input supply voltage range, VIN to GND
-0.5 ~ +520
V
VCS
CS input pin voltage range relative to GND
-0.3 ~ +0.45
V
VLD
LD input pin voltage range relative to GND
-0.3 ~ +(VDD + 0.3)
V
VPWM_D
PWM_D input pin voltage range relative to GND
-0.3 ~ +(VDD + 0.3)
V
VGATE
GATE output pin voltage range relative to GND
-0.3 ~ +(VDD + 0.3)
V
8 Pin SO (de-rating 6.3mW/°C above +25°C)
0.63
W
8 Pin SO-EP (de-rating 16mW/°C above +25°C)
1.6
W
+150
°C
-65 ~ +150
°C
Junction-to-ambient thermal resistance for SOP-8
165
°C/W
Junction-to-ambient thermal resistance for SO8-EP
60
°C/W
Continuous power dissipation (TA +25°C)
TJ
Junction temperature
TSTG
Storage temperature range
θJA
θJA(EP)
Note :
1. Exceeding these ratings could cause damage to the device. All voltages are with respect to ground. Currents are positive into,
negative out of the specified terminal.
Recommended Operating Conditions
Symbol
VINDC
Parametar
DC input supply voltage range, VIN to GND
Min.
Max.
BW9910
15
500
BW9910A
20
500
Unit
V
VEN(LO)
PWM_D input pin low voltage range relative to GND
0
1.0
V
VEN(HI)
PWM_D input pin high voltage range relative to GND
2.4
VDD
V
BW9910 MST
-40
+85
°C
BW9910 MPT
-40
+105
°C
TA
TA(EP)
Ambient temperature range for SOP-8 package
(Note 2)
Ambient temperature range for SO8-EP package
(Note 2)
Note :
2. Maximum ambient temperature range is limited by allowable power dissipation. The exposed pad SO8-EP with its lower thermal
impedance allows the variants using this package to extend the allowable maximum ambient temperature range.
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BW9910/A High Brightness LED Driver
Electrical Characteristics
(Over recommended operating conditions unless otherwise specified. TA +25°C)
Parameter
Symbol
Input DC supply voltage range
VINDC
Shut down mode supply
current
IINSD
Internally regulated voltage
VDD
Min.
Typ.
Max.
15
500
20
500
0.5
1.0
0.65
1.20
7.0
7.5
8.0
9.5
10.0
11.0
Unit
Condition
BW9910
V
mA
V
BW9910A
DC input voltage
BW9910
Pin PWM_D to GND,
(Note 3)
BW9910A VIN VINDC(MIN)
VIN VINDC(MIN) ~ 500V
(Note 3)
, lDD(EXT) 0, GATE
BW9910A pin open
BW9910
BW9910
VDD current available for
(Note 4)
external circuitry
IDD(EXT)
VDD under voltage lockout
threshold
VUVLO
VDD under voltage lockout
hysteresis
∆VUVLO
PWM_D pull-down resistance
RPWM_D
150
200
250
kΩ
VCS
225
250
275
mV
GATE high output voltage
VGATE(HI)
VDD - 0.3
VDD
V
IOUT 10mA
GATE low output voltage
VGATE(LO)
0
0.3
V
IOUT -10mA
fOSC1
20
26
32
fOSC2
80
100
120
Current sensing pull in
threshold voltage
Oscillator frequency
Maximum oscillator PWM duty
cycle
Linear dimming pin voltage
range
1.0
6.4
6.7
7.0
8.4
9.0
9.6
500
VLD
0
Current sensing blanking
interval
tBLANK
160
Delay from CS trip to GATE
low
tDELAY
250
V
mV
650
DMAX(HF)
mA
kHz
BW9910A
BW9910
BW9910A
BW9910
BW9910A
VIN VINDC(MIN) ~ 100V
(Note 3)
VDD rising
VDD falling
VPWM_D 5V
Full ambient temperature range
(Note 5)
ROSC 1MΩ
ROSC 226kΩ
fPWM(HF) 25kHz, at GATE, CS tie to
GND.
100
%
250
mV
Full ambient temperature range
(Note 5)
, VIN 20V
440
ns
VCS 0.5V
300
ns
VIN 20V, VLD 0.15V, VCS 0V ~
0.22V after tBLANK
GATE output rise time
tRISE
30
50
ns
CGATE 500pF
GATE output fall time
tFALL
30
50
ns
CGATE 500pF
Thermal shut down
TSD
150
°C
∆TSD
50
°C
Thermal shut down hysteresis
Note :
3. VINDC(MIN) for the BW9910 is 15V and for the BW9910A it is 20V.
4. Also limited by package power dissipation limit, whichever is lower.
5. Full ambient temperature range for BW9910 MST and BW9910A MST is -40 to +85°C; for BW9910 MPT and BW9910A MPT is 40 to +105°C.
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BW9910/A High Brightness LED Driver
Functional Block Diagram
© 2012 Bruckewell Technology Corp., Ltd.
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BW9910/A High Brightness LED Driver
Application Information
AC-DC Off-Line Application
The BW9910/BW9910A is a low cost off-line buck or
boost converter control IC specifically designed for driving
multi-LED stings or arrays. It can be operated from either
universal AC line or any DC voltage between 15V and
500V. Optionally, a passive power factor correction circuit
can be used in order to pass the AC harmonic limits set
by EN61000-3-2 class C for lighting equipment having
input power less than 25W. The BW9910/BW9910A can
drive up to hundreds of HB LEDs or multiple strings of HB
LEDs. The LED arrays can be configured as a series or
series/parallel connection. The BW9910/BW9910A
regulates constant current that ensures controlled
brightness and spectrum of the LEDs, and extends their
lifetime, and also allows PWM control of brightness via an
enable (PWM_D) pin.
connected in series with the source terminal of the
MOSFET. The voltage from the sensing resistor is
applied to the CS pin of the BW9910/BW9910A. When
the voltage at CS pin exceeds a peak current sensing
threshold voltage, the gate drive signal terminates, and
the power MOSFET turns off. The threshold is internally
set to 250mV, or it can be programmed externally by
applying voltage to the LD pin. When the soft-start
function is required, a capacitor can be connected to the
LD pin to allow this voltage to ramp at a desired rate,
therefore, assuring that output current of the LED ramps
gradually. Additionally, a simple passive power factor
correction circuit, consisting of 3 diodes and 2
capacitors, can be added as shown in the typical
application circuit diagram of Figure 6.
Supply Current
The BW9910/BW9910A can also control brightness of
LEDs by programming continuous output current of the
LED driver (so-called linear dimming) when a control
voltage is applied to the LD pin.
The BW9910/BW9910A is offered in standard 8-pin SOIC
and SOIC-EP packages.
The BW9910/BW9910A has a built-in high-voltage linear
regulator that powers all internal circuits and can also
serve as a bias supply for low voltage and low power
external circuitry.
LED Driver Operation
The BW9910/BW9910A can control all basic types of
converters, isolated or non-isolated, operating in
continuous or discontinuous conduction mode. When the
gate signal turns on the external power MOSFET, the
LED driver stores the input energy in an inductor or in the
primary inductance of a transformer and, depending on
the converter type, may partially deliver the energy
directly to LEDs. The energy stored in the magnetic
component is further delivered to the output during the
off-cycle of the power MOSFET producing current
through the string of LEDs (Fly-back mode of operation).
When the voltage at the VDD pin exceeds the VUVLO
threshold voltage, the gate drive is enabled. The output
current is controlled by means of limiting peak current in
the external power MOSFET. A current sensing resistor is
© 2012 Bruckewell Technology Corp., Ltd.
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A current of 1.0mA is needed to start the
BW9910/BW9910A. As shown in the block diagram on
page 5, this current is internally generated in the
BW9910/BW9910A without using bulky startup resistors
typically required in the off-line applications. Moreover,
in many applications the BW9910/BW9910A can be
continuously powered using its internal linear regulator
that provides a regulated voltage of 7.5V/10V for all
internal circuits.
Setting Lighting Output
When the buck converter topology of Figure 5 is
selected, the peak CS voltage is a good representation
of the average current in the LED. However, there is a
certain error associated with this current sensing method
that needs to be accounted for. This error is introduced
by the difference between the peak and the average
current in the inductor. For example, if the peak-to-peak
ripple current in the inductor is 150mA, to get a 500mA
LED current, the sensing resistor should be as follows :
0.43Ω
Dimming
Dimming can be accomplished in two ways, separately
or combined, depending on the application. Light output
of the LED can be controlled either by linear change of
its current, or by switching the current on and off while
maintaining it constant. The second dimming method
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BW9910/A High Brightness LED Driver
(so-called PWM dimming) controls the LED brightness by
varying the duty ratio of the output current.
The linear dimming can be implemented by applying a
control voltage from 0 to 250mV to the LD pin. This
control voltage overrides the internally set 250mV
threshold level of the CS pin and programs the output
current accordingly. For example, a potentiometer
connected between VDD and ground can program the
control voltage at the CS pin. Applying a control voltage
higher than 250mV will not change the output current
setting. When higher current is desired, select a smaller
sensing resistor.
Power Factor Correction
When the input power to the LED driver does not
exceed 25W, a simple passive power factor correction
circuit can be added to the BW9910/BW9910A typical
application circuit in Figure 2 in order to pass the AC line
harmonic limits of the EN61000-3-2 standard for class C
equipment. The typical application circuit diagram shows
how this can be done without affecting the rest of the
circuit significantly. A simple circuit consisting of 3
diodes and 2 capacitors is added across the rectified AC
line input to improve the line current harmonic distortion
and to achieve a power factor greater than 0.85.
Inductor Design
The PWM dimming scheme can be implemented by
applying an external PWM signal to the PWM_D pin. The
PWM signal can be generated by a microcontroller or a
pulse generator with a duty cycle proportional to the
amount of desired light output. This signal enables and
disables the converter modulating the LED current in the
PWM fashion. In this mode, LED current can be in one of
the two states: zero or the nominal current set by the
current sense resistor. It is not possible to use this
method to achieve average brightness levels higher than
the one set by the current sense threshold level of the
BW9910/BW9910A. By using the PWM control method of
the BW9910/BW9910A, the light output can be adjusted
between zero and 100%. The accuracy of the PWM
dimming method is limited only by the minimum gate
pulse width, which is a fraction of a percentage of the low
frequency duty cycle. PWM dimming of the LED light can
be achieved by turning on and off the converter with low
frequency 50Hz to 1kHz TTL logic level signal.
Programming Operating Frequency
The operating frequency of the oscillator is programmed
between 25kHz and 300kHz using an external resistor
connected to the ROSC pin.
Equation :
The buck circuit is usually selected and it has two
operation modes: continuous and discontinuous
conduction modes. A buck power stage can be designed
to operate in continuous mode for load current above a
certain level usually 15% to 30% of full load. Usually, the
input voltage range, the output voltage and load current
are defined by the power stage specification. This
leaves the inductor value as the only design parameter
to maintain continuous conduction mode. The minimum
value of inductor to maintain continuous conduction
mode can be determined by the following example.
Referring to the typical buck application circuit in Figure
5, the value can be calculated from the desired peak-topeak LED ripple current in the inductor. Typically, such
ripple current is selected to be 30% of the nominal LED
current. In the example given here, the nominal current
ILED is 350mA. The next step is to determine the total
voltage drop across the LED string. For example, when
the string consists of 10 high brightness LEDs and each
diode has a forward voltage drop of 3.3V at its nominal
current, i.e. the total LED voltage drop VLEDS is 33V.
Equation :
(2)
(3)
(1)
(4)
where fOSC unit is kHz. ROSC unit is in kΩ and shall be
820kΩ ~ 1MΩ for the case of VOUT < 7V because it has to
satisfy the condition of tON > tBLANK. The efficiency can be
improved as well.
© 2012 Bruckewell Technology Corp., Ltd.
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(5)
where ILED unit is Ampere.
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BW9910/A High Brightness LED Driver
Assuming the nominal rectified input voltage VIN
120V 1.414 169V, the switching duty ratio can be
determined as follows :
0.195
(6)
Then, in this example, given the switching frequency,
fOSC 50kHz, the required on-time of the MOSFET
transistor can be calculated as below :
3.91µs
(7)
24µF, a value 33µF/250V can be used.
A passive PFC circuit at the input requires using two
series connected capacitors at the place of calculated
CMIN. Each of these identical capacitors should be rated
for ½ of the input voltage and have twice as much
capacitance.
Enable Function
The BW9910/BW9910A can be turned off by pulling the
PWM_D pin to ground. When the device is disabled, the
BW9910/BW9910A draws quiescent current of less than
1.0mA.
Output Open Circuit Protection
The required minimum value of the inductor is given by :
5.06mH
(8)
Input Bulk Capacitor
An input filter capacitor should be designed to hold the
rectified AC voltage above twice the LED string voltage
throughout the AC line cycle. Assuming 15% relative
voltage ripple across the capacitor, a simplified formula
for the minimum value of the bulk input capacitor is given
by :
Equation :
(9)
When the buck topology is used, and the LED is
connected in series with the inductor, there is no need
for any protection against an open circuit condition in the
LED string. Open LED connection means no switching
and can be continuous. In this case, since the output
voltage will be the same as input voltage, if there is a
capacitor connected across the output, this capacitor
should be able to withstand the peak value of the input
voltage.
Thermal Shut Down
Thermal protection is added due to buck topology can
generate large heat when operated with high voltage
input. The over temperature protection is activated to
shut down external MOSFET when the junction
temperature (TJ) reaches 150°C. There is a 50°C
hysteresis to re-start the MOSFET.
DC-DC Low Voltage Applications
where
DCH : CIN capacity charge work period, generally about
0.20 ~ 0.25,
fL : input frequency for full range (85VRMS ~ 265VRMS),
∆VDC(MAX) should be set 10% ~ 15% of
Boost LED Driver
If the capacitor has a 15% voltage ripple then a simplified
formula for the minimum value of the bulk input capacitor
approximates to :
Refer to Figure 1, a boost LED driver is used when the
total voltage drop of the output LED string is higher than
the input supply voltage. For example, the boost
topology can be appropriate when input voltage is
supplied by a 48V power supply and the LED string
consists of twenty HB LEDs, as the case may be for a
street light.
(10)
© 2012 Bruckewell Technology Corp., Ltd.
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BW9910/BW9910A can also be used in boost
configurations – at reduced accuracy. The accuracy can
be improved by measuring the LED current with an OpAmp and use the Op Amp’s output to drive the LD pin.
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BW9910/A High Brightness LED Driver
In a boost converter, when the external MOSFET is ON
the energy is stored in the inductor which is then
delivered to the output when the external MOSFET
switches OFF. If the energy stored in the inductor is not
fully depleted by the next switching cycle (continuous
conduction mode) the DC conversion between input and
output voltage is given by :
(11)
From the switching frequency, fOSC, the on-time of the
MOSFET can be calculated :
(12)
Buck-Boost (Fly-Back) LED Driver
Refer Figure 2, the buck-boost power conversion
topology can be used when the forward voltage drop of
the LED string is higher, equal or lower than the input
supply voltage. For example, the buck-boost topology
can be appropriate when input voltage is supplied by
24V system bus for trucks (voltage at supply battery is
between 18V and 32V) and output string consists of six
to nine HB LEDs, as the case may be for tail and break
signal lights.
In the buck-boost converter, the energy from the input
source is first stored in the inductor or fly-back
transformer when the switching transistor is ON. The
energy is then delivered to the output during the OFF
time of the transistor. When the energy stored in the flyback inductor is not fully depleted by the next switching
cycle (continuous conduction mode) the DC conversion
between input and output voltage is given by :
From this the required inductor value can be determined
by :
(13)
(14)
or
D
The boost topology LED driver requires an output
capacitor to deliver current to the LED string during the
time that the external MOSFET is on. In boost LED driver
topologies if the LEDs should become open circuit,
damage may occur to the power switch and so some form
of detection should be present to provide over-voltage
detection/protection.
(15)
The output voltage can be either higher or lower than
the input voltage, depending on duty ratio.
Let us discuss the above example of 24V battery system
LED driver that needs to drive six HB LEDs (VF 3.3V)
at 350mA.
Figure 1. DC-DC Boost LED Driver
Knowing the nominal input voltage VIN
24V, the
nominal duty ratio can be determined as below :
D
0.45
Then, given the switching frequency, in this example
fOSC 50kHz, the required on-time of the MOSFET
transistor can be calculated :
9µs
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BW9910/A High Brightness LED Driver
The required minimum value of the inductor is given by :
2.05mH
So, use 2.2mH
Output Capacitor
Unlike the buck topology, the buck-boost converter
requires an output filter capacitor to deliver power to the
LED string during the ON time of the MOSFET.
In order to reduce the current ripple on the LED, this
capacitor must have impedance that is much lower than
the dynamic impedance ROUT of the LED string. If we
assume ROUT 3Ω in our example, in order to attenuate
the switching ripple by a factor of 10, a capacitor with
equivalent series resistance (ESR) of 0.3Ω is needed. A
chip SMT tantalum capacitor can be selected for this
purpose.
Figure 2. DC-DC Buck-Boost LED Driver
(BW9910 for 24V Battery System)
Buck LED Driver
The buck power conversion topology can be used when
the LED string voltage is needed to be lower than the
input supply voltage. The design procedure for a buck
LED driver outlined in the previous sections can be
applied to the low voltage LED drivers as well. However,
the designer must keep in mind that the input voltage
must be maintained higher than 2 times the forward
voltage drop across the LEDs. This limitation is related to
the output current instability that may develop when the
BW9910/BW9910A buck converter operates at a duty
cycle greater than 0.5. This instability reveals itself as an
© 2012 Bruckewell Technology Corp., Ltd.
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oscillation of the output current at a sub-harmonic of the
switching frequency.
Benefiting from the BW9910/BW9910A inherited high
voltage feature, rectified DC high voltage (VDC
VAC 1.414) can be directly fed into power pin to achieve
high duty cycle, which is only limited by VOUT / VIN, to
optimize design efficiency. This solution can easily
achieve above 90% efficiency. However, if the duty
cycle is configured to reach above more than 50%,
some instability called sub-harmonics oscillation (SBO)
will occur.
The best solution is to adopt the so-called constant offtime operation as shown in Figure 4 and 6. To set
operating frequency, the resistor (ROSC) is connected to
ground by default. This resistor can alternatively be
connected to gate of MOSFET to force the
BW9910/BW9910A to enter constant off-time mode
which will decrease duty cycle from 50% by increase
total period, tON + tOFF. Normally, fixed frequency design
is chosen as shown in Figure 3 because it has better
efficiency.
For general LED lighting application, PFC becomes a
necessary factor in order to meet the international
standard of solid state lighting. If passive valley-fill PFC
is chosen, then the BW9910/BW9910A is biased right
after passive PFC stage.
The DC voltage rail VIN, is halved and it will easily create
a more than 50% duty cycle for the same LED loading
due to VOUT / VIN ratio is doubled. A SBO noise can be
generated. In this case, the constant off-time mode as
shown in Figure 6 should be chosen.
Example :
VIN : VAC 110V with passive PFC
VOUT : Consisting of 1W HB LED with nominal VF 3.3V
VIN(MIN) : After rectified and passing PFC stage, the
actual DC rail will become
VIN(MIN) 110V 1.414 / 2 77.7VDC
The duty cycle, D VOUT / VIN(MIN), will reach above 50%
when voltage drop of LED string, as the VOUT is more
than 77.7/2
38.8V. Another word, if any string
consisting of 38.8/3.3 12 LEDs in a series, SBO will
occur.
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BW9910/A High Brightness LED Driver
In this case, the resistor (ROSC) should be connected
between pin 8, ROSC, and pin 4, GATE to set the
BW9910/BW9910A operate in constant off-time mode to
avoid SBO.
Figure 3. Fixed Frequency Mode
Figure 4. Constant Off-Time Mode
Figure 5. Typical Application Circuit without PFC in Fixed Frequency Mode
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BW9910/A High Brightness LED Driver
Figure 6. Typical Application Circuit with Valley-Fill PFC in Constant Off-Time mode
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BW9910/A High Brightness LED Driver
Package Outline Dimensions
Package Type : SOP-8 / SO8-EP
Marking Information
SOP-8
SO8-EP
SOP-8
SO8-EP
BW9910
XYYWWZ
BW9910
XYYWWZ
BW9910A
XYYWWZ
BW9910A
XYYWWZ
X = A/T Site, YY = Year, WW = Working Week, Z = Device Version
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BW9910/A High Brightness LED Driver
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Bruckewell# Technology# Inc.,# its# affiliates,# agents,# and# employees,# and# all# persons# acting# on# its# or# their#
behalf# (collectively,# “Bruckewell”),# disclaim# any# and# all# liability# for# any# errors,# inaccuracies# or#
incompleteness#contained#in#any#datasheet#or#in#any#other#disclosure#relating#to#any#product.#
Bruckewell#makes#no#warranty,#representation#or#guarantee#regarding#the#suitability#of#the#products#for#
any#particular#purpose#or#the#continuing#production#of#any#product.#To#the#maximum#extent#permitted#by#
applicable#law,#Bruckewell#disclaims##
(i)#Any#and#all#liability#arising#out#of#the#application#or#use#of#any#product.#
(ii)# Any#and#all#liability,#including#without#limitation#special,#consequential#or#incidental#damages.#
(iii)# Any# and# all# implied# warranties,# including# warranties# of# fitness# for# particular# purpose,# nonV
infringement#and#merchantability.#
#
Statements#regarding#the#suitability#of#products#for#certain#types#of#applications#are#based#on#Bruckewell’s#
knowledge#of#typical#requirements#that#are#often#placed#on#Bruckewell#products#in#generic#applications.##
Such#statements#are#not#binding#statements#about#the#suitability#of#products#for#a#particular#application.#It#
is#the#customer’s#responsibility#to#validate#that#a#particular#product#with#the#properties#described#in#the#
product# specification# is# suitable# for# use# in# a# particular# application.# Parameters# provided# in# datasheets#
and/or#specifications#may#vary#in#different#applications#and#performance#may#vary#over#time.##
Product#specifications#do#not#expand#or#otherwise#modify#Bruckewell’s#terms#and#conditions#of#purchase,#
including#but#not#limited#to#the#warranty#expressed#therein.#
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