AND9173/D A 3.3‐V/20‐A Active Clamp DC‐DC Converter with NCP1565 The NCP1565 is a new high-performance voltage or peak-current mode control integrated circuit dedicated to active-clamp forward converters. Designed in a BiCMOS process, the part can switch up to several MHz and offers everything needed to build rugged and cost-effective dc-dc converters for the telecommunication market. Available in a QFN package, the part will equally work well with a self-driven synchronous rectified output stage or with dedicated drivers such as the new NCP81178. This application note describes the part implemented in a 3.3-V/20-A quarter brick dc-dc converter implementing self-driven synchronous MOSFETs. http://onsemi.com APPLICATION NOTE vcc (t ) vuvlo (t ) General Description The part initial power is given by a high-voltage current source delivering up to 40 mA as a guaranteed minimum current across the allowed temperature range. Once connected to the input rail, the current source charges the VCC capacitor and lifts its positive terminal to the controller start-up voltage, 9.5 V. At this point, the source turns off and the part begins to initialize. During this short period of time, there are no output pulses. In case VCC falls down to 9.4 V the current source is turned on again and maintains VCC between 9.5/9.4 V in a hysteretic way. This is a so-called Dynamic Self-Supply (DSS) operation. Once all internal flags are cleared, the current source is turned off and the soft-start pin is released. When the soft-start (SS) voltage passes 1.35 V, the main drive output, OUTM, starts to pulse. Please note that OUTA was already pulled high at VCC equals 9.5 V to pre-charge the active clamp P-channel negative bias circuitry. Figure 1 shows a typical power-on sequence in which the UVLO filter delays the switching operations. Please note the DSS mode until the UVLO level gives the green light to pulse. The small leap on the UVLO signal illustrates the hysteresis action. Figure 2 offers a different view of the start-up sequence and in particular, the duty ratio evolution along the soft-start rising voltage. Please note that pulses appear after the SS voltage exceeds 1.35 V. © Semiconductor Components Industries, LLC, 2014 July, 2014 − Rev. 0 voutM (t ) Figure 1. A Typical Power-on Sequence where the UVLO Time Constant Dictates the Moment at which the Part Starts to Pulse voutM (t ) vSS (t ) d (t ) Figure 2. It is Possible to Monitor the Duty Ratio Evolution During the Soft-start Sequence 1 Publication Order Number: AND9173/D AND9173/D In this example, the auxiliary winding takes over after several switching cycles. In case it does not happen, e.g. because the primary-side rectification diode is broken, the current source will reactivate and will maintain the VCC voltage, self-supplying the controller until a proper auxiliary voltage takes over. It is important to insist on power dissipation in this mode as the current absorbed by the high-voltage pin (22) is roughly the average current consumed by the part. This current depends on the part internal consumption and the driver current. The part, alone, consumes around 5 mA. Assume you drive a 50-nC QG MOSFET at a 300-kHz switching frequency. In this case, the current consumed from the driver is I drv + F SW @ Q G + 300k @ 50n + 15 mA Figure 3. This Transient Thermal Resistance can be Used to Check the Peak Power Capability of the QFN Package. TA is 255C for this Chart (eq. 1) which added to the 5-mA consumption makes 20 mA. If the part is biased from a 72-V dc source, the controller will roughly dissipate 1.5 W. Needless to say that in lack of a wide and thick dissipative copper area, the part temperature will quickly rise, potentially destroying the die as the internal shutdown cannot stop the DSS. For a QFN package mounted on a 4-layer PCB together with a 100-mm2 35-mm copper area, the junction-to-ambient thermal resistance is evaluated to 48°C/W. If we consider a maximum junction temperature of 110°C at a 70-°C ambient temperature, the part will be able to dissipate a maximum power of P max + T j,max * T A R qJA + 100 * 70 + 833 mW 48 The chart tells you that a 50-mA average current can be consumed from the 72-V input during 1 s at a 25-°C ambient temperature. From this value, we can rederive the transient thermal resistance obtained from simulation. r(t) + P max V in,max + 0.833 + 11.6 mA 72 + 34.7 oCńW (eq. 4) Now, at a 70-°C ambient temperature, during 1 s, the maximum power the part will safely dissipate is equal to P max + 150 * 70 + 2.3 W 34.7 (eq. 5) or a 32-mA current from the 72-V input line. (eq. 2) The part is able to issue a status via its dual-function dedicated pin, FLT/SDN. When observed, the pin is low to signal a problem or a working sequence in progress. As an example, if the soft-start pin is shorted to ground, all pulses are immediately stopped and the fault is signaled via the assertion of the FLT/SDN pin. This is what you can see in Figure 4. Therefore, a permanent DSS mode is only acceptable when the part enters skip cycle in a deep no-load discontinuous mode (in lack of synchronous rectification for instance) where the total consumption is reduced via hysteretic operation. The total consumption according to Eq. 2 must remain below I DSS,max + 150 * 25 50 m @ 72 (eq. 3) voutM (t ) In case the VCC capacitor is purposely selected of small value, the DSS can be solicited for a few tens of ms until the auxiliary takes over at start up. The peak power dissipated in this mode must remain within the package power dissipation capability. In this case, we need the transient thermal resistance r(t) as plotted in the below chart for TA equals 25°C, a maximum junction temperature of 150°C and an input voltage of 72 V. voutA (t ) vshtdwn (t ) vSS (t ) Figure 4. If the SS Pin is Shorted to Ground, All Pulses are Stopped and the FLT/SDN is Asserted Low to Signal the Fault http://onsemi.com 2 AND9173/D reaching this goal, significantly improving the situation in moderate to light load conditions. Loop control requires current injection in the feedback pin. Injecting current reduces the duty ratio. When this current exceeds 850 mA, the duty ratio hits 0% and the controller skips cycles. With a synchronous rectifier, this situation never happens since the output inductor current remains continuous, even in a no-load situation. The duty ratio will remain almost constant across the load range at a given input voltage. On the opposite, with a classical set of diodes in the secondary side, Discontinuous Conduction Mode (DCM) will happen in light or no-load operation. This situation will naturally induce skip cycle operation in the primary side. In presence of narrow pulses randomly distributed, typical of skip operation, it is very likely that the auxiliary VCC collapses. In this case, the internal DSS will take over and maintain the controller dc supply around 7.5 V. As this operation can last a certain time, it is the designer duty to make sure that the average power dissipation in worst case (high input voltage, highest MOSFET QG ), keeps the controller die temperature below a safe limit. Figure 6 displays a typical operation when skip cycle is entered in no-load (Vin = 36 V, Iout = 0 A) NCP1565 includes a protection against short circuit or overload that is of auto recovery nature. An internal circuitry reconstructs the dc output current by sampling and averaging the primary-side current during the on time. When this voltage image exceeds 300 mV, the capacitor connected to the RES pin (restart), begins to charge with a 20-mA current source. While charging, should the detected fault disappear, e.g. the voltage on the CS pin passes below 300 mV, the 20-mA current source stops and the capacitor is discharged via a 5-mA source to ground. When the fault comes back, charging resumes and the capacitor voltage grows. When touching the 1-V threshold, all pulses stop and the part remains silent for 32 charge/discharge cycles of the RES capacitor. This is what Figure 5 illustrates. At the end of the 32 cycles, the part attempts to re-start but if the fault it still present, hiccup continues. Should the fault disappear, the converter will resume operations. voutM (t ) voutA (t ) outM (t ) 32 cycles vRES (t ) outA (t ) 1V 7.5 V Figure 5. The Part Enters a Safe Auto-recovery Hiccup Mode when a Fault is Detected vcc (t ) The controller also hosts a pulse-by-pulse current limit set to 450 mV which terminates a pulse in progress in case this limit is exceeded. Finally, in case an overcurrent is sensed for two consecutive clock cycles, e.g. because the secondary-side winding is accidentally shorted, the part immediately stops and enters the auto-restart mode. An important feature of NCP1565 lies in its capability to adjust the dead time in relationship to the load and the input voltage. As the load is getting lighter, the dead time will expand to help reach quasi ZVS at turn on. At full load, it is difficult to switch on again at a drain voltage below Vin . This is because the magnetizing current conflicts with the reflected output current N.iL (t) that appears in the primary side as soon as the drain drops below Vin . In light load, however, as Iout has decreased, it is possible to force the drain fall well below Vin . The adaptive dead time helps Figure 6. In Skip Mode, the DSS Takes Over the VCC Rail which Collapses Given Narrow Drive Pulses The Application Circuit We have designed a 500-kHz 36-72-V dc-dc converter delivering 3.3 V with a nominal output current of 20 A. Over current cutoff happens at Iout is 25 A in our prototype. The board is laid out to a quarter brick dimensions and its electric plugs are compatible with off-the-shelf modules. The primary side section appears in Figure 7 while the secondary side is drawn in Figure 8. http://onsemi.com 3 AND9173/D D2a BAV23CL L3 660uH Vcc 2 DO1606CT−684 DUAL SOT23 C31 1uF Mill−Max R6 3104−2−00−80−00−00−08−0 10 Vin 5 4 MSS1038−152NL L1 1.5uH C1 C2 C3 C4 R1 51k Group of components close to the IC J1b 29 EN Mill−Max 3104−2−00−80−00−00−08−0 J3a J3b J1c 0V 1 1. 2 C1210C225M1RACTU C1210C225M1RACTU C1210C225M1RACTU C1210C225M1RACTU J1a 36−75 V + D2b BAV23CL on/off jumper R4 2k R45 10 100 V R3 75k − CS 4 R18 10k R32 7.5 C16 10nF 20 6 7 8 9 10 SS 23 NC 22 21 20 2 17 16 OUTA DT 4 15 PGnd RT 5 NCP1565 R5 13k R8 66k 7 R31 19.8k comp 11 DT limit 63% Vref 8 9 10 11 res NC CS Ref 12 Q2 IRF6217 SO−8 R19 1Meg 200 V 17 Fault 16 14 OUTM D4 MMSD914 Ndrive 14 Vcc 13 Vcc 12 Q1 FDMS2572 Power 56 OTP R16 10k 13 Vref 500 kHz Vref R35 open CS R46 33k 28 R13 12k 25 R17 10k 18 FLT/SD DLMT 3 AGnd 6 C24 C14 390pF 22nF UVLO 19 18 REFA 2 21 Pdrive 27 24 ramp 1 NC .1 C26 26 C13 0.1uF 19 Vin T2 CT02 R39 2.2 R9 1k . 3 R40 2.2 C40 0.1uF 100 V Vsclamp NC 4 22 23 Mill−Max 3104−2−00−80−00−00−08−0 U1 NCP1565 QFN24 7 D8 MMSD914 R10 100 3 . C104 0.1uF C7 1uF close to U1 close to U1 C33 open R11 499 31 Vref D11 Red LED 30 R34 499 C32 C28 C11 C8 1.5nF 10nF 330pF 0.1uF Lit when fault 32 Fault Figure 7. The Primary Side of the Active-clamp Forward Uses a P-channel Transistor The input line first goes through an EMI filter made of a simple damped LC filter. Some resonance can occur at high frequency and potentially affect the transfer function in a wide-bandwidth design. Damping is possible via the addition of a large electrolytic capacitor connected across C1,2,3,4. As its ESR is naturally larger than that of the Multi-Layer Capacitors (MLC), it will provide an efficient natural ac damping. Check that its ESR changes at high temperature are still compatible with the required damping. Damping can also be provided by the parallel resistor R6. The input voltage splits in several paths then: • One goes to the controller VIN pin. It biases the DSS circuitry and provides energy to the chip a) at start up b) when the auxiliary winding disappears in deep DCM. Please note the insertion of a small RC network made of R45C40 that provides additional filtering in case of surge events. • The second undergoes a division by R1/R4 to feed the controller undervoltage lockout pin. You will adjust this level to define the input voltage at which the converter starts to pulse and the level at which it stops. The formulas are as follows: R upper + R lower + • I hyst R upper @ V enable V enable * V off (eq. 6) (eq. 7) For a 34-V turn-on voltage and a turn off at 33 V, the upper and lower resistances (R1 and R4) must respectively be 50 kW and 1.9 kW. Another path is the PWM sawtooth generation. The connection of resistance R3 to the input rail provides natural feedforward operation by modifying C24 charging current on the fly as the input voltage varies. This alters the PWM block small-signal gain and helps getting rid of Vin in the final transfer function dc gain expression. http://onsemi.com 4 V on * V off AND9173/D The secondary side implements a type 3 compensator, directly driving the optocoupler LED whose anode goes to a stable voltage. The auxiliary VCC is provided by a simple bipolar ballast whose role is to provide a regulated rail but also a Vout ac-decoupled feedback bias for the optocoupler LED. Failure to perfectly ac-isolate this point from Vout creates an unwanted fast lane which hampers the phase boost brought by the type 3 arrangement. The bipolar stage brings a first rejection barrier while the added TL431 in active Zener configuration brings rejection further down: the LED ac current must be solely be imposed by the op amp and not by Vout . To extend the crossover frequency, we have purposely compensated the optocoupler pole via R28 and C103. The auxiliary VCC is obtained by a direct rectification of forward and flyback voltages. It is important that this auxiliary supply comes up quickly at power on so that the secondary stage takes the lead immediately and imposes a soft voltage output rise through a soft-start on the op amp reference pin. To the controller left, you find all the timing components such as switching frequency and dead time settings. Board layout around these elements is critical and their grounds must return to the controller analog GND via the shortest path. NCP1565 directly drives one low-rDS(on) MOSFETs Q1. The clamp section is built around a P-channel MOSFET Q2 that is referenced to ground. You could also use an N-channel type and hook it to the upper rail but a more complex driving circuitry would be necessary. The primary-side current sense signal is delivered by transformer T2, further demagnetized by D8 and R18. The auxiliary voltage is provided by a buck converter supplied by the auxiliary winding. Different structures for this auxiliary section can be envisaged without problem. Synchronous rectification is accomplished by paralleling MOSFETs. Active Clamp Forward (ACF) represents the perfect structure for self-driven rectifiers. By forcing the magnetizing current circulation along the entire switching period, the drive voltage is always present in the secondary side. 2.2-W resistances are inserted in series with the gate signal and damp parasitic elements present in the driving path. close to Q5/Q6 gates R29b 2.2 R23a 2.2 3 . 8 SO−8L 5 R24a 10k 1 2 Q3 NTMFS4982NF 4 J2a T520V227M004ATE007 + 3.3 V/30 A J2b 7 C17 R25b 10k C18 C19 R47 130 C20 S+ Sense + Mill−Max 3104−2−00−80−00−00−08−0 C100 1nF 21 close to Q5/Q6 Q6 NTMFS4982NF SO−8L R101 2.2 close to Q3/Q4 SO−8L R100 2.2 6 R25a 10k R24b 10k 9 220 uF Kemet x 4 Payton Q5 NTMFS4982NF R23b 2.2 Mill−Max 3231−2−00−01−00−00−08−0 L2 0.5uH R29a 2.2 T520V227M004ATE007 T520V227M004ATE007 T520V227M004ATE007 Power GND J2c Mill−Max 3104−2−00−80−00−00−08−0 22 C101 1nF R2 10 ac sweep connections A Q4 NTMFS4982NF SO−8L Trim 23 B Mill−Max 3104−2−00−80−00−00−08−0 8 S− Sense − C41 12nF U4 LM8261 0.22uF / 200 V Kemet C25 0.33uF J2d close to op amp R20 82 R30 1.5k R33 10k 9 17 C103 10nF R21 162 Vcc 18 16 R28 910 C15 10nF 13 R14 22k sec. SS C6 0.1uF close to U4 Vcc 12 19 Quiet GND SOT−23 Q7 2N2222 R15 0 14 C37 0.1uF 16V 7 to 12 V Mill−Max 3231−2−00−01−00−00−08−0 11 C29 47nF R22 1k VEE D9 MMSD914 Vcc 4.3 V 20 D3 MBR130TG R26 270 D6 MBR130TG R7 10k R36 270 25 C38 0.1uF C10 0.1uF 2.45 V C9 C99 0.1uF 1nF 24 D1 1N751 1 2 U5 LM4041DIM3−1.2 SOT−23 R27 10 C5 NC Quiet GND U3 TL431QDBVR SOT−23 Figure 8. The Secondary Side Implements a Dual Op Amp with a Separate Reference Voltage http://onsemi.com 5 0V RTN J2e 10 VCC Power GND − R12 13 AND9173/D For a monotonic output voltage rise, capacitor C6 and resistance R14 soft-start the reference voltage at pin (+) of U4. This forces the secondary side to take over control during the start-up sequence and impose the output voltage shape via this network. This is the reason why the auxiliary VCC must come up quickly, hence a rather low value for C37. PCB routing distinguishes two grounds, noisy and quiet ones, via the 0-W series resistor R15. Reference 1 gives details on how to compensate the op amp for a particular crossover frequency selection. Operational Results These components have been assembled on a quarter brick 6-layer PCB whose pictures appears in Figure 9. Figure 9. The 100-W Converter Fits in a Compact 6-layer Quarter Brick PCB Size Below are some operational oscilloscope shots captured at different bias points: vout(t) vout(t) Figure 11. Start-up Sequence at a 0-A Output Current, Vin is 48 V Figure 10. Start-up Sequence at a 20-A Output Current, Vin is 48 V vout (t ) vout (t ) 20mV 40mV Vin = 36 V, Iout = 15 to 20 A, 1 A/ms Vin = 48 V, Iout = 15 to 20 A, 1 A/ms Figure 12. Transient Response for Two Different Configurations, Low and Nominal Line http://onsemi.com 6 AND9173/D vDS (t ) outM (t ) DT 2 DT 1 outA (t ) Figure 13. The Adaptive Dead Time Helps Obtain Quasi-ZVS at a Low Operating Current. Vin = 72 V, Iout = 3 A Efficiency results appear below for a constant output current of 20 A: Vin = 36 V η = 90.88% Vin = 48 V η = 90.65% Vin = 72 V η = 88.65% éT ( f ) T (f ) f m = 60 f c = 30kHz Figure 14. Open-loop AC Sweep at a 36-V Input Voltage. A 30-kHz Crossover Frequency is Measured Together with a 605 Phase Margin Reference Several open-loop measurements have been performed on this board using the series resistance R2 across which an ac signal is injected. One typical result at a 36-V input voltage is given in Figure 14 where a comfortable crossover frequency of 30 kHz is observed. The phase margin is also good with 60° with the absence of conditional stability zones. The author wishes to thank Payton and ICE Components for kindly providing samples for power magnetics and the current sense transformer. [1] Christophe Basso, “Designing Control Loops for Linear and Switching Power Supplies: A Tutorial Guide”, Artech House, Boston 2012, ISBN-13: 978-1-60807-557-7 [2] http://www.paytongroup.com/ [3] http://www.icecomponents.com/ http://onsemi.com 7 AND9173/D PCB ASSEMBLY Figure 15. Primary-side Components Assembly Figure 16. Secondary-side Components Assembly http://onsemi.com 8 AND9173/D Figure 17. Primary-side Layer 1 Figure 18. Layer 2, Ground Plane http://onsemi.com 9 AND9173/D Figure 19. Layer 3, Ground Plane Figure 20. Layer 4, Signal Plane http://onsemi.com 10 AND9173/D Figure 21. Layer 5, Signal Plane Figure 22. Layer 6, Secondary Side http://onsemi.com 11 AND9173/D BILL OF MATERIALS Table 1. BILL OF MATERIALS Substitution Allowed Designator Qty. Description Value Rating Footprint Manufacturer Part Number C7, C31 2 Capacitor 1 mF 20 V 805 Yageo CC0805KKX5R8BB105 Yes C26 1 Capacitor 0.22 mF 200 V 1210 TDK CGA6M3X7R2E224K200 AA No Tolerance C27 1 Capacitor 2200 pF 2 kV 1812 TDK C4532X7R3D222K No C1, C2, C3, C4 4 Capacitor 2.2 mF 100 V 1210 Kemet C1210C225M1RACTU No C17, C18, C19, C20 4 Capacitor 220 mF 6.3 V − Kemet T520V227M004ATE007 No C6, C8, C9, C13, C37, C38, C40, C104, C10 9 Capacitor 0.1 mF 50 V 0603 Yageo CC0603MRX7R9BB104 Yes C32 1 Capacitor 1.5 nF 16 V 0603 Yageo CC0201KRX7R7BB152 Yes C15, C16, C28, C103 4 Capacitor 10 nF 16 V 0603 Yageo CC0201KRX7R7BB103 Yes 16 V 0603 Yageo CC0603KRX7R7BB334 Yes 16 V 0603 Yageo CC0603KRX7R7BB102 Yes 16 V 0603 Yageo CC0603KRX7R7BB223 Yes C25 1 Capacitor 330 nF C99, C100, C101 3 Capacitor 1 nF C14 1 Capacitor 22 nF 5% 5% C11 1 Capacitor 330 pF 16 V 0603 Yageo CC0201KRX7R7BB331 Yes C24 1 Capacitor 390 pF 5% 50 V 0603 Yageo CC0603GRNPO9BN391 Yes C41 1 Capacitor 12 nF 5% 25 V 0603 Yageo CC0603KRX7R8BB123 Yes 16 V 0603 Yageo CC0603KPX7R7BB473 Yes − − − − Yes − − Coilcraft DS3316P-152MLB No C29 1 Capacitor 47 nF C23, C33 2 Capacitor Open L1 1 Inductor 1.5 mF L3 1 Inductor 680 mF − − Coilcraft DO1606CT-684 No L2 1 Inductor 0.5 mF 30 A − Payton 56846 No R19 1 Resistor 1 MW 5% 200 V 1206 Yageo RV1206FR-071ML Yes R6 1 Resistor 10 W 5% 150 V 805 Yageo RC0805FR-7W10RL Yes R47 1 Resistor 130 W 5% 150 V 805 Yageo RC0805FR-7W130RL Yes R39, R40, RR100, R101 4 Resistor 2.2 W 5% 150 V 805 Yageo RC0805FR-072R2L Yes R32 1 Resistor 7.5 W 1% 150 V 805 Yageo RC0805FR-077R5L Yes − R15 1 Resistor 0W 5% 50 V 603 Yageo AC0603JR-070RL Yes R23A, R23B, R29A, R29B 4 Resistor 2.2 W 5% 50 V 603 Yageo RC0603FR-072R2L Yes R2, R27, R45 3 Resistor 10 W 5% 50 V 603 Yageo RC0603FR-0710RL Yes R12 1 Resistor 12 W 1% 50 V 603 Yageo RC0603FR-0712RL Yes R20 1 Resistor 82 W 1% 50 V 603 Yageo RC0603FR-0782RL Yes R10 1 Resistor 100 W 5% 50 V 603 Yageo RC0603FR-07100RL Yes R21 1 Resistor 162 W 1% 50 V 603 Yageo RC0603FR-07162RL Yes R26, R36 2 Resistor 270 W 5% 50 V 603 Yageo RC0603FR-07270RL Yes R11, R34 2 Resistor 499 W 1% 50 V 603 Yageo RC0603FR-07499RL Yes R28 1 Resistor 910 W 1% 50 V 603 Yageo RC0603FR-13910RL Yes R9, R22 2 Resistor 1 kW 5% 50 V 603 Yageo RC0603FR-071KL Yes R30 1 Resistor 1.5 kW 1% 50 V 603 Yageo RC0603FR-071K5L Yes R4 1 Resistor 2 kW 1% 50 V 603 Yageo RC0603FR-072KL Yes http://onsemi.com 12 Comments 2% Planar 0-W res. AND9173/D Table 1. BILL OF MATERIALS (continued) Substitution Allowed Designator Qty. Description Value Tolerance Rating Footprint Manufacturer Part Number R7, R16-18, R33, R24A, R24B, R25A, R25B 9 Resistor 10 kW 5% 50 V 603 Yageo RC0603FR-0710KL Yes R13 1 Resistor 12 kW 5% 50 V 603 Yageo RC0603FR-0712KL Yes R5 1 Resistor 13 kW 1% 50 V 603 Yageo RC0603FR-0713KL Yes R31 1 Resistor 19.6 kW 1% 50 V 603 Yageo RC0603FR-0719K6L Yes R14 1 Resistor 22 kW 5% 50 V 603 Yageo RC0603FR-0722KL Yes R1 1 Resistor 51 kW 1% 100 V 603 Yageo RV0603FR-0751KL Yes R8 1 Resistor 66.5 kW 1% 50 V 603 Yageo RC0603FR-0766K5L Yes Yes Comments R3 1 Resistor 75 kW 1% 100 V 603 Yageo RV0603FR-0775KL R35 1 Resistor Open − − − − − Yes R46 1 Resistor 33 kW NTC − 603 AVX NB 21 M 0 0333 33 k @25°C Thermistor LED1 1 LED Red LED − LED0805 ROHM TLMS1000GS08 No SMD Type Flat Lead Q1 1 MOSFET FDMS2572 150 V CASE488AA Fairchild FDMS2572 No Q3-Q6 1 MOSFET NTMFS4982 30 V CASE488AA ON Semiconductor NTMFS4982NFT1G No Flat Lead Q2 1 MOSFET IRF6217 150 V SO8 International Rectifier IRF6217TRPBF No P-channel Q7 1 Bipolar MMBT2222 SOT23 ON Semiconductor MMBT2222ALT1 No NPN D1 1 Zener Diode MMSZ4689 SOD-123 ON Semiconductor MMSZ4689T1G No D2 1 Diode BAV23CL SOD-123 ON Semiconductor BAV23CLT1G No D4, D8, D9 3 Diode MMSD914 SOD-123 ON Semiconductor MMSD914 No D3, D6 2 Diode MBR130T1G SOD-123 ON Semiconductor MBR130T1G No J1, J2, J3, J5, J6, J7 6 Pin PLOT 1 mm 3104_ LOPOWER MILL-MAX 3104-1-00-80-00-00-08-0 No J4, J8 2 Pin (Power) PLOT 2 mm 3231_ POWER MILL-MAX 3231-2-00-01-00-00-08-0 No JP1 1 Jumper TMM102-0XX-S-SM JUMP TMM-SM Samtec TMM102-01-L-S-SM No JP1 1 Jumper Harwin M22-1920005 No T1 1 Transformer 500 mH − Payton 56847 No T2 1 Current Sense CT02-100 − ICE CT02 U1 1 Controller NCP1565 QFN24 ON Semiconductor NCP1565 U2 1 Optocoupler PS2801 SMD NEC PS2801 U3 1 IC TL431 SOT23 TI TL431ACDBZT U4 1 Op Amp LM8261M5 TSOP-5 TI LM8261M5 U5 1 Reference LM4041-1.2 SOT23 TI LM4041DIM3-1.2 15 A 30 A NOTE: All devices are Pb-Free http://onsemi.com 13 AND9173/D ON Semiconductor and the are registered trademarks of Semiconductor Components Industries, LLC (SCILLC) or its subsidiaries in the United States and/or other countries. SCILLC owns the rights to a number of patents, trademarks, copyrights, trade secrets, and other intellectual property. A listing of SCILLC’s product/patent coverage may be accessed at www.onsemi.com/site/pdf/Patent−Marking.pdf. SCILLC reserves the right to make changes without further notice to any products herein. SCILLC makes no warranty, representation or guarantee regarding the suitability of its products for any particular purpose, nor does SCILLC assume any liability arising out of the application or use of any product or circuit, and specifically disclaims any and all liability, including without limitation special, consequential or incidental damages. “Typical” parameters which may be provided in SCILLC data sheets and/or specifications can and do vary in different applications and actual performance may vary over time. All operating parameters, including “Typicals” must be validated for each customer application by customer’s technical experts. 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SCILLC is an Equal Opportunity/Affirmative Action Employer. This literature is subject to all applicable copyright laws and is not for resale in any manner. PUBLICATION ORDERING INFORMATION LITERATURE FULFILLMENT: Literature Distribution Center for ON Semiconductor P.O. Box 5163, Denver, Colorado 80217 USA Phone: 303−675−2175 or 800−344−3860 Toll Free USA/Canada Fax: 303−675−2176 or 800−344−3867 Toll Free USA/Canada Email: [email protected] N. American Technical Support: 800−282−9855 Toll Free USA/Canada Europe, Middle East and Africa Technical Support: Phone: 421 33 790 2910 Japan Customer Focus Center Phone: 81−3−5817−1050 http://onsemi.com 14 ON Semiconductor Website: www.onsemi.com Order Literature: http://www.onsemi.com/orderlit For additional information, please contact your local Sales Representative AND9173/D