202247A.pdf

DATA SHEET
AAT2404
Voltage-Variable Current Sourcing Boost Controller For LED Lighting Applications
General Description
Features
The AAT2404 is a highly integrated high-efficiency variable voltage current sourcing boost controller for white
LED backlight applications intended for use in large size
LCD panels and LCD TVs. To accommodate various LED
backlighting configurations in both direct and edge lighting applications, the device uses a high voltage external
power MOSFET. The AAT2404 contains an integrated current sense architecture eliminating the need for an
expensive low resistance/high accuracy sense resistor.
The device operates ideally from a regulated 12V or 24V
DC power supply, but can also operate over a 10.8V to
28V range.
•
•
•
•
•
•
•
•
•
•
•
•
•
The AAT2404 provides an output voltage up to 100V
regulated by the CSFB pin provided by the ICs in
Skyworks' family of white LED drivers for TV applications.
The CSFB pin is an analog voltage representing the LED
string with the highest voltage requirement. Regulating to
this voltage allows for a wide range of LED characteristics,
while maintaining the lowest possible power dissipation.
The CSFB regulation point can be set by adjusting a resistor to ground from the RSET pin.
VIN Range: 10.8V – 28.0V
Maximum VLED: 100V
Up to 95% Boost Conversion Efficiency
Integrated Current Sense Eliminates Need for Ballast
Resistors
Switching Frequency Options
▪ 400KHz Nominal
▪ Adjustable Range from 100kHz to 800kHz
Adjustable Regulation Voltage
▪ Analog Input from LED Driver
▪ User Adjustable for Fixed Output
Integrated Low Impedance Gate Drive = VCC
Flexible Current Sense Feedback Control
Power OK Output
Integrated Over-Voltage Protection
Soft-Start to Minimize Inrush Current
TQFN34-24 Low Profile Package
-40°C to +85°C Temperature Range
Applications
•
•
•
•
The boost switching frequency is nominally 400kHz to
allow for optimum efficiency with the smallest external
filter. However, the device switching frequency may be
adjusted with an external resistor to optimize system
performance. Current mode control provides fast response
to line and load transients.
Large Size LCD TV, Panels
LCD Monitors
Video Walls
White LED Backlighting
Thermal protection circuitry shuts down the boost converter in the event of an over-temperature condition.
The AAT2404 is available in the Pb-free, thermally
enhanced 24-pin 3 x 4mm TQFN package.
Typical Application
D1
L1
VIN
VCC
VIN = 10.8V to 28V
CIN
CVCC
CC
RC
RFREQ
RSET
GATE LXS
VLED
R1
COUT
OVP
R2
AAT2404
EN
COMP
FREQ
RSET
On/Off Enable Input
Q1
POK
CSFB
Power OK Output
Current Sense Feedback Input
PGND AGND
Skyworks Solutions, Inc. • Phone [781] 376-3000 • Fax [781] 376-3100 • sales@skyworksinc.com • www.skyworksinc.com
202247A • Skyworks Proprietary Information • Products and Product Information are Subject to Change Without Notice. • August 7, 2012
1
DATA SHEET
AAT2404
Voltage-Variable Current Sourcing Boost Controller For LED Lighting Applications
Pin Descriptions
Pin #
Symbol
Function
1, 2, 3,
23, 24
Description
LXS
I
Boost converter current sense node. Connect to the source terminal of the external low resistance power MOSFET to this pin.
4
GATE
O
Output drive pin. Connect directly to the gate terminal of the external low resistance power
MOSFET. The gate voltage range is from 0V to VCC
5
VIN
I
Input power supply.
6
VCC
I/O
7, 8
9
10
AGND
COMP
NC
GND
I
11
CSFB
I
12
FREQ
O
Boost converter PWM switching frequency adjust pin. Connect a RFREQ resistor between this
pin and AGND to set the switching frequency.
13
OVP
I
Over-voltage protection. Connect a resistive divider between VLED, this pin, and ground.
14
RSET
O
Current sink regulation voltage set resistor. Connect the RSET resistor between this pin and
AGND.
15
EN
I
Logic High enable pin. Apply a logic high voltage or connect to VIN to enable the device. Use
a 10kΩ resistor between this pin and AGND to for a logic pull-down to shut the device off
when an enable signal is not applied.
16
POK
O
Open drain output. Connect to LED cathode with the anode connected via a resistor to VCC or
drive an active low logic signal to a system controller. If not used, leave open / not connected.
17, 18, 19,
20, 21, 22
PGND
GND
Power ground.
EP
EP
GND
Exposed paddle. Connect to PCB GND plane. PCB paddle heat sinking should maintain
acceptable junction temperature.
Internally regulated power supply. Decouple with 2.2µF or greater value capacitor between
this pin and AGND.
Analog ground.
Boost converter compensation. Connect external resistor and capacitor to this pin and AGND.
Not connected.
Current sink feedback. When used with compatible Skyworks LED driver devices1, connect
the driver CSFBO output directly to this pin for the current sink feedback from current sink
device.
Pin Configuration
TQFN34-24
(Top View)
PGND
PGND
PGND
LXS
LXS
24
LXS
LXS
LXS
GATE
VIN
VCC
AGND
23
22
21
20
1
19
2
18
3
17
EP
4
5
16
15
6
14
7
13
8
9
10
11
PGND
PGND
PGND
POK
EN
RSET
OVP
12
FREQ
CSFB
N/C
COMP
AGND
1. Compatible Skyworks LED backlight driver products include the AAT2401, AAT2402 and AAT2403.
2
Skyworks Solutions, Inc. • Phone [781] 376-3000 • Fax [781] 376-3100 • sales@skyworksinc.com • www.skyworksinc.com
202247A • Skyworks Proprietary Information • Products and Product Information are Subject to Change Without Notice. • August 7, 2012
DATA SHEET
AAT2404
Voltage-Variable Current Sourcing Boost Controller For LED Lighting Applications
Absolute Maximum Ratings1
Symbol
Description
VIN,EN
VCC
GATE, LXS, POK,
OVP, COMP, RSET,
FREQ, CSFB
TJ
TLEAD
Input Voltage, EN to GND
Low Voltage Pin to GND
GATE, LXS, POK, OVP, COMP, RSET, FREQ, CSFB Voltage to GND
Maximum Junction Operating Temperature
Maximum Soldering Temperature (at leads, 10 sec.)
Value
Units
-0.3 to 32
-0.3 to 6.0
-0.3 to V CC + 0.3
-40 to +150
300
O
C
Thermal Information2
Symbol
θJA
PD
TA
Description
Thermal Resistance3
Maximum Power Dissipation
Operating Temperature Range
Value
50
2.3
-40 to 85
Units
O
C/W
W
O
C
1. Stresses above those listed in Absolute Maximum Ratings may cause permanent damage to the device. Functional operation at conditions other than the operating conditions
specified is not implied. Only one Absolute Maximum Rating should be applied at any one time.
2. Mounted on an FR4 board.
3. Derate 20mW/°C above 25°C.
Skyworks Solutions, Inc. • Phone [781] 376-3000 • Fax [781] 376-3100 • sales@skyworksinc.com • www.skyworksinc.com
202247A • Skyworks Proprietary Information • Products and Product Information are Subject to Change Without Notice. • August 7, 2012
3
DATA SHEET
AAT2404
Voltage-Variable Current Sourcing Boost Controller For LED Lighting Applications
Electrical Characteristics1
VIN = 24V; CIN = 4.7µF, COUT = 4.7µF; CVCC = 2.2µF; L1 = 10µH; RSET =10.2kΩ; TA = -40°C to 85°C unless otherwise
noted. Typical values are at TA = 25°C.
Symbol
Description
Power Supply, Current Sinks
VIN
Input Voltage Range
VCC
Linear Regulator Output Voltage
VUVLO
Under Voltage Threshold
VLED
IQ
ISD
Output Voltage Range
Quiescent Current
VIN Pin Shutdown Current
Over-Voltage Threshold
Over-Voltage Hysteresis
Sense Device ON Resistance
Low Side Switch Current Limit
Oscillator Frequency
Soft-Start
Duty Cycle2
VOVP
RSENSE
ILIMIT
FOSC
TSS
D
Gate Drive
RDS_P
Driver High Side ON Resistance
RDS_N
Driver Low Side ON Resistance
tR
Gate Rise Time
tF
Gate Fall Time
Logic Level Inputs: EN
VI(L)
Input Logic Threshold Low
VI(H)
Input Logic Threshold High
IEN
Input Enable Leakage Currrent
Logic Level Outputs: POK
VPOK(LOW)
POK Logic Output Low
ISINK
POK Logic High Leakage
Thermal Protection
TJ (SD)
TJ Thermal Shutdown Threshold
TJ (HYS)
TJ Thermal Shutdown Hysteresis
Conditions
Min
Typ
10.8
0mA < ILOAD < 15mA
VIN Rising
Hysteresis
VIN Falling
VIN = 10.8V to 28.0V
Not switching
EN = Logic Low
VLED Rising
VLED Falling
RFREQ = 10kΩ
VLED = 35V
RFREQ = 10kΩ
VCC
VCC
VCC
VCC
=
=
=
=
Max
Units
28
V
V
V
mV
V
V
mA
µA
V
mV
mΩ
A
kHz
ms
%
5.0
10
200
8.5
VIN + 3V
1.1
320
5V
5V
5V, CLOAD = 0.5nF
5V, CLOAD = 0.5nF
1
10
1.2
100
60
10
400
1.5
80
1.3
480
2
1
10
10
Ω
ns
ns
0.4
2
V
V
µA
0.4
1
V
µA
2.5
ISINK = -1mA
VPOK = 5.5V
140
15
°C
1. The AAT2404 is guaranteed to meet performance specifications over the -40°C to +85°C operating temperature range and is assured by design, characterization, and correlation with statistical process controls.
2. The boosted output voltage, VLED, cannot exceed 100V.
4
Skyworks Solutions, Inc. • Phone [781] 376-3000 • Fax [781] 376-3100 • sales@skyworksinc.com • www.skyworksinc.com
202247A • Skyworks Proprietary Information • Products and Product Information are Subject to Change Without Notice. • August 7, 2012
DATA SHEET
AAT2404
Voltage-Variable Current Sourcing Boost Controller For LED Lighting Applications
Typical Characteristics
UVLO vs. Temperature
Quiescent Current vs. Temperature
(VIN = 24V; VEN = VIN; Non-switching)
9.8
Quiescent Current (mA)
1.4
9.6
UVLO (V)
9.4
9.2
9.0
8.8
8.6
Rising
8.4
8.2
-40
Falling
-15
10
35
60
1.3
1.2
1.1
1.0
0.9
0.8
0.7
0.6
-40
85
-15
10
Shutdown Current vs. Temperature
85
(VIN = 24V; VLED = 31V; COUT = 20µF; L = 10µH)
16
100
14
96
12
92
Efficiency (%)
Shutdown Current (µA)
60
Efficiency vs. Load Current
(VIN = 24V; VEN = GND)
10
8
6
4
88
84
80
76
72
2
0
-40
35
Temperature (°C)
Temperature (°C)
68
-15
10
35
60
85
Temperature (°C)
0
0.4
0.8
1.2
1.6
2.0
2.4
2.8
3.2
3.6
4.0
Output Current (A)
Input Logic Threshold vs. Temperature
Input Logic Threshold (V)
(VIN = 24V)
1.7
1.6
1.5
1.4
1.3
1.2
1.1
1.0
0.9
-40
Logic Threshold High
Logic Threshold Low
-15
10
35
60
85
Temperature (°C)
Skyworks Solutions, Inc. • Phone [781] 376-3000 • Fax [781] 376-3100 • sales@skyworksinc.com • www.skyworksinc.com
202247A • Skyworks Proprietary Information • Products and Product Information are Subject to Change Without Notice. • August 7, 2012
5
DATA SHEET
AAT2404
Voltage-Variable Current Sourcing Boost Controller For LED Lighting Applications
Typical Characteristics
POK Logic High Leakage vs. Temperature
POK Logic Output Low vs. Temperature
(VIN = 24V; IPOK = -1mA)
Logic Output Low Voltage (mV)
(VIN = 24V; VPOK = 5.5V)
Leakage Current (nA)
80
70
60
50
40
30
20
10
0
-40
-15
10
35
60
85
Temperature (°C)
50
45
40
35
30
25
20
15
10
-40
Current Limit (A)
Frequency Accuracy (%)
11.5
0.5
0.0
-0.5
-1.0
11.0
10.5
10.0
9.5
9.0
8.5
-1.5
-15
10
35
60
8.0
-40
85
-15
10
35
60
Gate Rise and Fall Time vs. CLOAD
(VIN = 24V; VCC = 5V)
80
90
70
Rise/Fall Time (ns)
100
80
70
60
50
40
30
60
50
40
30
20
Rise
Fall
10
0
-15
10
35
Temperature (°C)
60
85
Temperature (°C)
Sense Device On Resistance vs. Temperature
RSENSE (mΩ)
85
12.0
Temperature (°C)
6
60
(VIN = 24V)
(VIN = 24V; fOSC = 400kHz; RFREQ = 10kΩ)
1.0
20
-40
35
Current Limit vs. Temperature
1.5
-2.0
-40
10
Temperature (°C)
Oscillator Frequency Accuracy
vs. Temperature
2.0
-15
85
0.1
1
Capacitance (nF)
Skyworks Solutions, Inc. • Phone [781] 376-3000 • Fax [781] 376-3100 • sales@skyworksinc.com • www.skyworksinc.com
202247A • Skyworks Proprietary Information • Products and Product Information are Subject to Change Without Notice. • August 7, 2012
10
DATA SHEET
AAT2404
Voltage-Variable Current Sourcing Boost Controller For LED Lighting Applications
Functional Block Diagram
VIN
Linear
Regulator
VCC
EN
OVP
GATE
COMP
FREQ
RSET
Logic
and PWM
Control
LXS
I-Precise™
CSFB
POK
AGND
Functional Description
The AAT2404 is a high voltage DC-DC boost converter
that functions as a voltage variable current source that is
designed to complement Skyworks' family of white LED
drivers for TV applications
PGND
Regulating to this voltage allows for a wide range of LED
characteristics, while maintaining the lowest possible
power dissipation for the system. The CSFB regulation
voltage point can be set by adjusting an external resistor
to ground from the RSET pin.
Operating from a 10.8V to 28V input supply range, the
AAT2404 can supply a compliance voltage up to 100V
with the output power limited only by the size and selection of the external switching MOSFET, inductor and
schottky diode. Input voltage sources common to LCD
monitors and TV display panels are 12V or 24V with a
maximum effective switching duty cycle of 80%.
The AAT2404 provides a low gate impedance driver to
minimize the switching losses of the external boost power
MOSFET and can attain boost conversion efficiencies up
to 95%. The boost switching frequency is nominally
400kHz to allow for optimum efficiency with the smallest
external filter. Alternatively, the device switching frequency may be adjusted over a 100kHz to 800kHz range by
an external resistor if required by a specific application.
The AAT2404 uses a unique internal current scheme, and
relies on a current sense feedback loop (CSFB) integrated
into the AAT2401/02S/03 LED driver ICs which eliminates
the need for low resistance, 1% tolerance current sense
resistors for each LED backlight string. The CSFB function
is an analog voltage feedback system that represents the
LED string with the highest voltage requirement.
For reliability and protection of the application system,
the AAT2404 has a thermal protection circuit to shut
down the boost converter in the event of an over-temperature condition. An output over voltage protection
circuit (OVP) constantly monitors the boost output voltage and will terminate the boost switching cycle if the
output exceeds a user set threshold.
Skyworks Solutions, Inc. • Phone [781] 376-3000 • Fax [781] 376-3100 • sales@skyworksinc.com • www.skyworksinc.com
202247A • Skyworks Proprietary Information • Products and Product Information are Subject to Change Without Notice. • August 7, 2012
7
DATA SHEET
AAT2404
Voltage-Variable Current Sourcing Boost Controller For LED Lighting Applications
Input Supply and Control Loop
Current Sink Feedback (CSFB) and RSET
The AAT2404 has specially designed input stages to permit operation and control over a 10.8V to 28V input
range. This device is intended to function as a voltage
variable current source to drive large strings of backlight
LEDs. The system current limit is based on the programming of the downstream LED controller constant current
sinks. The current sink feedback to the AAT2404 maintains a compliance voltage to support the varying
demands based on the LED combined forward voltage at
any given forward current setting.
The AAT2404 utilizes a current sink feedback (CSFB)
function that directly interfaces to Skyworks LED controllers such as the AAT2401, AAT2402S and AAT2403.
When used with these devices, their integrated CSFBO
output can be connected directly to the AAT2404 CSFB
pin. The voltage level of this feedback system represents
the proper regulation point for the LED array to support
a programmed LED drive current. The range of the CSFB
signal should be from 0.5V to 2.5V under normal operating conditions.
The AAT2404 has the benefit of current mode control
with a simple voltage feedback loop providing exceptional stability and fast response with minimal design
effort. The device modulates the external power MOSFET
switching current to maintain the programmed feedback
voltage that is user adjustable via the RSET resistor. The
switching cycle initiates when the N-channel MOSFET is
turned ON and current ramps up in the inductor. The ON
interval is terminated when the inductor current reaches
the programmed peak level. During the OFF interval, the
input current decays until a lower threshold, or zero
inductor current, is reached. The lower current is equal
to the peak current minus a preset hysteresis threshold,
which determines the inductor ripple current. The peak
current is adjusted by the controller until the output voltage requirement of the LED array is met as determined
by the voltage on the CSFB input pin.
The feedback voltage threshold is user adjustable by programming the RSET resistor, simplifying integration with
other Skyworks's devices. The feedback threshold voltage for the AAT2404 should be greater than the current
sink dropout voltage to prevent ILED from going out of
regulation. However if the feedback voltage threshold is
much higher than the dropout voltage, the VLED voltage
will be higher than the optimum voltage required to drive
the white LED strings. This will result in unwanted power
being dissipated by the LED driver. Set the feedback voltage threshold between 10% and 20% higher than the
dropout voltage to maintain current regulation and avoid
excessive power dissipation.
Control Loop Compensation
The COMP pin is the output of the transconductance error
amplifier. The AAT2404 is a current mode boost controller
and as such has eliminated the double pole of the LC filter.
The magnitude of the feedback error signal determines
the average input current to the AAT2404; the internal
control circuit implements a programmed current source
connected to the output capacitor and load impedance.
Regulator stability is achieved with a simple RC compensation network from the COMP pin to ground. If the ESR
of the output capacitor is high, then an additional capacitor in parallel with the RC network may be needed.
8
CSFB Threshold (V)
Operating frequency varies with changes in the input
voltage, output voltage, and inductor size. Once the
boost converter has reached continuous mode, further
increases in the output current will not significantly
change the operating frequency.
1.8
1.6
1.4
1.2
1.0
0.8
0.6
0.4
0.2
0.0
0
5
10
15
20
25
30
RSET (kΩ)
Figure 1: CSFB Threshold vs. RSET
(VIN = 24V, FOSC = 200kHz).
Skyworks Solutions, Inc. • Phone [781] 376-3000 • Fax [781] 376-3100 • sales@skyworksinc.com • www.skyworksinc.com
202247A • Skyworks Proprietary Information • Products and Product Information are Subject to Change Without Notice. • August 7, 2012
35
DATA SHEET
AAT2404
Voltage-Variable Current Sourcing Boost Controller For LED Lighting Applications
When using the AAT2404 in a given application, one
must first determine what the maximum combined LED
string voltage will be at the specified maximum forward
current. The maximum practical operating duty cycle for
the DC-DC boost function is approximately 80%.
The maximum output voltage can be approximated using
Equation 1:
Eq. 1: VLED =
VIN
1-D
value between the FREQ pin and ground. To set a recommend 400kHz switching frequency, the nominal value
RFREQ value is 10kΩ. Refer to Figure 2 for resistor values
to program a specific switching frequency.
1
Frequency (MHz)
Maximum Output Voltage Compliance
Where D = DC-DC boost switching duty cycle.
The AAT2404 has an internal linear regulator to produce
5V from the VIN high voltage input for internal logic,
clock, and control functions. The regulator output is connected to the VCC pin and should be bypassed with a
2.2µF or larger ceramic capacitor. The 5V may be used
as a logic pull-up reference termination for all AAT2404
logic functions such as a pull up for the open drain power
OK (POK) function. This output is not intended to support external loads from circuits other than low current
logic terminations.
IC Enable and Soft Start
An enable pin is provided as a master on/off function that
may be toggled by an external system controller or connected directly to VIN. This is a logic active high function.
If the IC enable is not needed, connect the EN pin to VCC
to turn the AAT2404 on. The slew rate limited turn-on is
guaranteed by the built-in soft-start circuitry. Soft start
eliminates output current overshoot across the full input
voltage range and all load conditions. After the soft start
sequence has terminated, the initial output voltage is
determined by the level sensed on the CSFB pin.
Boost Converter Switching Frequency
The AAT2404 is designed to operate over a wide input to
output voltage range with a nominal 400kHz switching
frequency. However, if a specific system or application
demands a different operating switching frequency, the
frequency can be user adjusted by changing the resistor
0.6
0.4
0.2
0
0
However, the maximum output voltage should not exceed
100V.
Internal Linear Voltage Regulator
0.8
5
10
15
20
25
30
35
40
45
RFREQ (kΩ)
Figure 2: AAT2404 DC_DC Boost Switching
Frequency vs. RFREQ Resistor Value.
OVP
The over-voltage protection (OVP) circuit is provided to
shut down the boost control switching to the external
N-channel MOSFET if the output voltage exceeds a user
preset level, which can occur if the load circuit becomes
disconnected (open). The OVP pin input threshold is 1.2V
and the OVP shutdown voltage should be selected so
that the circuit is active within a reasonable margin
above the normal output operation voltage. To program
a desired OVP output limit level, place a resistor divider
between the voltage output node, the OVP pin, and
ground. Set the OVP voltage using Equation 2:
Eq. 2: R1 = R2
VOUTPUT PROTECTION
-1
VOVP
Where:
VOVP = OVP threshold = 1.2V
VOUTPUT PROTECTION = Desired output protection voltage
level
R2 should typically be set to 12.1kΩ (Nominal range for
R2 should be between 10kΩ and 47kΩ). The maximum
OVP is 120V.
Skyworks Solutions, Inc. • Phone [781] 376-3000 • Fax [781] 376-3100 • sales@skyworksinc.com • www.skyworksinc.com
202247A • Skyworks Proprietary Information • Products and Product Information are Subject to Change Without Notice. • August 7, 2012
9
DATA SHEET
AAT2404
Voltage-Variable Current Sourcing Boost Controller For LED Lighting Applications
Thermal Protect Shutdown
Power OK Flag Output
If an operating condition causes excess power dissipation in the AAT2404, the device will shut down when the
die temperature exceeds 140°C. When the die cools or
when the source of the over-temperature condition is
removed, the AAT2404 will automatically restart. There
is 15°C of shutdown restart hysteresis.
A power OK (POK) flag is provided to inform the system
when the output supply voltage is turned on and has
reached 80% regulation. The POK output is an open drain
N-channel MOSFET switch connected to ground internally. A 10KΩ or greater value pull-up resistor should be
connected between the POK pin and VCC. The POK flag
can function as an active low logic signal that can be used
to alert system logic or as an enable signal to a downstream load circuit to sequence the load power-on after
the boost supply is operating.
10
Skyworks Solutions, Inc. • Phone [781] 376-3000 • Fax [781] 376-3100 • sales@skyworksinc.com • www.skyworksinc.com
202247A • Skyworks Proprietary Information • Products and Product Information are Subject to Change Without Notice. • August 7, 2012
DATA SHEET
AAT2404
Voltage-Variable Current Sourcing Boost Controller For LED Lighting Applications
Application Information
Selecting the Switching Frequency
The AAT2404 is a highly integrated high-efficiency variable voltage current sourcing boost controller and like all
boost controllers care must be taken in the selection of
external components during the design stage to ensure a
stable and reliable system. The design is an iterative process since design parameters are mutually dependant. As
an example of this iterative process please refer to the
step-by-step design example application note.
Selecting the optimal switching frequency is an iterative
process since component and electrical parameters are
all interrelated. For example, to reduce the inductor
value and hence its size a higher switching frequency is
desired. However, too high of a switching frequency may
cause the switching losses in the external N-channel
boost MOSFET to become dominant and exceed the
power dissipation. A good starting point for the switching frequency is between 200kHz and 400kHZ. To set
the switching frequency, please refer to the Boost
Converter Switching Frequency section of this product
datasheet.
DC-DC Boost Duty Cycle Calculation
In order to correctly determine the characteristics for
external component selection, the switching duty cycle
for the boost converter function should be calculated. If
the input voltage to the AAT2404 is constant, then there
is only one maximum duty cycle condition to be concerned with (Equation 3). In the case of varied input
supply, the minimum, maximum, and nominal duty cycle
should be calculated (Equations 3, 4, and 5) and the use
of the maximum value should be carried forward for the
selection of the inductor, N-channel MOSFET, and reverse
blocking diode.
Eq. 3: DNOM =
VLED - VIN(NOM) + VD
VLED + VD
Eq. 4: DMIN =
VLED - VIN(MAX) + VD
VLED + VD
Eq. 5: DMAX =
VLED - VIN(MIN) + VD
VLED + VD
Selecting the Boost Inductor
The first parameter to be considered in the selection of
the boost inductor is the inductance value. In a fixedfrequency boost converter like the AAT2404, this value is
based on the desired peak-to-peak ripple current ∆IL,
which flows in the inductor along with the average or DC
inductor current IL. In continuous conduction mode (CCM)
IL is greater than the current output of the boost regulator, ILED. Taking into account the conservation of power
and neglecting efficiency losses, the two currents are
related by the following:
Conservation of power:
Eq. 6: VIN · IL = VLED · ILED
Eq. 7: VLED =
VIN
(1 - D)
Rearranging for IL:
Where:
DMIN = Minimum boost switching duty cycle
DMAX = Maximum boost switching duty cycle
(must be ≤ 80%)
DNOM = nominal boost switching duty cycle
VIN[MAX] = Maximum input supply voltage for the
application
VIN[MIN] = Minimum input supply voltage for the
application
VLED = Voltage output of the boost regulator (estimate
the maximum summed VF for the LED string for the
backlighting application)
VD = Reverse blocking diode forward voltage. A
Schottky diode is recommended for this application due
to their low forward voltage characteristic. The VF of a
Schottky diode is typically between 0.5V and 0.7V.
Eq. 8: IL =
VLED · ILED
VIN
Substituting VIN for VLED:
VIN
·I
(1 - D) LED
Eq. 9: IL =
VIN
Eq. 10: IL =
ILED
(1 - D)
Where:
VIN = Input supply voltage
VLED = Voltage output of the boost regulator
IL = Average inductor current or input supply current
ILED = Current output of the boost regulator
D = Boost switching duty cycle
Skyworks Solutions, Inc. • Phone [781] 376-3000 • Fax [781] 376-3100 • sales@skyworksinc.com • www.skyworksinc.com
202247A • Skyworks Proprietary Information • Products and Product Information are Subject to Change Without Notice. • August 7, 2012
11
DATA SHEET
AAT2404
Voltage-Variable Current Sourcing Boost Controller For LED Lighting Applications
The inductance value chosen is a tradeoff between size
and cost. Larger inductance means lower input ripple
current, however because the inductor is connected to
the output during the off-time, there is a limit to the
reduction in output ripple voltage. Lower inductance
results in smaller, less expensive magnetics. An inductance that gives a ripple current of 30% of IL is a good
starting point for a CCM boost converter:
Eq. 11: ∆iL(MAX) ≈ 0.3 ·
overheat the inductor and/or push the AAT2404 into current limit. In a boost converter, peak inductor current,
IPK, is equal to the maximum average inductor current
plus one half of the ripple current. First, the ripple current, ∆iL, must be determined under the conditions that
give maximum average inductor current:
ILED
1-D
Where:
∆iL(MAX) = Maximum desired inductor peak to peak current ripple
ILED = Current output of the boost regulator
D = Boost switching duty cycle
Minimum inductance should be calculated at the extremes
of input voltage to find the operating condition with the
highest requirement. Depending on the amount the
input voltage is boosted, the duty cycle term (D) can
become the dominant term. The minimum inductor value
can be established by one of the following equations,
whichever produces the larger minimum inductor value:
Eq. 12: LMIN =
VIN(MAX)
1
∆iL(MAX) · DMIN · fSW
Eq. 13: LMIN =
VIN(MIN)
1
∆iL(MAX) · DMAX · fSW
Where:
LMIN = Minimum inductance
VIN(MAX) = Maximum input supply voltage
VIN(MIN) = Minimum input supply voltage
∆iL(MAX) = Maximum inductor peak to peak current
ripple
DMIN = Minimum boost switching duty cycle
DMAX = Maximum boost switching duty cycle
fSW = Switching frequency
Figure 3: CCM Inductor Current.
12
VIN(MIN)
1
· DMAX · f
L
SW
Eq. 15: ∆iL =
VIN(MAX)
1
· DMIN · f
L
SW
Eq. 16: IL(PK) = IL +
∆iL
2
Where:
∆iL = Nominal ripple current in the inductor
VIN(MIN) = Minimum input voltage
L = Inductance
D = Boost switching duty cycle
fSW = Switching frequency
IL(PK) = Peak inductor current
IL = Average inductor current
IPK should be less than the saturation current specification of the selected inductor.
The final parameter of an inductor to consider is the DC
resistance (DCR), which contributes to the power loss of
the inductor and degrades the boost converter efficiency
and increases the inductor's operating temperature.
Based on the inductor value calculation, the next higher
standard value inductor should be used.
The second parameter that should be taken into consideration when selecting the boost inductor is the peak
current capability. This is the level above which the
inductor will saturate and the inductance can drop
severely, resulting in a higher peak current that may
Eq. 14: ∆iL =
Eq. 17: PLOSS(L) = I2RMS · DCR
Where:
Eq. 18: IRMS =
(IL)2 +
2
1
∆iL
12
is the RMS current in the inductor for continuous conduction mode operation.
Skyworks Solutions, Inc. • Phone [781] 376-3000 • Fax [781] 376-3100 • sales@skyworksinc.com • www.skyworksinc.com
202247A • Skyworks Proprietary Information • Products and Product Information are Subject to Change Without Notice. • August 7, 2012
DATA SHEET
AAT2404
Voltage-Variable Current Sourcing Boost Controller For LED Lighting Applications
Selecting the Schottky Diode
A low forward voltage drop Schottky diode is used as a
rectifier diode to reduce its power dissipation and
improve efficiency.
The average current through diode is the average load
current ILED, and the peak current through the diode is
the peak current through the inductor IPK. The diode
should be rated to handle more than its peak current.
Eq. 19: ID(PK) = IL(PK) = IL +
∆iL
2
Where:
ID(PK) = Peak diode current
IL(PK) = Peak inductor current
IL = Average inductor current
∆iL = Nominal ripple current in the inductor
The peak reverse voltage for the boost converter is equal
to the regulator output voltage. The diode must be
capable of handling this voltage. Using 80% derating on
VLED for ringing on the switch node, the rectifier diode
minimum reverse breakdown voltage is:
Eq. 20: VBRR(MIN) ≥
VLED
0.8
Where:
Eq. 22: D =
TON
= TON · FS
TON + TOFF
The maximum duty cycle can be estimated from the
relationship for a continuous mode boost converter.
Maximum duty cycle (DMAX) is the duty cycle at minimum
input voltage (VIN(MIN)):
Eq. 23: DMAX =
VLED - VIN(MIN)
VLED
The average diode current during the OFF time can be
estimated:
Eq. 24: IAVG(OFF) =
ILED
1 - DMAX
The VF of the Schottky diode can be estimated from the
average current during the off time. The average diode
current is equal to the output current:
Eq. 25: IAVG(TOT) = ILED
The average output current multiplied by the forward
diode voltage determines the loss of the output diode:
Eq. 26: PLOSS(DIODE) = IAVG(TOT) · VF = ILED · VF
VBRR(MIN) = Minimum voltage breakdown of the Schottky
diode
VLED = Voltage output of the boost regulator
To assure the rectifier diode is rated for the power dissipation requirement for a given application, the Schottky
diode power dissipation can be estimated.
The switching period is divided between ON and OFF
time intervals:
Eq. 21:
1
= TON + TOFF = D + D’
FS
During the ON time, the N-channel power MOSFET is
conducting and storing energy in the boost inductor.
During the OFF time, the N-channel power MOSFET is
not conducting. Stored energy is transferred from the
input battery and boost inductor to the output load
through the output diode. Duty cycle is defined as the
ON time divided by the total switching interval:
For continuous LED currents, the diode junction temperature can then be estimated:
Eq. 27: TJ(DIODE) = TAMB + θJA · PLOSS(DIODE)
The external Schottky diode junction temperature should
be below 110°C, and may vary depending on application
and/or system guidelines. The diode θJA can be minimized with additional metal PCB area on the cathode.
However, adding additional heat-sinking metal around
the anode may degrade EMI performance. The reverse
leakage current of the rectifier must be considered to
maintain low quiescent (input) current and high efficiency under light load, the rectifier reverse current
increases dramatically at elevated temperatures.
Skyworks Solutions, Inc. • Phone [781] 376-3000 • Fax [781] 376-3100 • sales@skyworksinc.com • www.skyworksinc.com
202247A • Skyworks Proprietary Information • Products and Product Information are Subject to Change Without Notice. • August 7, 2012
13
DATA SHEET
AAT2404
Voltage-Variable Current Sourcing Boost Controller For LED Lighting Applications
Selecting the External
N-Channel Boost MOSFET
Then the gate drive power required to turn on a MOSFET
is:
Selection of the external power MOSFET is controlled by
tradeoffs among efficiency, cost and size. The critical
parameters for the selection of a MOSFET are: minimum
threshold voltage, VGSth(MIN), minimum drain to source
breakdown voltage, BVDSS, on-resistance, RDS(ON), and
total gate charge, QG.
VGS, Gate-Source Voltage (V)
The peak-to-peak gate drive level is set by the VCC voltage, which is typically 5V for the AAT2404 under normal
operating conditions. This requires the minimum threshold voltage of the MOSFET to be less than 5V; logic level
MOSFETS have minimum threshold voltages less than 5V.
However, in switch mode operation the gate-to-drain
(“Miller”) charge parameter of the MOSFET QGD will affect
the VGSTH parameter. Consult the Gate Charge
Characteristics plot found in the datasheet of the MOSFET
and ensure that the QGD plateau is less than 4.5V (the
lower the better).
12
Where:
PG = Gate charge loss in the linear regulator of the
AAT2404
VG = Gate drive voltage VG = VCC = 5V
QG = Total gate charge of the MOSFET
fSW = Switching frequency
During the off state of the boost controller the voltage
across the MOSFET is equal to the output voltage, VLED,
when neglecting the intrinsic diode voltage drop. The
BVDSS parameter of the MOSFET must be greater than
the voltage output. Using 80% derating on VLED for ringing on the switch node, the minimum BVDSS voltage of
the MOSFET is
Eq. 30: BVDSS ≥
VLED
0.8
BVDSS = Minimum drain to source breakdown voltage
of the MOSFET
VLED = Voltage output of the boost regulator
10
8
First order power losses in a MOSFET can be attributed to
conduction loss, switching loss, and the gate drive loss.
Although the gate drive loss is not strictly in the MOSFET
it is included in the MOSFET power loss calculation.
6
VDS = 40V
VDS = 100V
VDS = 160V
4
QGD plateau
2
0
Eq. 29: PG = VG · QG · fSW
0
10
20
30
40
50
Eq. 31: PMOSFET = PC + PSW + PG
60
QG, Total Gate Charge (nC)
Figure 4: Example Gate Charge Characteristics
(ID = 21A).
Estimating gate drive power required to turn the MOSFET
on and the power losses in the MOSFET is a good way of
balancing the tradeoffs and comparing the relative merit
between MOSFET devices.
The amount of current needed to turn on a MOSFET is:
Where:
PMOSFET = Power dissipated by the MOSFET
PC = Conduction loss of the MOSFET
PSW = Switching loss of the MOSFET
PG = Gate charge loss in the linear regulator of the
AAT2404
Conduction loss is the I2R loss when the MOSFET is turned
on and is approximated by the following equation:
Eq. 32: PC = D ·
Eq. 28: IG = QG · fSW
ILED
1-D
2
· RDS(ON)
Where
Where:
IG = Required current to turn on a MOSFET
QG = Total Gate charge of the MOSFET
fSW = Switching frequency
PC = Conduction loss of the MOSFET
D = Boost switching duty cycle
ILED = Current output of the boost regulator
RDS(ON) = Maximum high temperature on-resistance of
the MOSFET
14
Skyworks Solutions, Inc. • Phone [781] 376-3000 • Fax [781] 376-3100 • sales@skyworksinc.com • www.skyworksinc.com
202247A • Skyworks Proprietary Information • Products and Product Information are Subject to Change Without Notice. • August 7, 2012
DATA
SHEET
PRODUCT
DATASHEET
AAT2404
AAT2404
TM
SwitchReg
Voltage Variable
Current
Sourcing
Controller
LED
LightingApplications
Applications
Voltage-Variable
Current
Sourcing
BoostBoost
Controller
ForFor
LED
Lighting
Switching loss occurs during the transition between the
MOSFET being turned on and then turned off.
1
ILED
Eq. 33: PSW =
2 · VIN · (1 - D) · (tR + tF) · fSW
Where:
PSW = Switching loss of the MOSFET
VIN = Minimum input voltage
ILED = Current output of the boost regulator
D = Boost switching duty cycle
tR = Rise time of the MOSFET (refer to the selected
MOSFET's datasheet)
tF = Fall time of the MOSFET (refer to the selected
MOSFET's datasheet)
fSW = Switching frequency
After selecting the MOSFET the package power dissipation in the operating circuit can be estimated.
Eq. 34: PD(TOTAL) = POUT
1
η - 1 = VLED · ILED ·
1
η -1
Where:
PD(TOTAL) = Total power dissipation for the system, (output power plus power loss of the switching MOSFET)
η = Boost efficiency (refer to the efficiency curve for
the given output load current in the Typical
Characteristics section of this datasheet)
VLED = Voltage output of the boost regulator
ILED = Current output of the boost regulator
The power that will be dissipated by the MOSFET should
be determined; the package PD rating of the MOSFET
selected should exceed this value:
Eq. 35: PMOSFET < PD(TOTAL) - PL - PD - (VIN · IQ )
Where:
PMOSFET = Power dissipated by the MOSFET
PD(TOTAL) = Total system power calculated in
Equation 34
PL = Power dissipation of the inductor based on the DC
resistance (DCR)
PD = Power dissipation of the reverse blocking
Schottky diode
VIN = Input supply voltage
IQ = Device quiescent supply current
Selecting the Output Capacitor
The output capacitor in a current regulator is selected to
control the output ripple current (ΔiF) when the inductor
is charging as opposed to a voltage regulator where ΔVO
is controlled. As a result, the output capacitor is subjected to much larger ripple currents.
Assuming a constant discharging current when the
MOSFET switch is on, the voltage ripple across the capacitor is:
Eq. 36: ∆VPK-PK =
ILED · DMAX
COUT · fSW
Solving for COUT:
Eq. 37: COUT =
ILED · DMAX
∆VPK-PK · fSW
Where
∆VPK-PK = VLED voltage ripple
ILED = Output supply current
DMAX = Maximum boost switching duty cycle
fSW = Switching frequency
The output capacitor must be capable of handling the
maximum output RMS current. Use Equation 38 to estimate the ICLED(RMS) value.
Eq. 38: ICLED(RMS) =
D
(1 - D) · ILED2 · (1 - D)2 +
∆iL2
3
Where
ILED = Current output of the boost regulator
∆iL = Nominal ripple current in the inductor
D = Boost switching duty cycle
The equivalent series resistance (ESR) and the equivalent series inductance (ESL) of the output capacitor
directly control the output ripple. Use capacitors with low
ESR and ESL specification at the output for high efficiency and low ripple voltage. Surface mount tantalum
polymer electrolytic, and polymer tantalum SanyoOSCON capacitors are recommended at the output.
Selecting the Input Capacitor
The input capacitors in a boost regulator control the input
voltage ripple (ΔVIN) and prevent impedance mismatch
(also called power supply interaction) between the
AAT2404 and the stray inductance of the input wire connections. Selection of input capacitors is based on their
capacitance, ESR, and RMS current rating. The minimum
Skyworks Solutions, Inc. • Phone [781] 376-3000
Fax
• www.skyworksinc.com
w w w•. a
n a[781]
l o g 376-3100
i c t e c h . •c osales@skyworksinc.com
m
202247A • Skyworks Proprietary Information • Products and Product Information are Subject to Change Without Notice. • August 7, 2012
15
DATA SHEET
AAT2404
Voltage-Variable Current Sourcing Boost Controller For LED Lighting Applications
input capacitance is based on ΔVIN or prevention of power
supply interaction. In general, the requirement for the
greatest capacitance comes from the power supply interaction.
To stabilize the regulator, ensure that the regulator
crossover frequency is less than or equal to one-tenth of
the right-half plane zero or less than or equal to onetenth of the switching frequency whichever is lower.
The stray inductance, LS, and resistance, RS, of the input
source must be estimated, and if this information is not
available, good design practice may assume the inductance and resistances to be 1μH and 0.1Ω, respectively.
The regulator loop gain is determined by Equation 41:
Minimum input capacitance is then estimated as:
2 · LS · VLED · ILED
Eq. 39: CIN(MIN) =
VIN2 · RS
Where:
LS = Power supply parasitic inductance (assumed to
be 1μH)
VLED = Voltage output of the boost regulator
ILED = Current output of the boost regulator
VIN = Input supply voltage
RS = Power supply stray resistance (assumed to be
0.1Ω)
Eq. 41:
VREF
VIN
1
| AVL | = V
· V
· GMEA · RC · GCS · 2π · f · C
=1
LED
LED
C
OUT
Where
VREF = Feedback voltage reference set by RSET
VIN = Input supply voltage
VLED = Voltage output of the boost regulator
RC = Compensation resistor
GMEA = Error amplifier transconductance: 176µA/V
GCS = Current sense amplifier transconductance:
3.0A/V
fC = Selected crossover frequency
COUT = Output capacitor
The AAT2404 regulator loop solving for compensation
resistor, RC:
Selecting the Compensation
Resistor and Capacitor
Eq. 42: RC =
Regulator stability is achieved with a simple RC compensation network from the COMP pin to ground. Once the
boost regulator design requirements have been established and the inductor and output capacitor values have
been chosen, the LC filter must be compensated for to
stabilize the boost regulator. The AAT2404 senses the
inductor current and eliminates the double pole LC filter
and simplifies the compensation to a single pole RC
caused by the output capacitance and the output load
resistance. However, since the AAT2404 is designed to
work in the continuous conduction mode (CCM) an undesirable right-half plane zero is produced in the regulation
feedback loop. This requires compensating the AAT2404
such that the crossover frequency occurs well below the
frequency of the right-half plane zero.
Eq. 40: FzRHP =
VIN
VLED
2
·
RL
2π · L
Once the compensation resistor is known, set the zero
formed by the compensation capacitor and resistor to
one-tenth of the crossover frequency, or:
Eq. 43: CC =
16
10
2π · fC · RC
If the zero of the ESR of the output capacitor is near fC,
then it needs to be cancelled out by putting and an extra
cap in parallel with RC and CC. To determine the zero of
the ESR of the output capacitor:
Eq. 44: fESR =
1
2π · RESR · COUT
To cancel the ESR zero:
Eq. 45: C2 =
Where:
VIN = Input supply voltage
VLED = Voltage output of the boost regulator
RL = Output load resistance
L = Inductance
2π · fC · COUT · VLED · VLED
VREF · VIN · GMEA · GCS
RESR · COUT
RC
Where:
RESR = ESR of the output capacitor
COUT = Output capacitor
RC = Compensation resistor
Skyworks Solutions, Inc. • Phone [781] 376-3000 • Fax [781] 376-3100 • sales@skyworksinc.com • www.skyworksinc.com
202247A • Skyworks Proprietary Information • Products and Product Information are Subject to Change Without Notice. • August 7, 2012
DATA SHEET
AAT2404
Voltage-Variable Current Sourcing Boost Controller For LED Lighting Applications
Layout Fundamentals
1. Minimize the length of both traces in series with the
output capacitor terminals to avoid high dV/dt (fast
changing voltages) and reduce capacitive coupling
and electric fields. One trace is from the cathode of
the rectifying diode to the positive terminal of the
capacitor, the other trace is from PGND to the negative terminal.
2. Minimize the loop area of high di/dt (fast charging
currents) to reduce inductance and magnetic field.
Use wide traces for high current traces.
3. Maintain a ground plane and connect to the IC PGND
pin(s) as well as the PGND connections of CIN and
COUT.
4. Consider additional PCB exposed area for the AAT2404
to maximize heat sinking capability. Connect the
exposed paddle (bottom of the die) to PGND or GND.
Connect AGND as close as possible to the package
and maximize the overall heat sinking space.
5. To maximize package thermal dissipation and power
handling capacity of the AAT2404's TQFN34-24 and
external MOSFET and diode packages (Q1 and D1),
solder the exposed paddle of the IC onto the thermal
landing of the PCB, where the thermal landing is connected to the ground plane. If heat is still an issue,
multi-layer boards with dedicated ground planes are
recommended. Also, adding more thermal vias on the
thermal landing helps transfer heat to the PCB effectively. The MOSFET and diode can also be mounted
upright and connected to heat sinks.
Skyworks Solutions, Inc. • Phone [781] 376-3000 • Fax [781] 376-3100 • sales@skyworksinc.com • www.skyworksinc.com
202247A • Skyworks Proprietary Information • Products and Product Information are Subject to Change Without Notice. • August 7, 2012
17
DATA SHEET
AAT2404
Voltage-Variable Current Sourcing Boost Controller For LED Lighting Applications
Typical System Configurations
for Direct and Edge Backlighting Applications
VIN
L1
D1
C5
Q1
EN GATE LXS
VIN
VCC
C1
R4
AAT2404
C2
OVP
R5
POK
CSFB
FREQ
COMP
RSET
C3
R3
R1
R2
10x16
PGND
10x16
10x16
AGND
VIN
24V
VCC
VIN
24V
AAT2403
VIN
CSFBI
CSn
CSFBO
16
VIN
24V
AAT2403
VIN
CSFBI
CSn
CSFBO
16
AAT2403
VIN
CSn
16
CSFBI CSFBO
Figure 5: Direct LCD TV LED Backlight System Using the AAT2404
to Drive Three 10Sx16P LED Arrays with Three AAT2403 Current Sink Controllers.
18
Skyworks Solutions, Inc. • Phone [781] 376-3000 • Fax [781] 376-3100 • sales@skyworksinc.com • www.skyworksinc.com
202247A • Skyworks Proprietary Information • Products and Product Information are Subject to Change Without Notice. • August 7, 2012
DATA SHEET
AAT2404
Voltage-Variable Current Sourcing Boost Controller For LED Lighting Applications
Ordering Information
Package
Marking1
Part Number (Tape and Reel)2
TQFN34-24
9UXYY
AAT2404IMK-T1
Skyworks Green™ products are compliant with
all applicable legislation and are halogen-free.
For additional information, refer to Skyworks
Definition of Green™, document number
SQ04-0074.
Package Information
TQFN34-243
3.000 ± 0.050
1.700 ± 0.050
Index Area
0.400 ± 0.050
R(5x)
2.700 ± 0.050
4.000 ± 0.050
0.210 ± 0.040
0.400 BSC
Detail “A”
Bottom View
Detail “A”
0.750 ± 0.050
Top View
0
+ 0.10
- 0.00
0.203 REF
Side View
ALL DIMENSIONS IN MILLIMETERS.
1. XYY = assembly and date code.
2. Sample stock is generally held on part numbers listed in BOLD.
3. The leadless package family, which includes QFN, TQFN, DFN, TDFN, and STDFN, has exposed copper (unplated) at the end of the lead terminals due to the manufacturing
process. A solder fillet at the exposed copper edge cannot be guaranteed and is not required to ensure a proper bottom solder connection.
Skyworks Solutions, Inc. • Phone [781] 376-3000 • Fax [781] 376-3100 • sales@skyworksinc.com • www.skyworksinc.com
202247A • Skyworks Proprietary Information • Products and Product Information are Subject to Change Without Notice. • August 7, 2012
19
DATA SHEET
AAT2404
Voltage-Variable Current Sourcing Boost Controller For LED Lighting Applications
Copyright © 2012 Skyworks Solutions, Inc. All Rights Reserved.
Information in this document is provided in connection with Skyworks Solutions, Inc. (“Skyworks”) products or services. These materials, including the information contained herein, are provided by Skyworks as a
service to its customers and may be used for informational purposes only by the customer. Skyworks assumes no responsibility for errors or omissions in these materials or the information contained herein. Skyworks may change its documentation, products, services, specifications or product descriptions at any time, without notice. Skyworks makes no commitment to update the materials or information and shall have no
responsibility whatsoever for conflicts, incompatibilities, or other difficulties arising from any future changes.
No license, whether express, implied, by estoppel or otherwise, is granted to any intellectual property rights by this document. Skyworks assumes no liability for any materials, products or information provided hereunder, including the sale, distribution, reproduction or use of Skyworks products, information or materials, except as may be provided in Skyworks Terms and Conditions of Sale.
THE MATERIALS, PRODUCTS AND INFORMATION ARE PROVIDED “AS IS” WITHOUT WARRANTY OF ANY KIND, WHETHER EXPRESS, IMPLIED, STATUTORY, OR OTHERWISE, INCLUDING FITNESS FOR A PARTICULAR
PURPOSE OR USE, MERCHANTABILITY, PERFORMANCE, QUALITY OR NON-INFRINGEMENT OF ANY INTELLECTUAL PROPERTY RIGHT; ALL SUCH WARRANTIES ARE HEREBY EXPRESSLY DISCLAIMED. SKYWORKS DOES
NOT WARRANT THE ACCURACY OR COMPLETENESS OF THE INFORMATION, TEXT, GRAPHICS OR OTHER ITEMS CONTAINED WITHIN THESE MATERIALS. SKYWORKS SHALL NOT BE LIABLE FOR ANY DAMAGES, INCLUDING BUT NOT LIMITED TO ANY SPECIAL, INDIRECT, INCIDENTAL, STATUTORY, OR CONSEQUENTIAL DAMAGES, INCLUDING WITHOUT LIMITATION, LOST REVENUES OR LOST PROFITS THAT MAY RESULT FROM
THE USE OF THE MATERIALS OR INFORMATION, WHETHER OR NOT THE RECIPIENT OF MATERIALS HAS BEEN ADVISED OF THE POSSIBILITY OF SUCH DAMAGE.
Skyworks products are not intended for use in medical, lifesaving or life-sustaining applications, or other equipment in which the failure of the Skyworks products could lead to personal injury, death, physical or environmental damage. Skyworks customers using or selling Skyworks products for use in such applications do so at their own risk and agree to fully indemnify Skyworks for any damages resulting from such improper
use or sale.
Customers are responsible for their products and applications using Skyworks products, which may deviate from published specifications as a result of design defects, errors, or operation of products outside of published parameters or design specifications. Customers should include design and operating safeguards to minimize these and other risks. Skyworks assumes no liability for applications assistance, customer product
design, or damage to any equipment resulting from the use of Skyworks products outside of stated published specifications or parameters.
Skyworks, the Skyworks symbol, and “Breakthrough Simplicity” are trademarks or registered trademarks of Skyworks Solutions, Inc., in the United States and other countries. Third-party brands and names are for
identification purposes only, and are the property of their respective owners. Additional information, including relevant terms and conditions, posted at www.skyworksinc.com, are incorporated by reference.
20
Skyworks Solutions, Inc. • Phone [781] 376-3000 • Fax [781] 376-3100 • sales@skyworksinc.com • www.skyworksinc.com
202247A • Skyworks Proprietary Information • Products and Product Information are Subject to Change Without Notice. • August 7, 2012