A3933: Three Phase Power MOSFET Controller

A3933
Three Phase Power MOSFET Controller
Discontinued Product
These parts are no longer in production The device should not be
purchased for new design applications. Samples are no longer available.
Date of status change: October 29, 2007
Recommended Substitutions:
For new customers or new applications, contact Allegro MicroSystems
applications group ([email protected]) for information
regarding the use of the A3938 as a replacement.
NOTE: For detailed information on purchasing options, contact your
local Allegro field applications engineer or sales representative.
Allegro MicroSystems, Inc. reserves the right to make, from time to time, revisions to the anticipated product life cycle plan for a
product to accommodate changes in production capabilities, alternative product availabilities, or market demand. The information
included herein is believed to be accurate and reliable. However, Allegro MicroSystems, Inc. assumes no responsibility for its use; nor
for any infringements of patents or other rights of third parties which may result from its use.
Data Sheet
26301.100†
3933
SC
GLC
RESET
PGND
AGND
DEAD
REF
4
3
2
1
32
31
30
THREE-PHASE POWER
MOSFET CONTROLLER
5
29
SENSE
CC
6
28
RC
GLB
7
27
PWM
26
BRKSEL
25
BRKCAP
24
BRAKE
23
19
DIR
22
H2
21
H3
Internal fixed off-time PWM current-control circuitry can be used to
regulate the maximum load current to a desired value. The peak loadcurrent limit is set by the user’s selection of an input reference voltage
and external sensing resistor. The fixed off-time pulse duration is set
by a user-selected external RC timing network.
A power-loss braking circuit brakes the motor on an under-voltage
condition. The device is configured to either coast or dynamically
brake the motor when this occurs.
H1 20
VBB 19
13
CONTROL LOGIC
GHA
18
12
MODE
SA
FAULT
11
17
GLA
FAULT
10
LCAP 16
CB
15
9
VCCOUT
GHB
14
8
CA
SB
BRAKE
GHC
The A3933SEQ is a three-phase MOSFET controller for use with
bipolar brushless dc motors. It drives all n-channel external power
FETs, allowing system cost savings and minimizing r(DS)on power loss.
The high-side drive block is implemented with bootstrap capacitors at
each output to provide the floating positive supply for the gate drive.
The high-side circuitry also employs a unique “intelligent” FET
monitoring circuit that ensures the gate voltages are at the proper levels
before turn-on and during the ON cycle. This device is targeted for
applications with motor supplies from 12 V to 28 V.
Dwg. PP-068
The A3933SEQ is supplied in a 32-lead rectangular (9 x 7) plastic
chip carrier (quad pack) for minimum-area, surface-mount applications.
ABSOLUTE MAXIMUM RATINGS
at TA = 25°C
Supply Voltage, VBB ............................. 28 V
(peak) .............................................. 30 V
Terminal Voltage, VCCOUT ................. 13.2 V
(peak) .............................................. 15 V
Logic Input Voltage Range,
VIN .................. -0.3 V to VLCAP + 0.3 V
Sense Voltage Range,
VSENSE ............................. -5 V to VLCAP
Output Voltage Range,
VSA, VSB, VSC .................. -5 V to +30 V
VGHA, VGHB, VGHC . -5 V to VBB + 14 V
VCA, VCB, VCC ..................... VSX + 14 V
Operating Temperature Range,
TA ................................. -20°C to +85°C
Junction Temperature, TJ ................. +150°C
Storage Temperature Range,
TS ............................... -55°C to +150°C
FEATURES AND BENEFITS
■
■
■
■
■
■
■
■
■
■
■
■
■
■
Drives External N-Channel FETs
Intelligent High-Side Gate Drive
Selectable Coast or Dynamic Brake on Power Down
Adjustable Dead Time for Cross-Conduction Protection
Selectable Fast or Slow Current-Decay Modes
Internal PWM Peak Current Control
Reset/Coast Input
120° Hall Commutation with Internal Pullup
Internal 5-V Regulator
Low-Side Synchronous Rectification
Direction Control
PWM Speed-Control Input
Fault-Diagnostic Output
Under-Voltage Protection
3933
THREE-PHASE POWER
MOSFET CONTROLLER
Functional Block Diagram
CONNECT FOR
12-V OPERATION
+V
LCAP
VBB
VCCOUT
REGULATOR
UNDERVOLTAGE
DETECT
H1
BOOTSTRAP
MONITOR
CX
BOOTSTRAP
CHARGE
Cboot
H2
TURN-ON
DELAY
H3
GHX
CONTROL
LOGIC
DIR
MODE
TO
1 OF 3
MOTOR
PHASES
SX
GATE-SOURCE
MONITOR
RESET
1 OF 3 HIGH-SIDE DRIVERS
PWM
RC
RT
HIGH-SIDE
DRIVER
LOW-SIDE
SYNCHRONOUS
RECTIFICATION
RC BLANKING
CT
DEAD-TIME
ADJUST
DEAD
TO
LCAP
(FIXED OFF TIME)
REF
+
SENSE
–
TURN-ON
DELAY
TO
LOW-SIDE
DRIVER
GLX
VCCOUT
1 OF 3 LOW-SIDE DRIVERS
BRAKE
BRKSEL
PGND
BRAKE
BOOTSTRAP LOW
VGS LOW
INVALID HALL
UNDERVOLTAGE
BRKCAP
RS
FAULT
AGND
TO
SENSE
Dwg. FP-045
RECOMMENDED OPERATING CONDITIONS
Supply Voltage, VBB ...................................... 15 V to 28 V
or, if VBB = VCCOUT ................................... 12 V ±10%
Logic Input Voltage Range, VIN .............. -0.3 V to +4.8 V
Sense Voltage Range, VSENSE ........................ -1 V to +1 V
RC Resistance .......................................... 10 kΩ to 100 kΩ
PWM Frequency, fPWM ....................... 20 kHz to 100 kHz
Dwg. OA-007-32
115 Northeast Cutoff, Box 15036
Worcester, Massachusetts 01615-0036 (508) 853-5000
Copyright © 1999, Allegro MicroSystems, Inc.
3933
THREE-PHASE POWER
MOSFET CONTROLLER
ELECTRICAL SPECIFICATIONS at TA = 25°C, VBB = VCCOUT = 12 V, Cload = 1000 pF, Cboot = 0.047 µF
(unless noted otherwise).
Limits
Parameter
Supply Current
Symbol
Quiescent Current
IBB
Reference Voltage
Ref. Volt. Load Regulation
Output Voltage
Output Voltage Regulation
Conditions
Min
Typ
Max
Units
RESET low, fPWM = 40 kHz
–
16
19
mA
RESET high
–
15
17
mA
4.75
5.0
5.25
V
–
10
25
mV
10.8
12
13.2
V
–
–
25
mV
VIH
2.0
–
–
V
VIL
–
–
0.8
V
–
<1.0
10
µA
-70
–
-130
µA
9.5
10.5
11.5
V
–
–
0.30
V
9.0
10.5
11.5
V
IGHx = 1 mA
–
–
0.25
V
VLCAP
∆VLCAP(∆ILCAP) ILCAP = 0 to -2 mA
VCCOUT
VBB = 28 V
∆VCCOUT(∆ICCOUT) VBB = 28 V, ICCOUT = 0 to -10 mA
Digital Logic Levels
Logic Input Voltage
Logic Input Current
IIH
VIH = 2 V
IIL
VIL = 0.8 V
Gate Drive
Low-Side Output Voltage
VGLxH
VGLxL
High-Side Output Voltage
IGLx = 1 mA
VGHxH
VGHxL
Low-Side Output
Switching Time
trGLx
1 V to 8 V
–
50
–
ns
tfGLx
8 V to 1 V
–
40
–
ns
High-Side Output
Switching Time
trGHx
1 V to 8 V
–
100
–
ns
tfGHx
8 V to 1 V
–
100
–
ns
DEAD Time
(Source OFF to Sink ON)
tDEAD
IDEAD = 10 µA
–
3000
–
ns
IDEAD = 215 µA
–
180
–
ns
Continued —
NOTES: 1. Typical Data is for design information only.
2. Negative current is defined as coming out of (sourcing) the specified device terminal.
www.allegromicro.com
3933
THREE-PHASE POWER
MOSFET CONTROLLER
ELECTRICAL SPECIFICATIONS at TA = 25°C, VBB = VCCOUT = 12 V, Cload = 0.001 µF, Cboot = 0.047 µF
(unless noted otherwise), continued.
Limits
Parameter
Bootstrap Capacitor
Symbol
Conditions
Min
Typ
Max
Units
50
100
150
mA
9.5
10.5
11.5
V
–
15
20
µA
Vio
–
0
±5.0
mV
ISENSE
–
–
-1.0
µA
IRC
850
945
1040
µA
VRCL
1.0
1.1
1.2
V
VRCH
2.7
3.0
3.2
V
Operating
20
–
100
kHz
Increasing VBB
9.7
10.2
10.7
V
Decreasing VBB
9.35
–
10.35
V
VBB = 12 V
9.5
–
–
V
–
6.3
–
V
Bootstrap Charge Current
ICx
Bootstrap Output Voltage
VCx
Reference Sx
Leakage Current
ICx
High side switched high, Sx = VBB
Current Limit
Offset Voltage
Input bias current
RC Charge Current
RC Voltage Threshold
PWM frequency Range
fPWM
Protection Circuitry
Undervoltage Threshold
UVLO
Boot-Strap Capacitor Volt.
VCxSx
High-Side Gate-Source Volt.
VGHxSx
Fault Output Voltage
VFAULT
IO = 1 mA
–
–
0.8
V
IBRKCAP
VBB = 8 V, BRKSEL ≥ 2 V
–
30
–
µA
VBB = 0, BRKCAP = 8 V
–
6.6
–
V
Brake Function
Brake Cap. Supply Current
Low-Side Gate Voltage
VGLxH
NOTES: 1. Typical Data is for design information only.
2. Negative current is defined as coming out of (sourcing) the specified device terminal.
115 Northeast Cutoff, Box 15036
Worcester, Massachusetts 01615-0036 (508) 853-5000
3933
THREE-PHASE POWER
MOSFET CONTROLLER
Terminal Descriptions
Terminal
Name
1
2
3
4
5
6
7
8
9
10
11
12
13
14
15
16
17
18
19
20
21
22
23
24
25
26
27
28
29
30
31
PGND
RESET
GLC
SC
GHC
CC
GLB
SB
GHB
CB
GLA
SA
GHA
CA
VCCOUT
LCAP
FAULT
MODE
VBB
H1
H3
H2
DIR
BRAKE
BRKCAP
BRKSEL
PWM
RC
SENSE
REF
DEAD
32
AGND
www.allegromicro.com
RESET — A logic input used to enable the device, internally
pulled up to VLCAP (+5 V). A logic HIGH will disable the
device and force all gate drivers to 0 V, coasting the motor. A
logic LOW allows the gate drive to follow commutation logic.
This input overrides BRAKE.
GLA/GLB/GLC — Low-side, gate-drive outputs for external
NMOS drivers. External series-gate resistors (as close as
possible to the NMOS gate) can be used to control the slew rate
seen at the power-driver gate, thereby controlling the di/dt and
dv/dt of the SA/SB/SC outputs. Each output is designed and
specified to drive a 1000 pF load with a rise time of 50 ns.
SA/SB/SC — Directly connected to the motor, these terminals
sense the voltages switched across the load. These terminals
are also connected to the negative side of the bootstrap capacitors and are the negative supply connections for the floating
high-side drive.
GHA/GHB/GHC — High-side, gate-drive outputs for external
NMOS drivers. External series-gate resistors (as close as
possible to the NMOS gate) can be used to control the slew rate
seen at the power-driver gate, thereby controlling the di/dt and
dv/dt of the SA/SB/SC outputs. Each output is designed and
specified to drive a 1000 pF load with a rise time of 100 ns.
CA/CB/CC — High-side connections for the bootstrap capacitors, positive supply for high-side gate drive. The bootstrap
capacitor is charged to approximately VCCOUT when the
associated output SA/SB/SC terminal is low. When the output
swings high, the voltage on this terminal rises with the output to
provide the boosted gate voltage needed for n-channel power
FETs.
continued next page
3933
THREE-PHASE POWER
MOSFET CONTROLLER
Terminal Descriptions (cont’d)
FAULT — Open-drain output to indicate fault condition; will
go active high for any of the following:
1 – invalid HALL input code,
2 – high-side, gate-source voltage less than 7 V,
3 – bootstrap capacitor not sufficiently charged, or
4 – under-voltage condition detected at VCCOUT.
The fault state for gate-source and bootstrap monitors are
cleared at each commutation. If the motor has stalled, then the
fault can only be cleared by toggling the RESET terminal or
power-up sequence.
MODE — A logic input to set current-decay method, internally
pulled up to VLCAP (+5 V). When in slow-decay mode (logic
HIGH), only the high-side FET is switched open during a PWM
OFF cycle. The fast-decay mode (logic LOW) switches both
the source and sink FETs.
H1/H2/H3 — Hall-sensor inputs; internally pulled up to VLCAP
(+5 V). Configured for 120° electrical spacing.
DIR — A logic input to reverse rotation, see commutation logic
table. Internally pulled up to VLCAP (+5 V).
BRAKE — A logic input to short out the motor windings for a
braking function. A logic HIGH will turn ON the low-side
FETs, turn OFF the high-side FETs. Internally pulled up to
VLCAP (+5 V). The braking torque applied will depend on the
speed.
BRKCAP — Connection for reservoir capacitor. This terminal
is used to provide a positive power supply for the sink-drive
outputs for a power-down condition. This will allow predictable braking, if desired. A blocking diode to VCCOUT is required. A 4.7 µF capacitor will provide 6.5 V gate drive for
300 ms. If a power-down braking option is not needed
(BRKSEL = LOW) then this terminal should be tied to VCCOUT.
BRKSEL — A logic input to enable/disable braking on powerdown condition. Internally pulled up to VLCAP (+5 V). If held
low, the motor will coast on a power-down condition.
PWM — Speed control input, internally pulled up to VLCAP
(+5 V). A logic LOW turns OFF all drivers, a logic HIGH will
turn ON selected drivers as determined by H1/H2/H3 input
logic. Holding the terminal high allows speed/torque control
solely by the current-limit circuit via REF analog voltage
command.
RC — An analog input used to set the fixed off time with an
external resistor (RT) and capacitor (CT). The tblank time is
controlled by the value of the external capacitor (see Applications Information). As a rule, the fixed off time should not be
less than 10 µs. The resistor should be in the range of 10 kΩ to
100 kΩ.
SENSE — An analog input to the current-limit comparator.
A voltage representing load current appears on this terminal
during ON time, when it reaches REF voltage, the comparator
trips and load current decays for the fixed off-time interval.
Voltage transients seen at this terminal when the drivers turn
ON are ignored for time tblank.
REF — An analog input to the current-limit comparator.
Voltage applied here sets the peak load current.
Ipeak = VREF/RS.
VCCOUT — A regulated 12 V output; supply for low-side gate
drive and bootstrap capacitor charge circuits. It is good practice
to connect a decoupling capacitor from this terminal to AGND,
as close to the device terminals as possible. The terminal
should be shorted to VBB for 12 V applications.
VBB — The A3933 supply voltage. It is good practice to
connect a decoupling capacitor from this terminal to AGND, as
close to the device terminals as possible. This terminal should
be shorted to VCCOUT for 12 V applications.
LCAP — Connection for decoupling capacitor for the internal
5 V reference. This terminal can source no more than 2 mA.
DEAD — An analog input. A resistor between DEAD and
LCAP is selected to adjust turn-off to turn-on time. This delay
is needed to prevent shoot-through in the external power FETs.
The allowable resistor range is 20 kΩ to 430 kΩ, which
converts to deadtime of 210 ns to 2.1 µs, using the following
equation:
tDEAD = (6.75 x 10-12 x RDEAD) + (75 x 10-9).
AGND — The low-level (analog) reference point for the
A3933.
PGND — The reference point for all low-side gate drivers.
115 Northeast Cutoff, Box 15036
Worcester, Massachusetts 01615-0036 (508) 853-5000
3933
THREE-PHASE POWER
MOSFET CONTROLLER
Commutation Truth Table
H1
Logic Inputs
H2
H3
H
H
H
L
L
L
H
H
H
L
L
L
L
L
H
H
H
L
L
L
H
H
H
L
DIR
GLA
GLB
GLC
H
H
H
H
H
H
L
L
L
L
L
L
L
L
H
H
L
L
H
L
L
L
L
H
L
L
L
L
H
H
L
H
H
L
L
L
H
H
L
L
L
L
L
L
L
H
H
L
H
L
L
L
H
H
H
L
L
L
H
H
Driver Outputs
GHA
GHB
GHC
H
L
L
L
L
H
L
L
H
H
L
L
L
H
H
L
L
L
L
L
L
L
H
H
L
L
L
H
H
L
H
H
L
L
L
L
SA
SB
SC
H
Z
L
L
Z
H
L
Z
H
H
Z
L
Z
H
H
Z
L
L
Z
L
L
Z
H
H
L
L
Z
H
H
Z
H
H
Z
L
L
Z
Input Logic
MODE
PWM
RESET
Mode
L
L
H
H
X
L
H
L
H
X
L
L
L
L
H
Fast decay
Fast decay
Slow decay
Slow decay
Coast
Operation
PWM chop mode, current decay
Peak current limit, selected drivers ON
PWM chop mode. current decay
Peak current limit, selected drivers ON
All gate drive outputs OFF, clear fault logic
Brake Control
BRAKE BRKSEL
L
L
H
H
L
H
L
H
Normal Operation
Under Voltage or Power Loss Condition
Normal run mode
Normal run mode
Dynamic brake, all sink gate drives ON
Dynamic brake, all sink gate drives ON
Coast, all gate drive outputs OFF
Dynamic brake, all sink gate drives ON
Coast, all gate drive outputs OFF
Dynamic brake, all sink gate drives ON
L = Low Level, H = High Level, X = Don’t Care, Z = High Impedance
www.allegromicro.com
3933
THREE-PHASE POWER
MOSFET CONTROLLER
Applications Information
Bootstrap Capacitor Selection. The high-side bootstrap
circuit operates on a charge-transfer principle. The gate charge
(Qg) specification of the external power MOSFET must be
taken into consideration. The bootstrap capacitor must be large
enough to turn on the MOSFET without losing significant gate
voltage. If the bootstrap capacitor is too large, it would take too
long to charge up during the off portion of the PWM cycle. The
capacitor value must be selected with both of these constraints
in mind.
1) Minimum bootstrap capacitor value to transfer charge. The
charge on the bootstrap capacitor should be 20x greater than the
gate charge (Qg) of the power MOSFET.
Example: For Qg = 0.025 µC, select
Cboot = 20 x Qg/10.5 V = 0.047 µF.
Check for maximum Vg drop at turn on: dq = Cboot x dVg, where
Qg = dq.
dVg = dq/Cboot = 0.025 µC/0.047 µF = 532 mV.
2) Calculate minimum PWM “OFF” cycle with Cboot = 0.047 µF.
bootstrap capacitor. When the bootstrap capacitor has been
properly charged, the high side is turned back ON. The circuit
will allow three faults of this type within one commutation
cycle before signaling a fault and coast the motor (all gate
outputs go low).
2) Bootstrap Monitor. The bootstrap capacitor is charged
whenever a sink-side MOSFET is ON, Sx output goes low, and
the load current recirculates. This happens constantly during
normal operation. A 60 µs timer is started at the beginning of
this cycle and the capacitor is charged with typically 100 mA.
The bootstrap capacitor voltage is clamped at approximately
87% of VCCOUT. If the capacitor is not charged to the clamp
voltage in 60 µs, a fault is signaled and the motor will coast.
3) Undervoltage. The internal VCCOUT regulator supplies the
low-side gate driver and the bootstrap charge current. It is
critical to ensure that the voltages are at a proper level before
enabling any of the outputs. The undervoltage circuit is active
during power up and will force a motor coast condition until
VCCOUT is greater than approximately 10 V.
4) Hall Invalid. Illegal codes for the HALL inputs (000 or
111) will force a fault and coast the motor.
dt = ro x Cboot x ln(0.036/[Qg/Cboot + 0.036])
where ro = 20 ohms, the equivalent internal series resistance of
the bootstrap capacitor monitor circuit.
The sink-side MOSFET will be held OFF for this minimum
time such that the bootstrap capacitor can be recharged
independently of the PWM input frequency.
The above equation is valid for PWM cycles after the bootstrap
capacitor has been charged once. For the first cycle after a
motor phase commutates from Hi-Z to GHx ON, or during the
first charging cycle at power-up, the circuit will ignore PWM
signals until it has been charged.
The time required to charge up at power up and at commutation
change is approximately:
t = Cboot x 7 V/0.1 A
Protection Circuitry. The A3933 will protect the external
MOSFETs by shutting down the gate drive if any of the
following conditions are detected:
1) Gate Source Monitor (high side only). The voltage on
the GHx terminals must stay 7 V higher than the source. If this
voltage droops below the threshold, the high side turns OFF,
and the low-side gate will turn ON in an attempt to recharge the
Faults are cleared at the beginning of each commutation. If a
stalled motor results from a fault, the fault can only be cleared
by toggling the RESET terminal or by a power-up sequence.
Current Control. Internal fixed off-time PWM circuitry is
implemented to limit load current to a desired value. The
external sense resistor combined with the applied analog
voltage to REF terminal will set the peak current level
approximately
ITRIP ≈ VREF/RS.
After the peak level is reached, the sense comparator trips and
the load current will decay for a fixed off time.
An external resistor (RT) and capacitor (CT) are used to set the
fixed off-time period (toff = RT x CT). The toff should be in the
range of 10 µs to 50 µs. Longer values for toff can result in
audible noise problems.
Torque control can be implemented by varying the REF input
voltage as long as the PWM input stays high. If direct control
of the torque/current is desired by PWM input, a voltage can be
applied to the REF input to set an absolute maximum current
limit.
115 Northeast Cutoff, Box 15036
Worcester, Massachusetts 01615-0036 (508) 853-5000
3933
THREE-PHASE POWER
MOSFET CONTROLLER
Applications Information (cont’d)
PWM Blank. The capacitor (CT) also serves as the means to
set the blank time duration. After the off time expires, the
selected gates are turned back ON. At this time, large current
transients can occur during the reverse recovery time (trr) of the
intrinsic body diodes of the external MOSFETs. To prevent the
current-sense comparator from thinking the current spikes are a
real overcurrent event, the comparator is blanked:
tblank = 1.9 x CT/(1 mA-2/RT)
The user must ensure that CT is large enough to cover the
current-spike duration.
Load Current Recirculation. If MODE has been set for
slow decay, the high-side (source) driver will turn OFF forcing
the current to recirculate through the pair of sink MOSFETs. If
MODE has been selected for fast decay, both the selected highand low-side gates are turned OFF, which will force the current
to recirculate through one sink MOSFET and the high-side
clamp diode. Synchronous rectification (only on the low side)
allows current to flow through the MOSFET, rather than the
clamp diode, during the decay time. This will minimize power
loss during the off period. It is important to take into account
that, when switching, the intrinsic diodes will conduct during
the adjustable deadtime.
Power Loss Brake. The BRKCAP and BRKSEL terminals
provide a power-down braking option. By applying a logic
level to input BRKSEL, the system can control if the motor is
dynamically braked or is allowed to coast during an
undervoltage event. The reservoir capacitor on the BRKCAP
terminal provides the power to hold the sink-side gates ON after
supply voltage is lost. A logic high on BRKSEL will brake the
motor, a logic low and it will coast.
Layout. Careful consideration must be given to PCB layout
when designing high-frequency, fast-switching, high-current
circuits.
1) The analog ground (AGND), the power ground (PGND),
and the high-current return of the external MOSFETs (the
negative side of the sense resistor) should return separately to
the negative side of the motor supply filtering capacitor. This
will minimize the effect of switching noise on the device logic
and analog reference.
2) Minimize stray inductances by using short, wide copper
runs at the drain and source terminals of all power MOSFETs.
This includes motor lead connections, the input power buss, and
the common source of the low-side power MOSFETs. This will
minimize voltages induced by fast switching of large load
currents.
VBB
DRIVE CURRENT
RECIRCULATION
(SLOW-DECAY MODE)
RECIRCULATION
(FAST-DECAY MODE)
RS
Dwg. EP-006-50
www.allegromicro.com
Braking. The A3933 will dynamically brake by forcing all
sink-side MOSFETs ON. This will effectively short out the
BEMF. During braking, the load current can be approximated
by:
IBRAKE = VBEMF/RL
3) Kelvin connect the SENSE terminal PC trace to the
positive side of the sense resistor.
3933
THREE-PHASE POWER
MOSFET CONTROLLER
Dimensions in Inches
(controlling dimensions)
20
0.013
0.021
14
13
21
0.026
0.032
0.546
0.476
0.595
0.585
LONG SIDE
(0.446
0.376
0.553
0.547
SHORT SIDE)
0.050
BSC
29
5
30
32
1
4
0.453
0.447
0.495
0.485
0.015
MIN
0.125
0.140
Dwg. MA-006-32 in
NOTES: 1. Lead spacing tolerance is non-cumulative.
2. Exact body and lead configuration at vendor’s option within limits shown
115 Northeast Cutoff, Box 15036
Worcester, Massachusetts 01615-0036 (508) 853-5000
3933
THREE-PHASE POWER
MOSFET CONTROLLER
Dimensions in Millimeters
(for reference only)
20
0.33
0.54
14
13
21
0.66
0.82
13.86
12.10
15.11
14.86
LONG SIDE
(11.32
9.56
14.04
13.90
SHORT SIDE)
1.27
BSC
29
5
30
0.38
MIN
3.18
3.55
32
1
4
11.50
11.36
12.57
12.32
Dwg. MA-006-32 mm
NOTES: 1. Lead spacing tolerance is non-cumulative.
2. Exact body and lead configuration at vendor’s option within limits shown
The products described here are manufactured under one or more U.S.
patents or U.S. patents pending.
Allegro MicroSystems, Inc. reserves the right to make, from time to
time, such departures from the detail specifications as may be required to
permit improvements in the performance, reliability, or manufacturability
of its products. Before placing an order, the user is cautioned to verify that
the information being relied upon is current.
Allegro products are not authorized for use as critical components in
life-support devices or systems without express written approval.
The information included herein is believed to be accurate and reliable.
However, Allegro MicroSystems, Inc. assumes no responsibility for its use;
nor for any infringement of patents or other rights of third parties which
may result from its use.
www.allegromicro.com
3933
THREE-PHASE POWER
MOSFET CONTROLLER
MOTOR DRIVERS
Function
Output Ratings*
Part Number†
INTEGRATED CIRCUITS FOR BRUSHLESS DC MOTORS
3-Phase Power MOSFET Controller
—
28 V
3933
3-Phase Power MOSFET Controller
—
50 V
3932
3-Phase Power MOSFET Controller
—
50 V
7600
2-Phase Hall-Effect Sensor/Driver
400 mA
26 V
3626
Bidirectional 3-Phase Back-EMF Controller/Driver
±600 mA
14 V
8906
2-Phase Hall-Effect Sensor/Driver
900 mA
14 V
3625
3-Phase Back-EMF Controller/Driver
±900 mA
14 V
8902–A
3-Phase Controller/Drivers
±2.0 A
45 V
2936 & 2936-120
INTEGRATED BRIDGE DRIVERS FOR DC AND BIPOLAR STEPPER MOTORS
Dual Full Bridge with Protection & Diagnostics
±500 mA
30 V
3976
PWM Current-Controlled Dual Full Bridge
±650 mA
30 V
3966
PWM Current-Controlled Dual Full Bridge
±650 mA
30 V
3968
PWM Current-Controlled Dual Full Bridge
±750 mA
45 V
2916
PWM Current-Controlled Dual Full Bridge
±750 mA
45 V
2919
PWM Current-Controlled Dual Full Bridge
±750 mA
45 V
6219
PWM Current-Controlled Dual Full Bridge
±800 mA
33 V
3964
PWM Current-Controlled Full Bridge
±1.3 A
50 V
3953
PWM Current-Controlled Dual Full Bridge
±1.5 A
45 V
2917
PWM Current-Controlled Dual Full Bridge
±1.5 A
45 V
2918
PWM Current-Controlled Microstepping Full Bridge
±1.5 A
50 V
3955
PWM Current-Controlled Microstepping Full Bridge
±1.5 A
50 V
3957
PWM Current-Controlled Dual DMOS Full Bridge
±1.5 A
50 V
3972
Dual Full-Bridge Driver
±2.0 A
50 V
2998
PWM Current-Controlled Full Bridge
±2.0 A
50 V
3952
DMOS Full Bridge PWM Driver
±2.0 A
50 V
3958
Dual DMOS Full Bridge
±2.5 A
50 V
3971
UNIPOLAR STEPPER MOTOR & OTHER DRIVERS
Voice-Coil Motor Driver
±500 mA
6V
8932–A
Voice-Coil Motor Driver
±800 mA
16 V
8958
Unipolar Stepper-Motor Quad Drivers
1A
46 V
7024 & 7029
Unipolar Microstepper-Motor Quad Driver
1.2 A
46 V
7042
Unipolar Stepper-Motor Translator/Driver
1.25 A
50 V
5804
Unipolar Stepper-Motor Quad Driver
1.8 A
50 V
2540
Unipolar Stepper-Motor Quad Driver
1.8 A
50 V
2544
Unipolar Stepper-Motor Quad Driver
3A
46 V
7026
Unipolar Microstepper-Motor Quad Driver
3A
46 V
7044
* Current is maximum specified test condition, voltage is maximum rating. See specification for sustaining voltage limits
or over-current protection voltage limits. Negative current is defined as coming out of (sourcing) the output.
† Complete part number includes additional characters to indicate operating temperature range and package style.
Also, see 3175, 3177, 3235, and 3275 Hall-effect sensors for use with brushless dc motors.
115 Northeast Cutoff, Box 15036
Worcester, Massachusetts 01615-0036 (508) 853-5000
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