DESIGN FEATURES New Instrumentation Amplifier: SingleResistor Gain Set and Precision Front End Make Accuracy Easy by Glen Brisebois The LT1168 is a low power, single-resistor gain-programmable instrumentation amplifier that is easy to apply. It is a pin-compatible upgrade for the AD620 (and the INA118 with a resistor-value change) and is available in C and I grades. With negligible 60µV (Max) offset voltage and ultrahigh 1TΩ input impedance, it can sense bridges with source impedances from 10Ω to 100k without degrading the signal. Its 120dB CMRR at 60Hz (AV = 100V) is achieved even with a 1k source impedance imbalance. Matching the LT1168’s CMRR using discrete op amps would require the use of 0.001% resistors. The LT1168’s robust inputs meet IEC1000-4-2 Level 4 ESD tests with the addition of two external 5k series resistors. These 5k resistors will contribute only a negligible 6µV of DC error. Table 1. Examples of series resistors for precision gain Desired Gain RG (Theoretical) RG1 0.1% RG 2 1% "Top-Up" Resultant Gain 59.28 847.63Ω 845Ω 2.61Ω 59.28 102.69 412.72Ω 412Ω 1Ω 120.61 408.72 121.62Ω 121Ω 0Ω 409.62 range of the LT1097 is not exceeded over temperature. With the current drive and the sensor bridge in place, the rest of the circuit is composed entirely of the LT1167 and its gainset resistor, R2. The sensor gives a full-scale output of 50mV (±1%) at 30psi (just over two atmospheres) with a 1.235V reference. With a 1.25V reference, the full-scale output value scales to 50.61mV. In order to get a convenient and easily read output of 100mV per 1psi, R2 should be chosen to set the gain to 3V/.05061V = 59.28. Typical Application: Absolute Or, with 2.036 inches of mercury Pressure Meter (Barometer) equal to 1psi (referred to 39°F), change Figure 1 shows just how easy it is to R2 to set a gain of 120.7 for a conveapply the LT1167. The LT1097, in nient output of 100mV per 1inHg. Or, conjunction with the LT1634-1.25 again, with 6.8947kPascals equal to reference and R1, provides a preci- 1psi, set the gain to 408.7 for an sion current drive for the bridge. D1 output of 100mV per kiloPascal. The ensures that the common mode input single-resistor gain adjustment makes ABSOLUTE PRESSURE SENSOR IC SENSORS (MEASUREMENT SPECIALTIES) #1220-030A (408) 432-1800 GAIN R2 100mV = 6 59.3 847.6Ω 1psi R1 102.7* 412.7Ω 1in Hg CURRENT 408.7* 121.6Ω 1kPa SET 5 ~2k *SEE TEXT FOR ACHIEVING D1 1N4148 5V C1 0.01µF 5V LT1634 -1.25 2 3 R3 33k – + LT1097 BRIDGE 4× ~4k 6 3 3 R2 2 4 1 + RG2 1% 2 7 LT1168 – 5 4 Linear Technology Magazine • May 2000 6 LT1168 VOUT 5 RG1 = LARGER VALUE PRECISION RESISTOR RG2 = SMALLER VALUE (A FEW OHMS) "TOP-UP" RESISTOR RG = RG1 + RG2 GAIN = Figure 1. Simple barometer 3 + VOUT –5V –5V 1 8 – REF 6 8 1 The relation between the LT1168 gain and the gain-set resistor is given by the following equations: RG = 49.4kΩ/ (Gain – 1), and equivalently, Gain = (49.4kΩ/RG) + 1. In order to take advantage of the high CMRR without taking gain, simply do not connect an RG. This configures the LT1168 as a precision, buffered, unity-gain difference amplifier. If precision gain is desired, use a 0.1% precision resistor in order not to degrade the 0.1% gain error specification of the LT1168. To target the desired gain exactly, pick a standard 0.1% value that is slightly smaller than required. Then, in order to “top up” the total RG to the required value, use a small value standard 1% resistor in series, as shown in Figure 2. As long as the 1% resistor is a relatively small value, say 1/20 of the 0.1% value, the overall precision will not be degraded. Table 1 shows prac- RG1 0.1% 5V 7 Setting the Gain 2 LARGE OUTPUT SWING 4 it easy to accommodate the desired units effortlessly. 49,400Ω +1 RG Figure 2. Targeting gain precisely 21 DESIGN FEATURES 60 V+ VB R5 30k + A1 2 Q1 R1 24.7k V – 0 G=1 –10 RG 8 + R7 30k R8 30k 1 10 FREQUENCY (kHz) 100 1000 Figure 4. LT1168 gain vs frequency 5 REF C2 V– Q2 R2 24.7k V 0.1 VY – R4 400Ω 3 –20 0.01 V– VB V+ A2 7 V+ 4 V– – PREAMP STAGE DIFFERENCE AMPLIFIER STAGE Figure 3. LT1168 block diagram tical resistor values for the gains specified above. Note that most transducers do not have 0.1% accurate sensitivity anyway, so most applications would use a 1% resistor and then perform a two-point calibration on the overall system. Achieving Large Output Swings Figure 3 shows the block diagram of the LT1168. Note that the last stage is a unity-gain difference amplifier. This means that the output voltage (across the Output and the Ref pins) will appear internal to the LT1168 across nodes Vx and Vy, centered around the common mode input voltage (minus one VBE). In order to support full output swings, whether due to high applied gains or large differential inputs, the common mode input voltage should not be too close to either rail. For example, if the inputs are centered around ground and the Ref pin is grounded, then under excitation Vx and Vy will swing around ground (minus one VBE) and the output swing will be limited by the normal output stage limitation of about 1.2V from either rail. However, if the common mode input voltage is at 10V on ±15V supplies, Vx and Vy will swing around 9.3V. In this case, the output swing will be limited by the outputs of 22 G = 10 10 A3 RG 1 +IN 20 – + G = 100 30 GAIN (dB) C1 40 the intermediate amplifiers, A1 and A2, as they reach their upper limits about 1V from the rail. Thus, the final output swing in this case will be limited to ±4.6V even though the supplies are ±15V. With regard to the lower rail, if the common mode input voltage is at –10V on ±15V supplies, then VX and VY will swing around –10.7V. The final output swing in this case will be limited to ±3.3V even though the supplies are ±15V. As a rule of thumb, in order to achieve the full output swing, keep the common mode input voltage within the middle one-third of the supplies. For example, in the case of Figure 1, with gain = 408.7, the full-scale output voltage at 30psi (204.4kPa) would be 20.44V. Providing the LT1168 with +24V/–5V supplies and, given that the bridge section of the sensor typically has about 3V of excitation across it, replacing D1 with a 12V Zener diode will approximately center the common mode input voltage. This allows the LT1168 to achieve full 0V (vacuum) to 20.44V (204.4kPa, or about 2.2 atmospheres) output swing. For information on using the LT1168 on a single 5V supply, see “Designing the LT1167 Instrumentation Amplifier into a Single 5V Supply Application,” in Linear Technology IX:2 (June 1999). AC Performance at Low Power The LT1168 is not limited to DC and low frequency applications. Figures 4 and 5 show the frequency response and common mode rejection ratio of the LT1168 for various gains. The high frequency performance renders the LT1168 applicable in accelerometer and balanced audio line receiver applications, for example, in addition to the usual slower applications. This AC performance is achieved with a low supply-current budget of only 0.5mA. Conclusion The LT1168’s precision front end and simple gain programmability make accuracy easy to achieve. The AC performance of the internal amplifier results in both extended differential mode bandwidth and excellent common mode rejection. Good common mode rejection is essential for extracting signals from a hostile world of interference. 160 COMMON MODE REJECTION RATIO (dB) –IN 6 OUTPUT VS = ±15V TA = 25°C G = 1000 50 VX – R3 400Ω R6 30k G = 1000 140 G = 100 120 G = 10 100 G=1 80 60 40 VS = 15V TA = 25°C 1k SOURCE IMBALANCE 20 0 0.1 1 10 100 1k FREQUENCY (Hz) 10k 100k Figure 5. Common mode rejection ratio vs frequency (1k source imbalance) Linear Technology Magazine • May 2000