HIP5600 ® WN ITHDRA PART W BSOLETE SS O PROCE IGNS W DES N NO E September 1998 File Number Thermally Protected High Voltage Linear Regulator Features The HIP5600 is an adjustable 3-terminal positive linear voltage regulator capable of operating up to either 400VDC or 280VRMS. The output voltage is adjustable from 1.2VDC to within 50V of the peak input voltage with two external resistors. This high voltage linear regulator is capable of sourcing 1mA to 30mA with proper heat sinking. The HIP5600 can also provide 40mA peak (typical) for short periods of time. • Operates from 50VRMS to 280VRMS Line Protection is provided by the on chip thermal shutdown and output current limiting circuitry. The HIP5600 has a unique advantage over other high voltage linear regulators due to its ability to withstand input to output voltages as high as 400V(peak), a condition that could exist under output short circuit conditions. Common linear regulator configurations can be implemented as well as AC/DC conversion and start-up circuits for switch mode power supplies. The HIP5600 requires a minimum output capacitor of 10µF for stability of the output and may require a 0.02µF input decoupling capacitor depending on the source impedance. It also requires a minimum load current of 1mA to maintain output voltage regulation. All protection circuitry remains fully functional even if the adjustment terminal is disconnected. However, if this happens the output voltage will approach the input voltage. 3270.7 • Operates from 50VDC to 400VDC • UL Recognized • Variable DC Output Voltage 1.2VDC to VIN - 50V • Internal Thermal Shutdown Protection • Internal Over Current Protection • Up to 40mA Peak Output Current • Surge Rated to ±650V; Meets IEEE/ANSI C62.41.1980 with Additional MOV CAUTION: This product does not provide isolation from AC line. Applications • Switch Mode Power Supply Start-Up • Electronically Commutated Motor Housekeeping Supply • Power Supply for Simple Industrial/Commercial/Consumer Equipment Controls • Off-Line (Buck) Switch Mode Power Supply Ordering Information PART NUMBER TEMP. RANGE PACKAGE HIP5600IS -40oC to +100oC 3 Lead Plastic SIP HIP5600IS2 -40oC to +100oC 3 Lead Gullwing Plastic SIP Pinouts HIP5600 (TO-220) TOP VIEW TAB ELECTRICALLY CONNECTED TO VOUT HIP5600 (MO-169) TOP VIEW VOUT 63 VIN VOUT VIN ADJ VOUT ADJ HIP5600 CAUTION: These devices are sensitive to electrostatic discharge; follow proper IC Handling Procedures. 1-888-INTERSIL or 321-724-7143 | Intersil (and design) is a registered trademark of Intersil Americas Inc. Copyright © Intersil Americas Inc. 2002. All Rights Reserved HIP5600 Functional Block Diagram HIP5600 RECTIFIER FOR AC OPERATION PASS TRANSISTOR SHORT-CIRCUIT PROTECTION VOUT - VIN - + + RF1 BIAS NETWORK C2 THERMAL SHUTDOWN - C1 FEEDBACK OR CONTROL AMPLIFIER + RF2 + VOLTAGE REFERENCE - ADJ Schematic Diagram VIN R1 D2 D1 D4 Q1 R2 Q2 D3 R3 Q11 D7 R12 Q12 D8 Q4 R13 D9 R4 Q9 D6 Q5 R11 R5 D5 Q14 C1 R7 R14 Q3 Q6 Q10 R8 R6 R15 Q8 Q7 R10 R9 ADJ FIGURE 1. 64 Q13 VOUT HIP5600 Absolute Maximum Ratings Thermal Information (Typical) Input to Output Voltage, Continuous . . . . . . . . . . . . +480V to -550V Input to Output Voltage, Peak (Non Repetitive, 2ms) . . . . . . . ±650V Junction Temperature. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . +150oC ADJ to Output, Voltage to ADJ . . . . . . . . . . . . . . . . . . . . . . . . . . . . ±5V Storage Temperature Range . . . . . . . . . . . . . . . . . -65oC to +150oC Lead Temperature (Soldering 10s). . . . . . . . . . . . . . . . . . . . +265oC Thermal Resistance Plastic SIP Package . . . . . . . . . . . . . . θJA 60oC/W θJC 4oC/W CAUTION: Stresses above those listed in “Absolute Maximum Ratings” may cause permanent damage to the device. This is a stress only rating and operation of the device at these or any other conditions above those indicated in the operational sections of this specification is not implied. Operating Conditions Operating Voltage Range . . . . . . . . . . . . . . 80VRMS to 280V RMS or 50V DC to 400VDC Operating Temperature Range . . . . . . . . . . . . . . . .-40oC to +100oC Electrical Specifications Conditions VIN = 400VDC, IL = 1mA, CL = 10µF, VADJ = 3.79V, VOUT = 5V (Unless Otherwise Specified) Temperature = Case Temperature. PARAMETER CONDITION TEMP MIN TYP MAX UNITS INPUT Input Voltage DC Full 50 - 400 V Max Peak Input Voltage Non-Repetitive (2ms) Full - - ±650 V Input Frequency (Note 1) Full DC - 1000 Hz Bias Current (IBIAS Note 2) Full 0.4 0.5 0.6 mA +25oC 50 65 80 µA Full - +0.15 - µA/oC +25oC - -215 - nA/mA +25oC 1.07 1.18 1.30 V Full - -460 - µV/oC +25oC - 9 14.5 µV/V Full - 9 29 µV/V +25oC - 3 5 mV/mA Full - 3 6 mV/mA REFERENCE IADJ IADJTC (Note 1) IL = 1mA IADJ LOAD REG (Note 1) IL = 1mA to 10mA VREF (Note 3) VREF TC (Note 1) IL = 1mA Line Regulation VREF LINE REG 50VDC to 400VDC Load Regulation VREF LOAD REG IOUT = 1mA to 10mA PROTECTION CIRCUITS Output Short Circuit Current Limit V IN = 50V +25oC 35 - 45 mA Thermal Shutdown TTS (IC surface, not case temperature. Note 1) VIN = 400V - 127 134 142 oC Thermal Shutdown Hysteresis (Note 1) VIN = 400V - - 34 - oC NOTES: 1. Characterized not tested 2. Bias current ≡ input current with output pin floating. 3. VREF = VOUT - VADJ 65 HIP5600 Application Information Introduction HIP5600 VIN ADJ AC/DC VOUT In many electronic systems the components operate at 3V to 15V but the system obtains power from a high voltage source (AC or DC). When the current requirements are small, less than 10mA, a linear regulator may be the best supply provided that it is easy to design in, reliable, low cost and compact. The HIP5600 is similar to other 3 terminal regulators but operates from much higher voltages. It protects its load from surges +250V above its 400V operating input voltage and has short circuit current limiting and thermal shutdown self protection features. VREF IADJ = (V REF RF2 3.3V 3.6k 5.6k 4.9V 2.7k 7.5k 12.0V 1.8k 15k 14.8V 1.1k 12k VOUT AC/DC The HIP5600 provides a temperature independent 1.18V reference, VREF , between the output and the adjustment terminal (V REF = VOUT - VADJ). This constant reference voltage is impressed across RF1 (see Figure 2) and results in a constant current (I1) that flows through RF2 to ground. The voltage across RF2 is the product of its resistance and the sum of I1 and IADJ. The output voltage is given in Equations 1(A, B). OUT RF1 RF2 Output Voltage V I1 RF1 VOUT(NOMINAL) RF1 + RF2 ( RF2 ) ) ------------------------------ + I ADJ RF1 RF1 + RF2 = ( 1.18 ) × ------------------------------ + 65µA ( RF2 ) V OUT RF1 (EQ. 1A) FIGURE 2. Example: Given: VIN = 200VDC , VOUT = 15V, IOUT = 2mA to 12mA, θSA = 10oC/W, RF1 = 1.1kΩ 5% low, RF2 = 12kΩ 5% high, ∆IOUT equals 10mA and ∆Temp equals +60 oC (ambient temperature +25oC to +85oC). The worst case ∆VOUT for the given conditions is -1.13V. The shift in VOUT is attributed to the following: -1.55V manufacturing tolerances, +1.33V external resistors, -0.62V load regulation and -0.29V temperature effects. Regulator With Zener (EQ. 1B) VOUT = 1.18 + VZ HIP5600 RF1 VIN VOUT ∆RF2 RF 1 + RF2 ∆V OUT = ∆V T REF -------------------------- + ∆I T ADJ RF2 + I A DJ RF 2 ------------- ADJ Error Budget RF2 R F2 ∆R F2 ∆RF1 + V RE F ---------- -------------- – -------------- R F1 R F2 R F1 (EQ. 2A) Where; VREF IADJ T ∆V RE F ≡ ∆V REF + V REF LOA DREG ( ∆I OUT ) + V REF TC ( ∆Temp ) +V TC ( θ ) ∆( IOUT ⋅ V IN ) + V REF SA REFLINEREG (EQ. 2B) ∆I T ADJ ≡ ∆I ADJ + I A DJ +I ADJ TC ( θ LO ADRE G SA ( ∆I OUT ) + IADJ TC ( ∆Te mp ) ) ∆( I OUT ⋅ V IN ) Note: (EQ. 2C) ∆RFx = % tolerance of resistor x --------------RFx Equations 2(A,B,C) are provided to determine the worst case output voltage in relation to; manufacturing tolerances (∆VREF and ∆IREF),% tolerance in external resistors (∆RF1/RF1, ∆RF2/RF2), load regulation (VREF LOAD REG , IADJ LOAD REG ), line regulation (VREF LINE REG) and the effects of temperature (VREFTC, IREFTC), which includes self heating (θSA). 66 AC/DC I1 RF1 VOUT VZ VOUT VZ 3.7V 2.5V 5.1V 3.9V 10.3V 9.1V 12.2V 11V 16.2V 15V RF1 = 10k AC/DC FIGURE 3. The output voltage can be set by using a zener diode (Figure 3) instead of the resistor divider shown in Figure 2. The zener diode improves the ripple rejection ratio and reduces the value of the worst case output voltage, as illustrated in the example to follow. The bias current of the zener diode is set by the value of RF1 and IADJ. The regulator / zener diode becomes an attractive solution if ripple rejection or the worst case tolerance of the output voltage is critical (i.e. one zener diode cost less than one 10µF capacitor (C3) and one 1/4W resistor RF2). Minimum power dissipation is possible by reducing I1 current, with little effect on the output voltage regulation. The output voltage is given in Equation 3. Equations 4(A,B, C) are provided to determine the worst case output voltage in relation to; manufacturing tolerances HIP5600 = V REF + V Z (EQ. 3) Error Budget HIP5600 REF TC ( θ SA ) ∆( I OUT ⋅ V IN ) + V REFLINEREG ∆V T Z ≡ V Z to l er an ce ( V Z ) + V Z TC ( ∆Te mp ) RS (EQ. 4B) I1 RF1 VREF (EQ. 4C) of HIP5600 and the zener diode (∆VREF and ∆Vz), load regulation of the HIP5600 (VREF LOAD REG), and the effects of temperature on the HIP5600 and the zener diode (VREFTC, VZTC). Example: Given: VIN = 200V, V OUT = 14.18V (VREF = 1.18V, VZ = 13V), ∆VZ = 5%, VZTC = +0.079%/ °C (assumes 1N5243BPH), ∆IOUT equal 10mA and ∆Temp equal +60 oC. The worst case ∆VOUT is 0.4956V. The shift in VOUT is attributed to the following: -0.2 (HIP5600) and 0.69 (zener diode). The regulator/zener diode configuration gives a 3.5% (0.49/14.18) worst case output voltage error where, for the same conditions, the regulator/resistor configuration results in an 7.5% (1.129/15) worst case output voltage error. External Capacitors IADJ An optional bypass capacitor (C3) from VADJ to ground improves the ripple rejection by preventing the ripple at the Adjust pin from being amplified. Bypass capacitors larger than 10µF do not appreciably improve the ripple rejection of the part (see Figure 20 through Figure 25). VREF I1 RF1 VOUT IADJ AC/DC (B) FIGURE 4. VOUT RF2 AC/DC Protection Diodes The HIP5600, unlike other voltage regulators, is internally protected by input diodes in the event the input becomes shorted to ground. Therefore, no external protection diode is required between the input pin and the output pin to protect against the output capacitor (C2) discharging through the input to ground. If the output is shorted in the absence of D1 (Figure 5), the bypass capacitor voltage (C3) could exceed the absolute maximum voltage rating of ±5V between VOUT and VIN . Note; No protection diode (D1) is needed for output voltages less than 6V or if C3 is not used. A minimum10µF output capacitor (C2) is required for stability of the output stage. Any increase of the load capacitance greater than 10µF will merely improve the loop stability and output impedance. VIN HIP5600 ADJ A 0.02µF input decoupling capacitor (C1) between VIN and ground may be required if the power source impedance is not sufficiently low for the 1MHz - 10MHz band. Without this capacitor, the HIP5600 can oscillate at 2.5MHz when driven by a power source with a high impedance for the 1MHz 10MHz band. RS RF2 (A) AC/DC VIN ADJ ( ∆I OUT ) + V REF TC ( ∆Temp ) VOUT LOADREG VIN ≡ ∆V REF + V RE F AC/DC C1 0.02µF D1 PROTECTS AGAINST C3 DISCHARGING WHEN THE OUTPUT IS SHORTED. VIN +V REF ADJ ∆VT HIP5600 (EQ. 4A) ∆V OUT = ∆V T REF + ∆V T Z VOUT OUT VOUT V + VOUT RF1 C3 10µF RF2 D1 C2 10µF FIGURE 5. REGULATOR WITH PROTECTION DIODE Load Regulation Selecting the Right Heat Sink For improved load regulation, resistor RF1 (connected between the adjustment terminal and VOUT) should be tied directly to the output of the regulator (Figure 4A) rather than near the load Figure 4B. This eliminates line drops (RS) from appearing effectively in series with RF1 and degrading regulation. For example, a 15V regulator with a 0.05Ω resistance between the regulator and the load will have a load regulation due to line resistance of 0.05Ω x ∆IL. If RF1 is connected near the load the effective load regulation will be 11.9 times worse (1+R2/R1, where R2 = 12k, R1 = 1.1k). Linear power supplies can dissipate a lot of power. This power or heat must be safely dissipated to permit continuous operation. This section will discuss thermal resistance and show how to calculate heat sink requirements. 67 Electronic heat sinks are generally rated by their thermal resistance. Thermal resistance is defined as the temperature rise per unit of heat transfer or power dissipated, and is expressed in units of degrees centigrade per watt. For a particular application determine the thermal resistance (θSA) which the heat sink must have in order to maintain a junction temperature below the thermal shut down limit (TTS). HIP5600 A thermal network that describes the heat flow from the integrated circuit to the ambient air is shown in Figure 6. The basic relation for thermal resistance from the IC surface, historically called “junction”, to ambient (θJA) is given in Equation 5. The thermal resistance of the heat sink (θSA) to maintain a desired junction temperature is calculated using Equation 6. Example, Given: VIN = 400VDC VOUT = 15V ILOAD = 15mA θJC = 4.8oC/W TTS = +127οC IADJ = 80µA TA = +50oC RF1 = 1.1k VREF = 1.18V P = 6.2W = (VIN - VOUT)(IIN ) PD I TJ = JUNCTION θJC TC = CASE Solution: θSA HEAT SINK ° C -------- W ∴ θ SA + θ CS ≈θ T TS – T A -–θ JC SA = --------------------------P Use Equation 6, (EQ. 7) (EQ. 8) (EQ. 5) The selection of a heat sink with θSA less than +7.62oC/W would ensure that the junction temperature would not exceed the thermal shut down temperature (TTS) of +127×oC. A Thermalloy P/N7023 at 6.2W power dissipation would meet this requirement with a θSA of +5.7×oC/W. (EQ. 6) Operation Without A Heatsink Where: and LOAD °C 127 ° C – 50 ° C θ SA = ------------------------------------------- – 4.8 ° C = 7.62 -------6.2 W FIGURE 6. θ JA = θJC + θ CS + θ SA RF1 –T T TS A θ SA = ---------------------------- – θ JC P TA = AMBIENT AIR θ JA = ---------------------P ADJ V REF + ------------------- + I Find: Proper heat sink to keep the junction temperature of the HIP5600 from exceeding TTS (+127oC). θCS TS = HEAT SINK TJ – T A IN ≡I T = T J TS Where: θJA = (Junction to Ambient Thermal Resistance) The sum of the thermal resistances of the heat flow path. θJA = θJC + θCS + θSA TJ = (Junction Temperature) The desired maximum junction temperature of the part. TJ = TTS TTS = (Thermal Shutdown Temperature) The maximum junction temperature that is set by the thermal protection circuitry of the HIP5600 (min = +127oC, typ = +134oC and max = +142oC). θJC = (Junction to Case Thermal Resistance) Describes the thermal resistance from the IC surface to its case. θJC = 4.8oC/W θCS = (Case to Mounting Surface Thermal Resistance) The resistance of the mounting interface between the transistor case and the heat sink. For example, mica washer. θSA = (Mounting Surface to Ambient Thermal Resistance) The resistance of the heat sink to the ambient air. Varies with air flow. The package has a θJA of +60oC/W. This allows 0.7W power dissipation at +85oC in still air. Mounting the HIP5600 to a printed circuit board (see Figure 39 through Figure 41) decreases the thermal impedance sufficiently to allow about 1.6W of power dissipation at +85oC in still air. Thermal Transient Operation For applications such as start-up, the HIP5600 in the TO-220 package can operate at several watts -without a heat sinkfor a period of time before going into thermal shutdown. PD = I IN (VIN - VOUT) TJ = JUNCTION 0.6θJC CD DIE/PACKAGE INTERFACE 0.4θJC 0.5C P TS = HEAT SINK OR CASE θSA TA = AMBIENT AIR CS + 0.5CP TA = Ambient Temperature P = The power dissipated by the HIP5600 in watts. P = (VIN - VOUT)(IOUT) Worst case θSA is calculated using the minimum TTS of +127oC in Equation 6. 68 FIGURE 7. THERMAL CAPACITANCE MODEL OF HIP5600 Figure 7 shows the thermal capacitances of the TO-220 package, the integrated circuit and the heat sink, if used. When power is initially applied, the mass of the package absorbs heat which limits the rate of temperature rise of the HIP5600 junction. With no heat sink CS equals zero and θSA equals the difference between θJA and θJC. The following equations predict the transient junction temperature and the time to thermal shutdown for ambient temperatures up to +85oC and power levels up to 8W. The output current limit temperature coefficient (Figure 39) precludes continuous operation above 8W. –t T ≡ 1 (EQ. 9) -------- 1 – e τ1 Pθ SA (EQ. 11B) τ1 ≡ θ SA ( C P + C S ) Where: τ ≡ θSA ( C P + C S ) t = (EQ. 11A) Where: –t ----- TJ ( t ) = TA + PθJC + PθSA 1 – e τ TJ ( t ) = TA + T1 + T2 + T3 –t -------- T 2 ≡ 0.4Pθ JC 1 – e τ2 P ( θ JC + θ SA ) + T A – T TS – τln ------------------------------------------------------------------- PθSA (EQ. 10) Where: ( 0.5C P + C S ) 0.5C P τ2 ≡ 0.7θJC ------------------------------------------------------------ CP + C S For the TO-220, CP is 0.9Ws to 1.1Ws per degree compared to about 2.6mWs per degree for the integrated circuit and C S is 0.9Ws per degree per gram for aluminum heat sinks. –t Figure 8 shows the time to thermal shutdown versus power dissipation for a part in +22oC still air and at various elevated ambient temperatures with a θSA of +27oC/W from forced air flow. For the shorter shutdown times, the θSA value is not important but the thermal capacitances are. A more accurate equation for the transient silicon surface temperature can be derived from the model shown in Figure 7. Due to the distributed nature of the package thermal capacitance, the second time constant is 1.7 times larger than expected. 10 2 (EQ. 11C) T ≡ 3 -------- 0.6Pθ 1 – e τ3 JC Where: τ3 ≡ 0.6θ (EQ. 11D) C JC D Thermal Shutdown Hysteresis Figure 9 shows the HIP5600 thermal hysteresis curve with VIN = 100VDC , VOUT = 5V and IOUT = 10mA. Hysteresis is added to the thermal shutdown circuit to prevent oscillations as the junction temperature approaches the thermal shutdown limit. The thermal shutdown is reset when the input voltage is removed, goes negative (i.e. AC operation) or when the part cools down. 10 1 +22×oC +70×oC +85×oC 10 0 HEATING 8.0 IOUT (mA) TIME TO THERMAL SHUTDOWN (s) 10 SHUTDOWN REGION 6.0 4.0 COOLING 2.0 +100×oC 10-1 0.0 98.0 +115× oC 2.0 4.0 6.0 8.0 POWER DISSIPATION (W) FIGURE 8. TIME TO THERMAL SHUTDOWN vs POWER DISSIPATION 69 113.0 120 127 CASE TEMPERATURE (oC) 135 142 FIGURE 9. THERMAL HYSTERESIS CURVE +120 o×C 10-2 0.0 105.0 10 AC to DC Operation Since the HIP5600 has internal high voltage diodes in series with its input, it can be connected directly to an AC power line. This is an improvement over typical low current supplies constructed from a high voltage diode and voltage dropping resistor to bias a low voltage zener. The HIP5600 provides better line and load regulation, better efficiency and heat HIP5600 transfer. The latter because the TO-220 package permits easy heat sinking. The efficiency of either supply is approximately the DC output voltage divided by the RMS input voltage. The resistor value, in the typical low current supply, is chosen such that for maximum load at minimum line voltage there is some current flowing into the zener. This resistor value results in excess power dissipation for lighter loads or higher line voltages. Using the circuit in Figure 3 with a 1000µF output capacitor the HIP5600 only takes as much current from the power line as the load requires. For light loads, the HIP5600 is even more efficient due to it’s interaction with the output capacitor. Immediately after the AC line goes positive, the HIP5600 tries to replace all the charge drained by the load during the negative half cycle at a rate limited by the short circuit current limit (see “A1” and “B1” Figure 10). Since most of this charge is replaced before the input voltage reaches its RMS value, the power dissipation for this charge is lower than it would be if the charge were transferred at a uniform rate during the cycle. When the product of the input voltage and current is averaged over a cycle, the average power is less than if the input current were constant. Figure 11 shows the HIP5600 efficiency as a function of load current for 80VRMS and 132VRMS inputs for a 15.6V output. Referring again to Figure 10, Curve “A1” shows the input current for a 10mA output load and curve “B1” with a 3mA output load. The input current spike just before the negative going zero crossing occurs while the input voltage is less than the minimum operating voltage but is so short it has no detrimental effect. The input current also includes the charging current for the 0.02µF input decoupling capacitor C1. The maximum load current cannot be greater than 1/2 of the short circuit current because the HIP5600 only conducts over 1/2 of the line cycle. The short circuit current limit (Figure 38) depends on the case temperature, which is a function of the power dissipation. Figure 38 for a case temperature of +100oC (i.e. no heat sink) indicates for AC operation the maximum available output current is 10mA (1/2 x 20mA). Operation from full wave rectified input will increase the maximum output current to 20mA for the same +100oC case temperature. As a reminder, since the HIP5600 is off during the negative half cycle, the output capacitor must be large enough to supply the maximum load current during this time with some acceptable level of droop. Figure 10 also shows the output ripple voltage, for both a 10mA and 3mA output loads “A2” and “B2”, respectively. Do’s And Don’ts DC Operation 120VRMS, 60Hz I IN 1. Do not exceed the absolute maximum ratings. 2. The HIP5600 requires a minimum output current of 1mA. Minimum output current includes current through RF1. Warning: If there is less than 1mA load current, the output voltage will rise. If the possibility of no load exists, RF1 should be sized to sink 1mA under these conditions. 20mA/DIV. A1 B1 V REF 1.07V RF1 MIN = ------------------ = ---------------- = 1kΩ 1mA 1mA B2 VOUT A2 3. Do not “HOT” switch the input voltage without protecting the input voltage from exceeding ±650V. Note: inductance from supplies and wires along with the 0.02µF decoupling capacitor can form an under damped tank circuit that could result in voltages which exceed the maximum ±650V input voltage rating. Switch arcing can further aggravate the effects of the source inductance creating an over voltage condition. 2ms/DIV. 100mV/DIV. FIGURE 10. AC OPERATION 25 VIN = 80VRMS 23 Recommendation: Adequate protection means (such as MOV, avalanche diode, surgector, etc.) may be needed to clamp transients to within the ±650V input limit of the HIP5600. EFFICIENCY (%) 21 19 18 VIN = 132VRMS 16 14 12 10 VOUT = 15.6VDC 0.0 5.0 10.0 LOAD CURRENT (mA) 15.0 FIGURE 11. EFFICIENCY AS A FUNCTION OF LOAD CURRENT 70 4. Do not operate the part with the input voltage below the minimum 50VDC recommended. Low voltage operation: For input voltages between 0V DC and +5VDC nothing happens (IOUT = 0), for input voltages between +5V DC and +35V DC there is not enough voltage for the pass transistor to operate properly and therefore a high frequency (2MHz) oscillation occurs. For input voltages +35VDC to +50VDC proper operation can occur with some parts. HIP5600 5. Warning: the output voltage will approach the input voltage if the adjust pin is disconnected, resulting in permanent damage to the low voltage output capacitor. AC Operation minimized by connecting the test equipment ground as close to the circuit ground as possible. CAUTION: Dangerous voltages may appear on exposed metal surfaces of AC powered test equipment. 1. Do not exceed the absolute maximum ratings. Application Circuits + 50VDC TO 400VDC BUS HIP5600 0.5m A C1 0.02µF ± VIN 0.5mA ADJ V REF 1.07V RF1 MIN = ------------------ = ------------------ = 2kΩ VOUT 2. The HIP5600 requires a minimum output current of 0.5mA. Minimum output current includes current through RF1. Warning: If there is less than 0.5mA output current, the output voltage will rise. If the possibility of no load exists, RF1 should be sized to sink 0.5mA under these conditions. + VOUT 3. If using a laboratory AC source (such as VARIACs or step-up transformers, etc.) be aware that they contain large inductances that can generate damaging high voltage transients when they are switched on or off. RF1 C3 10µF Recommendations C2 10µF RF2 (1) Preset VARIAC output voltage before applying power to part. (2) Adequate protection means (such as MOV, avalanche diode, surgector, etc.) may be needed to clamp transients to within the ±650V input limit of the HIP5600. 4. Do not operate the part with the input voltage below the minimum 50VRMS recommended. Low voltage operation similar to DC operation (reference step 4 under DC operation). 5. Warning: the output voltage will approach the input voltage if the adjust pin is disconnected, resulting in permanent damage to the low voltage output capacitor. FIGURE 12. DC/DC CONVERTER The HIP5600 can be configured in most common DC linear regulator applications circuits with an input voltage between 50VDC to 400VDC (above the output voltage) see Figure 12. A 10µF capacitor (C2) provides stabilization of the output stage. Heat sinking may be required depending upon the power dissipation. Normally, choose RF1 << VREF / IADJ. (NOTE 1) 1kΩ General Precautions HIP5600 Recommendations for Evaluation of the HIP5600 in the Lab a) The use of battery powered DVMs and scopes will eliminate ground loops. b) When connecting test equipment, locate grounds as close to circuit ground as possible. c) Input current measurements should be made with a noncontact current probe. If AC powered test equipment is used, then the use of an isolated plug is recommended. The isolated plug eliminates any voltage difference between earth ground and AC ground. However, even though the earth ground is disconnected, ground loop currents can still flow through transformer of the test equipment. Ground loops can be 71 C1 0.02µF VIN ADJ Background: Input to output parasitic impedances exist in most test equipment power supplies. The inter-winding capacitance of the transformer may result in substantial current flow (mA) from the equipment power lines to the DC ground of the HIP5600. This “ground loop” current can result in erroneous measurements of the circuits performance and in some cases lead to overstress of the HIP5600. VOUT Instrumentation Effects + VOUT RF1 C3 10µF C2 10µF SURGE PROTECTION NOTE 1. 200VRMS - 280VRMS Operation Only RF2 FIGURE 13. AC/DC CONVERTER The HIP5600 can operate from an AC voltage between 50V RMS to 280VRMS, see Figure 13. The combination of a 1kΩ (2W) input resistor and a V275LA10B MOV provides input surge protection up to 6kV 1.2 x 50µs oscillating and pulse waveforms as defined in IEEE/ANSI C62.41.1980. When operating from 120VAC , a V130LA10B MOV provides protection without the 1kΩ resistor. The output capacitor is larger for operation from AC than DC because the HIP5600 only conducts current during the positive half cycle of the AC line. The efficiency is approximately equal to V OUT /V IN (RMS), see Figure 11. HIP5600 The HIP5600 provides an efficient and economical solution as a start-up supply for applications operating from either AC (50VRMS to 280VRMS) or DC (50VDC to 400V DC). + 50VDC TO 400VDC BUS VIN ADJ VOUT HIP5600 RF1 10µF part, the amount of heat sinking (if any) and the ambient temperature. For example; at 400VDC with no heat sink, it will provide 20mA for about 8s, see Figure 8. Power supply efficiency is improved by turning off the HIP5600 when the SMPS is up and running. In this application the output of the HIP5600 would be set via RF1 and RF2 to be about 9V. The tickler winding would be adjusted to about 12V to insure that the HIP5600 is kept off during normal operating conditions.The input current under these conditions is approximately equal to IBIAS. (See Figure 27). ± The HIP5600 can supply a 450µA (±20%) constant current. (See Figure 15). It makes use of the internal bias network. See Figure 27 for bias current versus input voltage. +12V With the addition of a potentiometer and a 10µF capacitor the HIP5600 will provide a constant current source. IOUT is given by Equation 13 in Figure 16. RF2 VOUT PWM FIGURE 14. START UP CIRCUIT The HIP5600 has on chip thermal protection and output current limiting circuitry. These features eliminate the need for an in-line fuse and a large heat sink. The HIP5600 can provide up to 40mA for short periods of time to enable start up of a switch mode power supply‘s control circuit. The length of time that the HIP5600 will be on, prior to thermal shutdown, is a function of the power dissipation in the The HIP5600 can control a P-channel MOSFET or IGPT in a self-oscillating buck regulator. The circuit shown (Figure 17) shows the self-oscillating concept with a P-IGBT driving a dedicated fan load. The output voltage is set by the resistor combination of RF1, RF2, and RF3. Components C3 and RF3 impresses the output ripple voltage across RF1 causing the HIP5600 to oscillate and control the conduction of the P-IGBT. The start-up protection components limit the initial surge current in the P-IGBT by forcing this device into its active region. The snubber circuit is recommended to reduce the power dissipation of the P-IGBT. +50VDC TO +400VDC HIP5600 0.02µF +20VDC TO +400VDC R1 IOUT NOTES: LOAD 1. V OUT Floating 2. Fixed 500µA Current Source IOUT ± FIGURE 15. CONSTANT 450µA CURRENT SOURCE 72 ± VIN ADJ VOUT VIN VOUT ADJ HIP5600 IOUT = 1.21V R1 (EQ. 13) 10µF FIGURE 16. ADJUSTABLE CURRENT SOURCE HIP5600 START-UP PROTECTION P-IGBT HIP5600 VIN ADJ VOUT SNUBBER CIRCUIT RF1 + RF2 C3 - DC FAN RF3 FIGURE 17. HIGH CURRENT “BUCK” REGULATOR CONCEPT -0.8 -1.0 1mA TO 20mA -1.2 -1.4 -1.6 1mA TO 30mA -40 -20 VIN = 50VDC 0 25 40 60 CASE TEMPERATURE (oC) 80 100 -1 -2 1mA TO 10mA -3 -4 -5 -6 1mA TO 20mA -7 -8 1mA TO 30mA VIN = 400VDC -9 -10 -40 -20 0 25 40 CASE TEMPERATURE (oC) 60 80 FIGURE 18. LOAD REGULATION vs TEMPERATURE FIGURE 19. LOAD REGULATION VS. TEMPERATURE 85 90 VIN = 400VDC, IL = 10mA, f = 120Hz, T C = +25oC VIN = 170VDC, IL = 10mA, f = 120Hz, TC = +25 oC 80 RIPPLE REJECTION (dB) 1mA TO 10mA -0.6 OUTPUT VOLTAGE DEVIATION (%) -0.4 80 75 70 1µF BYPASS CAPACITOR 10µF BYPASS CAPACITOR 65 60 55 NO BYPASS CAPACITOR 50 45 0 10 20 30 40 50 60 70 80 OUTPUT VOLTAGE (V) 90 100 110 FIGURE 20. RIPPLE REJECTION RATIO (OUTPUT VOLTAGE) 73 RIPPLE REJECTION (dB) OUTPUT VOLTAGE DEVIATION (%) Typical Performance Curves 70 1µF BYPASS CAPACITOR 10µF BYPASS CAPACITOR 60 50 NO BYPASS CAPACITOR 40 30 0 50 100 150 200 250 OUTPUT VOLTAGE (V) 300 350 FIGURE 21. RIPPLE REJECTION RATIO (OUTPUT VOLTAGE) HIP5600 Typical Performance Curves 85 85 VIN = 170VDC, IL = 10mA, VOUT = 15V, TC = +25oC 80 75 70 65 60 55 1µF BYPASS CAPACITOR 50 45 10 70 65 60 55 1µF BYPASS CAPACITOR 1M 45 10M 1 10 RIPPLE REJECTION (dB) 75 70 1µF BYPASS CAPACITOR 10µF BYPASS CAPACITOR 60 55 NO BYPASS CAPACITOR 0 5 10k 100k 1M 10M VIN = 400VDC, VOUT = 10mA, f = 120Hz, TC = +25oC 80 (REFERENCE FIGURE 3) 65 1k FIGURE 23. RIPPLE REJECTION RATIO (INPUT FREQUENCY) VIN = 170VDC, VOUT = 10mA, f = 120Hz, TC = +25oC 80 100 INPUT FREQUENCY (Hz) 85 85 RIPPLE REJECTION (dB) 75 NO BYPASS CAPACITOR 100 1k 10k 100k INPUT FREQUENCY (Hz) FIGURE 22. RIPPLE REJECTION RATIO (INPUT FREQUENCY) 50 10µF BYPASS CAPACITOR 50 NO BYPASS CAPACITOR 1 VIN = 400VDC , IL = 10mA, VOUT = 15V, TC = +25 oC 80 10µF BYPASS CAPACITOR RIPPLE REJECTION (dB) RIPPLE REJECTION (dB) (Continued) (REFERENCE FIGURE 3) 75 70 1µF BYPASS CAPACITOR 65 10µF BYPASS CAPACITOR 60 NO BYPASS CAPACITOR 55 10 15 20 25 OUTPUT CURRENT (mA) 30 50 35 FIGURE 24. RIPPLE REJECTION RATIO (OUTPUT CURRENT) 0 5 10 15 20 25 OUTPUT CURRENT (mA) 30 35 FIGURE 25. RIPPLE REJECTION RATIO (OUTPUT CURRENT) 520 IOUT = 0 510 500 C2 = 0.01µF, C3 = 0µF TC = +100oC 490 IBIAS (µA) OUTPUT IMPEDANCE (Ω) 100 10.0 C2 = 10µF, C3 = 0µF 480 TC = -40oC 470 460 TC = +25 oC 450 1.0 440 C2 = 10µF, C3 = 10µF 430 0.1 10 100 1K 10K FREQUENCY (Hz) 100K FIGURE 26. OUTPUT IMPEDANCE 74 1M 420 50 100 200 300 INPUT VOLTAGE (VDC) FIGURE 27. IBIAS vs INPUT VOLTAGE 400 HIP5600 Typical Performance Curves (Continued) 100mV/DIV C3 = 10µF VOUT 20mV/DIV 15V VOUT C3 = 10µF C3 = 0µF 15V 400V VOUT = 15VDC IL= 5mA TJ = +25oC 100V OUTPUT CURRENT 100V/DIV INPUT VOLTAGE T = 100ms/DIV 0V C3 = 0µF FIGURE 29. LOAD TRANSIENT RESPONSE VIN = 400VDC 1mA REFERENCE VOLTAGE (V) REFERENCE VOLTAGE (V) 1.25 VIN = 50VDC 1.18 5mA 1.17 1.16 10mA 1.15 1.14 30mA 1.13 1.12 20mA 1.11 -40 -20 0 25 40 60 CASE TEMPERATURE (oC) 80 1mA 1.20 5mA 1.15 10mA 1.10 20mA 1.05 1.00 100 30mA -40 -20 0 25 40 60 80 CASE TEMPERATURE (oC) FIGURE 30. REFERENCE VOLTAGE vs TEMPERATURE FIGURE 31. REFERENCE VOLTAGE vs TEMPERATURE 1.20 1.20 1.19 IOUT = 10mA 1.18 1.17 TC = -40oC REFERENCE VOLTAGE (V) REFERENCE VOLTAGE (V) 1.10 T= 100ms/DIV 0mA 1.21 1.19 VIN = 400VDC VOUT = 15V TJ = +25 oC 5mA FIGURE 28. LINE TRANSIENT RESPONSE 1.20 5mA/DIV 10mA 1.16 1.15 1.14 TC = +25o C 1.13 1.12 1.11 1.10 TC = +100oC 1.09 1.08 0 100 200 300 INPUT VOLTAGE (VDC) 400 FIGURE 32. REFERENCE VOLTAGE vs INPUT VOLTAGE 75 1.18 1mA 1.16 5mA 1.14 10mA 1.12 1.10 20mA 1.08 30mA 1.06 1.04 0 100 200 300 INPUT VOLTAGE (VDC) 400 FIGURE 33. REFERENCE VOLTAGE vs VIN; CASE TEMPERATURE OF +25oC HIP5600 Typical Performance Curves (Continued) 80 80 VIN = 400VDC VIN = 50VDC 75 75 ADJ CURRENT (µA) ADJ CURRENT (µA) 1mA 70 20mA 65 60 30mA 55 10mA 5mA 65 1mA 60 20mA 55 30mA 50 50 45 70 45 -40 -20 0 25 40 60 CASE TEMPERATURE (oC) 80 -40 100 -20 FIGURE 34. IADJ vs TEMPERATURE 0 25 40 CASE TEMPERATURE (oC) 2000 VIN = 100VDC TC = 25oC TC = +25oC 1500 CURRENT (µA) 765 760 TC = +100oC 755 MINIMUM LOAD CURRENT 1000 BIAS CURRENT IIN 500 IOUT 750 100 200 300 0 400 IADJ 1 2 INPUT VOLTAGE (VDC) FIGURE 36. MINIMUM LOAD CURRENT vs V IN 3 VOUT - VADJ (VDC) 50 TC = -40 oC 45 40 TC = +25oC 35 30 TC = +100oC 25 20 50 100 150 200 250 300 350 INPUT-OUTPUT (VDC) FIGURE 38. CURRENT LIMIT vs TEMPERATURE 76 4 FIGURE 37. TERMINAL CURRENTS vs FORCED VREF 55 OUTPUT CURRENT (mA) LOAD CURRENT (µA) 770 50 80 FIGURE 35. IADJ vs TEMPERATURE 775 745 60 400 5 HIP5600 Evaluation Boards θSA = 22oC/W HEAT SINK VIN ADJ F1 3.25” 3.25” HIP5600 VOUT RF1 RS VIN + C2 MOV C1 RF2 C3 VOUT HIP5600 EVALUATION BOARD 3.25” 3.25” FIGURE 39. EVALUATION BOARD (TOP) FIGURE 40. EVALUATION BOARD METAL MASK (BOTTOM) 3.25” HEAT SINK ADJ VIN VOUT + - VIN VOUT HIP5600 EVALUATION BOARD 3.25” FIGURE 41. EVALUATION BOARD METAL MASK (TOP) 77 HIP5600 Single-In-Line Plastic Packages (SIP) ØP Z3.1B A E F 3 LEAD PLASTIC SINGLE-IN-LINE PACKAGE INCHES Q H1 D L1 b1 L b 1 2 c1 3 e e1 J1 NOTES: 1. Lead dimension and finish uncontrolled in zone L1. 2. Position of lead to be measured 0.250 inches (6.35mm) from bottom of dimension D. 3. Position of lead to be measured 0.100 inches (2.54mm) from bottom of dimension D. 4. Controlling dimension: INCH. 78 MILLIMETERS SYMBOL MIN MAX MIN MAX NOTES A 0.140 0.190 3.56 4.82 - b 0.015 0.040 0.38 1.02 - b1 0.045 0.070 1.14 1.77 1 c1 0.014 0.022 0.36 0.56 1 D 0.560 0.650 14.23 16.51 - E 0.380 0.420 9.66 10.66 - e 0.090 0.110 2.29 2.79 2 e1 0.190 0.210 4.83 5.33 2 F 0.020 0.055 0.51 1.39 - H1 0.230 0.270 5.85 6.85 - J1 0.080 0.115 2.04 2.92 3 L 0.500 0.580 12.70 14.73 - L1 - 0.250 6.35 1 - ØP 0.139 0.161 3.53 4.08 - Q 0.100 0.135 2.54 3.43 Rev. 1 2/95