INTERSIL EL5364IU-T13

EL5164, EL5165, EL5364
®
Data Sheet
August 10, 2005
600MHz Current Feedback Amplifiers with
Enable
The EL5164, EL5165, and EL5364 are current feedback
amplifiers with a very high bandwidth of 600MHz. This
makes these amplifiers ideal for today’s high speed video
and monitor applications.
With a supply current of just 5mA and the ability to run from
a single supply voltage from 5V to 12V, the amplifiers are
also ideal for hand held, portable or battery-powered
equipment.
The EL5164 also incorporates an enable and disable
function to reduce the supply current to 100µA typical per
amplifier. Allowing the CE pin to float or applying a low logic
level will enable the amplifier.
The EL5165 is offered in the 5-pin SOT-23 package, EL5164
is available in the 6-pin SOT-23 and the industry-standard
8-pin SO packages, and the EL5364 in a 16-pin SO and
16-pin QSOP packages. All operate over the industrial
temperature range of -40°C to +85°C.
FN7389.5
Features
• 600MHz -3dB bandwidth
• 4700V/µs slew rate
• 5mA supply current
• Single and dual supply operation, from 5V to 12V supply
span
• Fast enable/disable (EL5164 & EL5364 only)
• Available in SOT-23 packages
• Dual (EL5264 & EL5265) and triple (EL5362 & EL5363)
also available
• High speed, 1GHz product available (EL5166 & EL5167)
• 300MHz product available (EL5162 family)
• Pb-Free plus anneal available (RoHS compliant)
Applications
• Video amplifiers
• Cable drivers
• RGB amplifiers
• Test equipment
• Instrumentation
• Current to voltage converters
1
CAUTION: These devices are sensitive to electrostatic discharge; follow proper IC Handling Procedures.
1-888-INTERSIL or 1-888-468-3774 | Intersil (and design) is a registered trademark of Intersil Americas Inc.
Copyright Intersil Americas Inc. 2004, 2005. All Rights Reserved
All other trademarks mentioned are the property of their respective owners.
EL5164, EL5165, EL5364
Ordering Information (Continued)
Ordering Information
PART NUMBER
EL5164IS
PACKAGE
TAPE &
REEL
PKG.
DWG. #
8-Pin SO
-
MDP0027
PACKAGE
TAPE &
REEL
PKG.
DWG. #
EL5364IS-T13
16-Pin SO (0.150”)
13”
MDP0027
EL5364ISZ
(See Note)
16-Pin SO (0.150”)
(Pb-free)
-
MDP0027
PART NUMBER
EL5164IS-T7
8-Pin SO
7”
MDP0027
EL5164IS-T13
8-Pin SO
13”
MDP0027
EL5164ISZ
(See Note)
8-Pin SO
(Pb-free)
-
MDP0027
EL5364ISZ-T7
(See Note)
16-Pin SO (0.150”)
(Pb-free)
7”
MDP0027
EL5164ISZ-T7
(See Note)
8-Pin SO
(Pb-free)
7”
MDP0027
EL5364ISZ-T13
(See Note)
16-Pin SO (0.150”)
(Pb-free)
13”
MDP0027
EL5164ISZ-T13
(See Note)
8-Pin SO
(Pb-free)
13”
MDP0027
16-Pin QSOP
-
MDP0040
EL5364IU-T7
16-Pin QSOP
7”
MDP0040
EL5164IW-T7
6-Pin SOT-23
7” (3K pcs)
MDP0038
EL5364IU-T13
16-Pin QSOP
13”
MDP0040
EL5164IW-T7A
6-Pin SOT-23
7” (250 pcs)
MDP0038
MDP0040
6-Pin SOT-23
(Pb-free)
7” (3K pcs)
MDP0038
16-Pin QSOP
(Pb-free)
-
EL5164IWZ-T7
(See Note)
EL5364IUZ
(See Note)
MDP0040
6-Pin SOT-23
(Pb-free)
7” (250 pcs)
MDP0038
16-Pin QSOP
(Pb-free)
7”
EL5164IWZ-T7A
(See Note)
EL5364IUZ-T7
(See Note)
EL5364IUZ-T13
(See Note)
16-Pin QSOP
(Pb-free)
13”
MDP0040
EL5364IUZA
(See Note)
16-Pin QSOP
(Pb-free)
-
MDP0040
EL5364IUZA-T7
(See Note)
16-Pin QSOP
(Pb-free)
7”
MDP0040
EL5364IUZA-T13
(See Note)
16-Pin QSOP
(Pb-free)
13”
MDP0040
EL5165IC-T7
5-Pin SC-70
7” (3K pcs)
P5.049
EL5165IC-T7A
5-Pin SC-70
7” (250 pcs)
P5.049
EL5165IW-T7
5-Pin SOT-23
7” (3K pcs)
MDP0038
EL5165IW-T7A
5-Pin SOT-23
7” (250 pcs)
MDP0038
EL5165IWZ-T7
(See Note)
5-Pin SOT-23
(Pb-free)
7” (3K pcs)
MDP0038
EL5165IWZ-T7A
(See Note)
5-Pin SOT-23
(Pb-free)
7” (250 pcs)
MDP0038
EL5364IS
16-Pin SO (0.150”)
-
MDP0027
EL5364IS-T7
16-Pin SO (0.150”)
7”
MDP0027
EL5364IU
NOTE: Intersil Pb-free plus anneal products employ special Pb-free material sets;
molding compounds/die attach materials and 100% matte tin plate termination finish,
which are RoHS compliant and compatible with both SnPb and Pb-free soldering
operations. Intersil Pb-free products are MSL classified at Pb-free peak reflow
temperatures that meet or exceed the Pb-free requirements of IPC/JEDEC J STD-020.
Pinouts
EL5364
(16-PIN SO, QSOP)
TOP VIEW
EL5164
(8-PIN SO)
TOP VIEW
NC 1
IN- 2
IN+ 3
8 CE
+
7 VS+
CEA 2
6 OUT
VS- 3
5 NC
VS- 4
INA+ 1
CEB 4
16 INA+
14 VS+
+
-
INB+ 5
EL5165
(5-PIN SOT-23, SC-70)
TOP VIEW
OUT 1
VS- 2
5 VS+
CEC 7
12 INB11 NC
+
-
10 OUTC
INC+ 8
9 INC-
EL5164
(6-PIN SOT-23)
TOP VIEW
4 INOUT 1
VS- 2
IN+ 3
2
13 OUTB
NC 6
+ -
IN+ 3
15 OUTA
6 VS+
+ -
5 CE
4 IN-
FN7389.5
August 10, 2005
EL5164, EL5165, EL5364
Absolute Maximum Ratings (TA = 25°C)
Supply Voltage between VS+ and VS- . . . . . . . . . . . . . . . . . . . 13.2V
Maximum Continuous Output Current . . . . . . . . . . . . . . . . . . . 50mA
Pin Voltages . . . . . . . . . . . . . . . . . . . . . . . . . VS- -0.5V to VS+ +0.5V
Operating Junction Temperature . . . . . . . . . . . . . . . . . . . . . . . 125°C
Supply Slewrate between VS+ and VS- . . . . . . . . . . . . . 1V/µs (Max)
Power Dissipation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . See Curves
Storage Temperature . . . . . . . . . . . . . . . . . . . . . . . .-65°C to +150°C
Ambient Operating Temperature . . . . . . . . . . . . . . . .-40°C to +85°C
CAUTION: Stresses above those listed in “Absolute Maximum Ratings” may cause permanent damage to the device. This is a stress only rating and operation of the
device at these or any other conditions above those indicated in the operational sections of this specification is not implied.
IMPORTANT NOTE: All parameters having Min/Max specifications are guaranteed. Typical values are for information purposes only. Unless otherwise noted, all tests
are at the specified temperature and are pulsed tests, therefore: TJ = TC = TA
Electrical Specifications
VS+ = +5V, VS- = -5V, RF = 750Ω for AV = 1, RF = 375Ω for AV = 2, RL = 150Ω, VENABLE = VS+ - 1V,
TA = 25°C unless otherwise specified.
PARAMETER
DESCRIPTION
CONDITIONS
MIN
TYP
MAX
UNIT
AC PERFORMANCE
BW
-3dB Bandwidth
AV = +1, RL = 500Ω, RF = 510Ω
600
MHz
AV = +2, RL = 150Ω, RF = 412Ω
450
MHz
50
MHz
BW1
0.1dB Bandwidth
AV = +2, RL = 150Ω, RF = 412Ω
SR
Slew Rate
VOUT = -3V to +3V, AV = +2, RL = 100Ω
(EL5164, EL5165)
3500
4700
7000
V/µs
VOUT = -3V to +3V, AV = +2, RL = 100Ω
(EL5364)
3000
4200
6000
V/µs
tS
0.1% Settling Time
VOUT = -2.5V to +2.5V, AV = +2,
RF = RG = 1kΩ
15
ns
eN
Input Voltage Noise
f = 1MHz
2.1
nV/√Hz
iN-
IN- Input Current Noise
f = 1MHz
13
pA/√Hz
iN+
IN+ Input Current Noise
f = 1MHz
13
pA/√Hz
HD2
5MHz, 2.5VP-P
-81
dBc
HD3
5MHz, 2.5VP-P
-74
dBc
dG
Differential Gain Error (Note 1)
AV = +2
0.01
%
dP
Differential Phase Error (Note 1)
AV = +2
0.01
°
DC PERFORMANCE
VOS
Offset Voltage
TCVOS
Input Offset Voltage Temperature
Coefficient
ROL
Transimpedance
-5
Measured from TMIN to TMAX
1.5
+5
mV
6
µV/°C
1.1
3
MΩ
V
INPUT CHARACTERISTICS
CMIR
Common Mode Input Range
Guaranteed by CMRR test
±3
±3.3
CMRR
Common Mode Rejection Ratio
VIN = ±3V
50
62
75
dB
-ICMR
- Input Current Common Mode Rejection
-1
0.1
+1
µA/V
+IIN
+ Input Current
-10
2
+10
µA
-IIN
- Input Current
-10
2
+10
µA
RIN
Input Resistance
300
650
1200
kΩ
CIN
Input Capacitance
3
+ Input
1
pF
FN7389.5
August 10, 2005
EL5164, EL5165, EL5364
Electrical Specifications
VS+ = +5V, VS- = -5V, RF = 750Ω for AV = 1, RF = 375Ω for AV = 2, RL = 150Ω, VENABLE = VS+ - 1V,
TA = 25°C unless otherwise specified. (Continued)
PARAMETER
DESCRIPTION
CONDITIONS
MIN
TYP
MAX
UNIT
RL = 150Ω to GND
±3.6
±3.8
±4.0
V
RL = 1kΩ to GND
±3.9
±4.1
±4.2
V
Output Current
RL =10Ω to GND
100
140
190
mA
ISON
Supply Current - Enabled
No load, VIN = 0V
3.2
3.5
4.2
mA
ISOFF+
Supply Current - Disabled, per Amplifier
+25
µA
ISOFF-
Supply Current - Disabled, per Amplifier
No load, VIN = 0V
-25
-14
0
µA
PSRR
Power Supply Rejection Ratio
DC, VS = ±4.75V to ±5.25V
65
79
-IPSR
- Input Current Power Supply Rejection
DC, VS = ±4.75V to ±5.25V
-1
0.1
OUTPUT CHARACTERISTICS
VO
IOUT
Output Voltage Swing
SUPPLY
0
dB
+1
µA/V
ENABLE (EL5164 ONLY)
tEN
Enable Time
200
ns
tDIS
Disable Time
800
ns
IIHCE
CE Pin Input High Current
CE = VS+
1
10
+25
µA
IILCE
CE Pin Input Low Current
CE = (VS+) -5V
-1
0
+1
µA
VIHCE
CE Input High Voltage for Power-down
VILCE
CE Input Low Voltage for Power-down
VS+ - 1
V
VS+ - 3
V
NOTE:
1. Standard NTSC test, AC signal amplitude = 286mVP-P, f = 3.58MHz
4
FN7389.5
August 10, 2005
EL5164, EL5165, EL5364
Typical Performance Curves
5
3
VCC, VEE = ±5V
AV = +2
5
RF=1.2K, CL=5pF
4
RF=1.2K, CL=3.5pF
NORMALIZED GAIN (dB)
NORMALIZED GAIN (dB)
4
RF=1.2K, CL=2.5pF
2
RF=1.2K, CL=0.8pF
1
0
RF=1.5K, CL=0.8pF
-1
RF=1.8K, CL=0.8pF
-2
RF=2.2K, CL=0.8pF
-3
-4
3
VCC, VEE=±5V
CL=2.5pF
AV=+5
RF=160, RG=41
1
0
RF=300, RG=75
RF=360, RG=87
RF=397, RG=97
-1
-2
-3
RF=412, RG=100
RF=560, RG=135
-4
-5
100K
1M
10M
100M
-5
100K
1G
1M
FREQUENCY (Hz)
1G
6
VCC, VEE=±5V
CL=2.5pF
AV=+1
5
NORMALIZED GAIN (dB)
NORMALIZED GAIN (dB)
100M
FIGURE 2. FREQUENCY RESPONSE FOR VARIOUS RF
6
4
10M
FREQUENCY (Hz)
FIGURE 1. FREQUENCY RESPONSE FOR VARIOUS
RF AND CL
5
RF=220, RG=55
2
RF=510Ω
3
2
RF=681Ω
1
0
-1
RF=750Ω
-2
RF=909Ω
-3
RF=1201Ω
-4
100K
1M
10M
100M
4
3
2
VCC=+5V
VEE=-5V
CL=5pF
AV=+2
RL=150Ω
RF=412Ω
RF=562Ω
1
0
RF=681Ω
-1
RF=866Ω
-2
RF=1.2kΩ
-3
-4
100K
1G
RF=1.5kΩ
1M
10M
100M
1G
FREQUENCY (Hz)
FREQUENCY (Hz)
FIGURE 3. FREQUENCY RESPONSE FOR VARIOUS RF
FIGURE 4. FREQUENCY RESPONSE FOR VARIOUS RF
5
3
RL=150Ω
RF=422Ω
RG=422Ω
AMPLITUDE (V)
NORMALIZED GAIN (dB)
4
2
1
0
-1
VCC, VEE=
-2
-3
-4
-5
100K
1M
10M
6V
5V
4V
3V
2.5V
100M
OUTPUT
2V/DIV
1V/DIV
VCC, VEE = ±5 V
AV = +2
RL = 150Ω
1G
FREQUENCY (Hz)
FIGURE 5. FREQUENCY RESPONSE FOR VARIOUS POWER
SUPPLY VOLTAGES
5
INPUT
ns
FIGURE 6. RISE TIME (ns)
FN7389.5
August 10, 2005
EL5164, EL5165, EL5364
Typical Performance Curves
0
-10
(Continued)
0
VCC=+5V
VEE=-5V
AV=+1
-20
DISTORTION (dB)
-20
PSRR (dB)
VCC=+5 V
VEE=-5 V
AV=+1
VOUT=2VP-P
RL=100Ω
-10
-30
-40
VEE
-50
VCC
-60
-30
-40
THD
-50
-60
SECOND HARMONIC
-70
-70
THIRD HARMONIC
-80
-80
10K
100K
1M
10M
100M
-90
1G
0
10
20
30
40
FREQUENCY (MHz)
FREQUENCY (Hz)
0
DISTORTION (dB)
-30
OUTPUT IMPEDANCE (Ω)
VCC=+5 V
VEE=-5 V
AV=+2
VOUT=2VP-P,
RL=100Ω
-20
-40
-50
THD
-60
-70
-80
THIRD HARMONIC
-90
-100
VCC=+5 V
VEE=-5 V
AV=+2
10
1
0.1
0.01
SECOND HARMONIC
0
10
20
30
40
FREQUENCY (MHz)
50
10K
60
100K
1M
10M
100M
FREQENCY (Hz)
FIGURE 10. OUTPUT IMPEDANCE
FIGURE 9. DISTORTION vs FREQUENCY (AV = +2)
1M
VOLTAGE NOISE (nV/√Hz)
VCC, VEE=±5V
100K
VCC, VEE= ±6V
ROL (Ω)
60
FIGURE 8. DISTORTION vs FREQUENCY (AV = +1)
FIGURE 7. PSRR
-10
50
10K
±5V
±4V
1K
±3V
±2.5V
100
10
1
0
10
10K
100K
1M
10M
100M
FREQUENCY (Hz)
FIGURE 11. ROL FOR VARIOUS VCC, VEE
6
1G
100
1K
10K
100K
1M
FREQENCY (Hz)
FIGURE 12. VOLTAGE NOISE
FN7389.5
August 10, 2005
EL5164, EL5165, EL5364
Typical Performance Curves
(Continued)
VCC = +5V, VEE = -5V
AV = +2
RL = 150Ω
CURRENT NOISE (pA)
VCC=+5V
VEE=-5V
100
CH1
10
CH2
1
100
1K
10K
100K
FREQUENCY (Hz)
FIGURE 14. TURN ON DELAY
FIGURE 13. CURRENT NOISE
CH1
VCC = +5V
VEE = -5V
AV = +2
RL = 150Ω
CH2
PHASE
0.002
0.002
0.001
0.001
0.00
0
GAIN
-0.001
-0.001
-0.002
-0.002
-0.003
-0.003
VCC = +5V, VEE = -5V
AV = +2
TEST FREQUENCY, 3.58MHz
1V
-0.004
DIFFERENTIAL PHASE (°)
DIFFERENTIAL GAIN (%)
0.003
-0.005
0
-1V
DC INPUT
FIGURE 15. TURN OFF DELAY
FIGURE 16. DIFFERENTIAL GAIN/PHASE vs DC INPUT
VOLTAGE AT 3.58MHz
-30
-30
-50
-60
-70
VCC=+5V
VEE=-5V
RL=100Ω
RF=860Ω
RG=860Ω
CL=5pF
-40
-50
C
-80
CROSSTALK (dB)
NORMALIZED GAIN (dB)
-40
B
-90
A
-100
-60
-80
-90
-110
-120
1M
10M
100M
FREQUENCY (Hz)
FIGURE 17. FREQUENCY RESPONSE FOR VARIOUS
CHANNELS
7
1G
A TO C
A TO B
-100
-110
100K
C TO B
-70
-120
-130
10K
VCC=+5V
VEE=-5V
RL=100Ω
RF=422Ω
RG=422Ω
-130
10K
100K
1M
10M
100M
1G
FREQUENCY (Hz)
FIGURE 18. CHANNEL CROSSTALK BETWEEN CHANNELS
FN7389.5
August 10, 2005
EL5164, EL5165, EL5364
Typical Performance Curves
JEDEC JESD51-7 HIGH EFFECTIVE THERMAL
CONDUCTIVITY TEST BOARD
1.250W
1.2
1
0.8 909mW
0.6
SO8
θJA=110°C/W
435mW
0.4
SOT23-5/6
θJA=230°C/W
0.2
0
0
25
50
75 85 100
125
JEDEC JESD51-7 HIGH EFFECTIVE THERMAL
CONDUCTIVITY TEST BOARD
1.4
SO16 (0.150”)
θJA=80°C/W
POWER DISSIPATION (W)
POWER DISSIPATION (W)
1.4
(Continued)
1.2
1
0.6
0.4
0.2
0
150
0
25
AMBIENT TEMPERATURE (°C)
1.2
POWER DISSIPATION (W)
POWER DISSIPATION (W)
0.9
0.8
0.7
SO8
625mW
0.5
θJA=160°C/W
0.4
391mW
0.3
SOT23-5/6
θJA=256°C/W
0.2
0.1
0
25
50
75 85 100
125
150
AMBIENT TEMPERATURE (°C)
FIGURE 21. PACKAGE POWER DISSIPATION vs AMBIENT
TEMPERATURE
8
125
150
JEDEC JESD51-3 LOW EFFECTIVE THERMAL
CONDUCTIVITY TEST BOARD
1 909mW
SO
16
=1 (0.1
10 50
°C ” )
/W
QS
OP
θJ
16
A =1
58
°C
/W
θ
0.8
JA
0.6
633mW
0.4
0.2
0
0
75 85 100
FIGURE 20. PACKAGE POWER DISSIPATION vs AMBIENT
TEMPERATURE
JEDEC JESD51-3 LOW EFFECTIVE THERMAL
CONDUCTIVITY TEST BOARD
0.6
50
AMBIENT TEMPERATURE (°C)
FIGURE 19. PACKAGE POWER DISSIPATION vs AMBIENT
TEMPERATURE
1
QSOP16
θJA=112°C/W
0.8 893mW
0
25
50
75 85 100
125
150
AMBIENT TEMPERATURE (°C)
FIGURE 22. PACKAGE POWER DISSIPATION vs AMBIENT
TEMPERATURE
FN7389.5
August 10, 2005
EL5164, EL5165, EL5364
Pin Descriptions
EL5164
(8-PIN SO)
EL5164
(6-PIN
SOT-23)
EL5165
(5-PIN
SOT-23)
1, 5
2
4
4
PIN NAME
FUNCTION
NC
Not connected
IN-
Inverting input
EQUIVALENT CIRCUIT
VS+
IN+
IN-
VSCircuit 1
3
3
3
IN+
Non-inverting input
4
2
2
VS-
Negative supply
6
1
1
OUT
Output
(See circuit 1)
VS+
OUT
VSCircuit 2
7
6
8
5
5
VS+
Positive supply
CE
Chip enable, allowing the pin to float
or applying a low logic level will
enable the amplifier.
VS+
CE
VSCircuit 3
Applications Information
Product Description
The EL5164, EL5165, and EL5364 are current-feedback
operational amplifiers that offers a wide -3dB bandwidth of
600MHz and a low supply current of 5mA per amplifier. The
EL5164, EL5165, and EL5364 work with supply voltages
ranging from a single 5V to 10V and they are also capable of
swinging to within 1V of either supply on the output. Because
of their current-feedback topology, the EL5164, EL5165, and
EL5364 do not have the normal gain-bandwidth product
associated with voltage-feedback operational amplifiers.
Instead, its -3dB bandwidth to remain relatively constant as
closed-loop gain is increased. This combination of high
bandwidth and low power, together with aggressive pricing
make the EL5164, EL5165, and EL5364 ideal choices for
many low-power/high-bandwidth applications such as
portable, handheld, or battery-powered equipment.
For varying bandwidth needs, consider the EL5166 and
EL5167 with 1GHz on a 8.5mA supply current or the EL5162
and EL5163 with 300MHz on a 1.5mA supply current.
9
Versions include single, dual, and triple amp packages with
5-pin SOT-23, 16-pin QSOP, and 8-pin or 16-pin SO
outlines.
Power Supply Bypassing and Printed Circuit
Board Layout
As with any high frequency device, good printed circuit
board layout is necessary for optimum performance. Low
impedance ground plane construction is essential. Surface
mount components are recommended, but if leaded
components are used, lead lengths should be as short as
possible. The power supply pins must be well bypassed to
reduce the risk of oscillation. The combination of a 4.7µF
tantalum capacitor in parallel with a 0.01µF capacitor has
been shown to work well when placed at each supply pin.
For good AC performance, parasitic capacitance should be
kept to a minimum, especially at the inverting input. (See the
Capacitance at the Inverting Input section.) Even when
ground plane construction is used, it should be removed
from the area near the inverting input to minimize any stray
capacitance at that node. Carbon or Metal-Film resistors are
FN7389.5
August 10, 2005
EL5164, EL5165, EL5364
acceptable with the Metal-Film resistors giving slightly less
peaking and bandwidth because of additional series
inductance. Use of sockets, particularly for the SO package,
should be avoided if possible. Sockets add parasitic
inductance and capacitance which will result in additional
peaking and overshoot.
Disable/Power-Down
The EL5164 amplifier can be disabled placing its output in a
high impedance state. When disabled, the amplifier supply
current is reduced to < 150µA. The EL5164 is disabled when
its CE pin is pulled up to within 1V of the positive supply.
Similarly, the amplifier is enabled by floating or pulling its CE
pin to at least 3V below the positive supply. For ±5V supply,
this means that an EL5164 amplifier will be enabled when
CE is 2V or less, and disabled when CE is above 4V.
Although the logic levels are not standard TTL, this choice of
logic voltages allows the EL5164 to be enabled by tying CE
to ground, even in 5V single supply applications. The CE pin
can be driven from CMOS outputs.
Capacitance at the Inverting Input
Any manufacturer’s high-speed voltage- or current-feedback
amplifier can be affected by stray capacitance at the
inverting input. For inverting gains, this parasitic capacitance
has little effect because the inverting input is a virtual
ground, but for non-inverting gains, this capacitance (in
conjunction with the feedback and gain resistors) creates a
pole in the feedback path of the amplifier. This pole, if low
enough in frequency, has the same destabilizing effect as a
zero in the forward open-loop response. The use of largevalue feedback and gain resistors exacerbates the problem
by further lowering the pole frequency (increasing the
possibility of oscillation.)
The EL5164, EL5165, and EL5364 have been optimized
with a TBDΩ feedback resistor. With the high bandwidth of
these amplifiers, these resistor values might cause stability
problems when combined with parasitic capacitance, thus
ground plane is not recommended around the inverting input
pin of the amplifier.
Feedback Resistor Values
The EL5164, EL5165, and EL5364 have been designed and
specified at a gain of +2 with RF approximately 412Ω. This
value of feedback resistor gives 300MHz of -3dB bandwidth
at AV = 2 with 2dB of peaking. With AV = -2, an RF of 300Ω
gives 275MHz of bandwidth with 1dB of peaking. Since the
EL5164, EL5165, and EL5364 are current-feedback
amplifiers, it is also possible to change the value of RF to get
more bandwidth. As seen in the curve of Frequency
Response for Various RF and RG, bandwidth and peaking
can be easily modified by varying the value of the feedback
resistor.
Because the EL5164, EL5165, and EL5364 are currentfeedback amplifiers, their gain-bandwidth product is not a
constant for different closed-loop gains. This feature actually
10
allows the EL5164, EL5165, and EL5364 to maintain about
the same -3dB bandwidth. As gain is increased, bandwidth
decreases slightly while stability increases. Since the loop
stability is improving with higher closed-loop gains, it
becomes possible to reduce the value of RF below the
specified TBDΩ and still retain stability, resulting in only a
slight loss of bandwidth with increased closed-loop gain.
Supply Voltage Range and Single-Supply
Operation
The EL5164, EL5165, and EL5364 have been designed to
operate with supply voltages having a span of greater than
5V and less than 10V. In practical terms, this means that
they will operate on dual supplies ranging from ±2.5V to ±5V.
With single-supply, the EL5164, EL5165, and EL5364 will
operate from 5V to 10V.
As supply voltages continue to decrease, it becomes
necessary to provide input and output voltage ranges that
can get as close as possible to the supply voltages. The
EL5164, EL5165, and EL5364 have an input range which
extends to within 2V of either supply. So, for example, on
±5V supplies, the EL5164, EL5165, and EL5364 have an
input range which spans ±3V. The output range of the
EL5164, EL5165, and EL5364 is also quite large, extending
to within 1V of the supply rail. On a ±5V supply, the output is
therefore capable of swinging from -4V to +4V. Single-supply
output range is larger because of the increased negative
swing due to the external pull-down resistor to ground.
Video Performance
For good video performance, an amplifier is required to
maintain the same output impedance and the same
frequency response as DC levels are changed at the output.
This is especially difficult when driving a standard video load
of 150Ω, because of the change in output current with DC
level. Previously, good differential gain could only be
achieved by running high idle currents through the output
transistors (to reduce variations in output impedance.)
These currents were typically comparable to the entire
5.5mA supply current of each EL5164, EL5165, and EL5364
amplifiers. Special circuitry has been incorporated in the
EL5164, EL5165, and EL5364 to reduce the variation of
output impedance with current output. This results in dG and
dP specifications of TBD% and TBD°, while driving 150Ω at
a gain of 2.
Video performance has also been measured with a 500Ω
load at a gain of +1. Under these conditions, the EL5164,
EL5165, and EL5364 have dG and dP specifications of
0.01% and 0.01°, respectively.
Output Drive Capability
In spite of their low 5.5mA of supply current, the EL5164,
EL5165, and EL5364 are capable of providing a minimum of
±75mA of output current. With a minimum of ±75mA of
output drive, the EL5164, EL5165, and EL5364 are capable
of driving 50Ω loads to both rails, making it an excellent
FN7389.5
August 10, 2005
EL5164, EL5165, EL5364
where:
choice for driving isolation transformers in
telecommunications applications.
• VS = Supply voltage
Driving Cables and Capacitive Loads
When used as a cable driver, double termination is always
recommended for reflection-free performance. For those
applications, the back-termination series resistor will
decouple the EL5164, EL5165, and EL5364 from the cable
and allow extensive capacitive drive. However, other
applications may have high capacitive loads without a backtermination resistor. In these applications, a small series
resistor (usually between 5Ω and 50Ω) can be placed in
series with the output to eliminate most peaking. The gain
resistor (RG) can then be chosen to make up for any gain
loss which may be created by this additional resistor at the
output. In many cases it is also possible to simply increase
the value of the feedback resistor (RF) to reduce the
peaking.
• ISMAX = Maximum supply current of 1A
• VOUTMAX = Maximum output voltage (required)
• RL = Load resistance
Typical Application Circuits
0.1µF
+5V
IN+
VS+
IN-
OUT
VS-
0.1µF
-5V
375Ω
Current Limiting
5Ω
0.1µF
+5V
The EL5164, EL5165, and EL5364 have no internal currentlimiting circuitry. If the output is shorted, it is possible to
exceed the Absolute Maximum Rating for output current or
power dissipation, potentially resulting in the destruction of
the device.
IN+
IN-
With the high output drive capability of the EL5164, EL5165,
and EL5364, it is possible to exceed the 125°C Absolute
Maximum junction temperature under certain very high load
current conditions. Generally speaking when RL falls below
about 25Ω, it is important to calculate the maximum junction
temperature (TJMAX) for the application to determine if
power supply voltages, load conditions, or package type
need to be modified for the EL5164, EL5165, and EL5364 to
remain in the safe operating area. These parameters are
calculated as follows:
T JMAX = T MAX + ( θ JA × n × PD MAX )
where:
• TMAX = Maximum ambient temperature
375Ω
VS-
0.1µF
375Ω
375Ω
375Ω
0.1µF
+5V
IN+
IN375Ω
-5V
375Ω
+5V
IN+
IN-
• n = Number of amplifiers in the package
5Ω
FIGURE 23. INVERTING 200mA OUTPUT CURRENT
DISTRIBUTION AMPLIFIER
VIN
• θJA = Thermal resistance of the package
OUT
-5V
VIN
Power Dissipation
VS+
VOUT
-5V
VS+
VS-
OUT
0.1µF
0.1µF
VS+
VS-
OUT
VOUT
0.1µF
• PDMAX = Maximum power dissipation of each amplifier in
the package
PDMAX for each amplifier can be calculated as follows:
FIGURE 24. FAST-SETTLING PRECISION AMPLIFIER
V OUTMAX
PD MAX = ( 2 × V S × I SMAX ) + ( V S – V OUTMAX ) × ---------------------------R
L
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FN7389.5
August 10, 2005
EL5164, EL5165, EL5364
0.1µF
+5V
IN+
VS+
IN-
VS-
-5V
IN+
IN0.1µF
IN+
VS+
IN-
VS-
-5V
VIN
375Ω
VS-
-5V
162Ω
0.1µF
0.1µF
1kΩ
240Ω
0.1µF
+5V
OUT
OUT
375Ω
375Ω
VOUT+
0.1µF
+5V
VS+
OUT
375Ω
0.1µF
+5V
162Ω
0.1µF
VOUT-
IN+
1kΩ
VS+
IN-
0.1µF
VS-
-5V
375Ω
375Ω
TRANSMITTER
OUT
VOUT
0.1µF
375Ω
RECEIVER
FIGURE 25. DIFFERENTIAL LINE DRIVER/RECEIVER
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FN7389.5
August 10, 2005