300 W, 80 PLUS® Certified ATX Power Supply GreenPoint® Reference Design

TND313/D
Rev 3, Sep-11
High-Efficiency
305 W ATX Reference Design
Documentation Package
© 2011 ON Semiconductor.
1
Disclaimer: ON Semiconductor is providing this reference design
documentation package “AS IS” and the recipient assumes all risk
associated with the use and/or commercialization of this design package.
No licenses to ON Semiconductor’s or any third party’s Intellectual
Property is conveyed by the transfer of this documentation. This
reference design documentation package is provided only to assist the
customers in evaluation and feasibility assessment of the reference
design. The design intent is to demonstrate that efficiencies beyond
80% are achievable cost effectively utilizing ON Semiconductor
provided ICs and discrete components in conjunction with other
inexpensive components. It is expected that users may make further
refinements to meet specific performance goals.
2
Table of Contents
1.
2.
3.
4.
5.
6.
7.
8.
9.
10.
Overview ................................................................................. 6
Specifications .......................................................................... 7
Architecture Overview .......................................................... 8
Performance Results ............................................................ 13
Evaluation Guidelines .......................................................... 23
Schematics ............................................................................ 24
Parts List ............................................................................... 29
Critical Component Information........................................ 35
Resources/Contact Information .......................................... 35
Appendix ............................................................................... 36
3
List of Tables
Table 1: Target Specifications ........................................................................ 7
Table 2: Load matrix for efficiency measurements ...................................... 13
Table 3: Load matrix for cross regulation measurements ............................ 15
Table 4: Transient load conditions ............................................................... 18
4
List of Figures
Figure 1: Reference Design Architecture Block Diagram .................................................. 7
Figure 2: One switch forward topology and associated waveform..................................... 9
Figure 3: Active clamp forward topology and associated waveform ............................... 11
Figure 4: Efficiency vs percentage load from 20% to full load ........................................ 13
Figure 5: Power factor vs percentage load ........................................................................ 14
Figure 6: Efficiency vs percentage load from 5% to full load .......................................... 14
Figure 7: 5 V and 5 V SBY outputs cross regulation vs load conditions ......................... 16
Figure 8: 3.3 V output cross regulation vs load conditions .............................................. 16
Figure 9: 12 V1 and 12 V2 outputs cross regulation vs load conditions .......................... 17
Figure 10: -12 V output cross regulation vs load conditions ............................................ 17
Figure 11: 5 V output transient load response .................................................................. 18
Figure 12: 12 V1 output transient load response .............................................................. 18
Figure 13: 12 V2 output transient load response .............................................................. 19
Figure 14: 3.3 V output transient load response ............................................................... 19
Figure 15: 5 V output voltage ripple at full load .............................................................. 20
Figure 16: 3.3 V output voltage ripple at full load ........................................................... 20
Figure 17: 12 V1 output voltage ripple at full load .......................................................... 20
Figure 18: 12 V2 output voltage ripple at full load .......................................................... 21
Figure 19: -12 V output voltage ripple at full load ........................................................... 21
Figure 20: 5 V SBY output voltage ripple at full load ...................................................... 21
Figure 21: Holdup time at full load................................................................................... 22
Figure 22: Input inrush current ......................................................................................... 22
Figure 23: ATX solution boards in ATX enclosure.......................................................... 24
Figure 24: PFC controller PCB board schematic .............................................................. 25
Figure 25: EMC component board ................................................................................... 25
Figure 26: Active clamp controller PCB board schematic ............................................... 26
Figure 27: Supervisory and 3.3 V post regulator controller PCB board schematic .......... 27
Figure 28: Main PCB board schematic PFC and standby section .................................... 27
Figure 29: Main PCB board schematic active clamp stage section .................................. 28
Figure 30: Main PCB board schematic 3.3 V post regulator section................................ 28
5
1. Overview
ON Semiconductor was the first Semiconductor company to provide an 80 PLUS open
reference design for an ATX Power Supply in 2005. This 1st generation reference design,
was certified and met all the requirements of the 80 PLUS program. Following on this
successful 1st generation design, ON Semiconductor is introducing its improved 2nd
Generation reference design. This 2nd generation design utilizes newer ICs from ON
Semiconductor that enable this design to exceed 80% efficiency starting at 20% load
across different line conditions with ample margin to spare.
This reference document provides the details behind this 2nd generation design. The
design manual provides a detailed view of the performance achieved with this design in
terms of efficiency, performance, thermals and other key parameters. In addition, a
detailed list of the bill-of-materials (BOM) is also provided. ON Semiconductor will also
be able to provide technical support to help our customers design and manufacture a
similar ATX power supply customized to meet their specific requirements.
The results achieved in this 2nd generation design were possible due to the use of
advanced new components from ON Semiconductor. These new ICs not only speeded up
the overall development cycle for this new design, but also helped achieve the high
efficiencies while at the same time keeping a check on the overall cost. With the use of
these new ICs, ON Semiconductor has proven again that the emerging requirements for
high efficiency desktop power supplies can be met and further, can be optimized to meet
specific performance vs. cost goals.
This 2nd generation design consists of a single PCB designed to fit into the standard ATX
enclosure along with a fan. Figure 1 below presents the overall architecture employed in
this design – detailed schematics are included later in this design manual. As seen in
figure 1, this design employed an Active Clamp forward topology using the new, highly
integrated Active Clamp Controller IC from ON Semiconductor – NCP1562. A
Continuous Conduction Mode (CCM) Power Factor Correction (PFC) IC was employed
for the active PFC circuit. This IC, the NCP1653 provides an integrated, robust and costeffective PFC solution. The standby controller, NCP1027, is an optimized IC for the
ATX power supply and incorporates a high-voltage MOSFET. On the secondary side,
this architecture employs a post regulator approach for generating the 3.3 V output. This
is an alternative approach to the traditional magnetic amplifier (Mag Amp) approach.
Though ON Semiconductor believes that this post regulator approach provides the
highest efficiency amongst the different means of generating these outputs in the power
supply, it is important to note that if the customer desires to use a different approach, that
is possible – i.e. a similar design can be developed that utilizes all the other pieces of this
architecture without the post regulator and still achieve very good results.
6
With the introduction of this 2nd generation, high-efficiency ATX Power Supply, ON
Semiconductor has shown that with judicious choice of design tradeoffs, optimum
performance is achieved at minimum cost.
Figure 1: Reference Design Architecture Block Diagram
2. Specifications
The design closely follows the ATX12V version 2.2 power supply guidelines and
specifications available from www.formfactors.org, unless otherwise noted. For instance,
our reference design had a target of +/- 5% tolerance for both the 5 V and 5 Vstandby
outputs. Further, the efficiency targets for the 80 PLUS program and the EPA’s Energy
Star specification – Energy Star Program Requirements for Computers, version 4.0 that is
set to take effect from July 20, 2007 – were targeted. Key specifications are included in
Table 1 below.
Output
5V
5 V standby
12 V
- 12 V
Current
Min. (A)
0.3
0.0
1.0
0.0
Max (A)
22
2.5
18
1
Tolerance
(%)
± 3.3
± 3.3
± 5.0
± 10
Table 1: Target Specifications
7
Ripple/Noise
(mV)
50
50
120
120
Target specifications for other key parameters of the reference design include:
-
Efficiency: Minimum efficiency of 80% for 20%, 50% and 100% of rated output
load conditions as defined by the 80 PLUS requirements as well as the Energy
Star specification.
Power Factor: Power factor of 0.9 or greater at 100 % load.
Input Voltage: Universal Mains – 90 Vac to 265 Vac, 47 – 63 M Hz.
Output Power: Total maximum output power is 305 W.
Safety Features: As per the ATX12V specification, this design includes safety
features such as OVP, UVP, and OCP.
This design meets the IEC1000-3-2 requirements over the input line range and
under full load conditions.
This converter was designed for a 20 ms minimum Hold-up time.
Physical dimensions: This converter is designed to fit into the standard ATX
enclosure with dimensions of 150 mm x 140 mm x 86 mm.
3. Architecture Overview
Before discussing the power supply architecture of the Generation 2 design, it is worth
reiterating the design goals. We are tasked with providing a flexible power platform,
which is required to have the lowest cost and highest efficiency that can be packaged in a
small volume. The architecture must deliver a minimum of 80% efficiency over a wide
range of operating conditions (high-line and low-line) as well as rated output load
conditions (20% load and above). In addition we require a robust design solution having
low parts count to provide the same performance on a unit to unit basis in a high volume
manufacturing environment.
The architecture selected follows a traditional two stage conversion approach as
illustrated in Figure 1. It is worth noting that in order to achieve 80% efficiency overall,
the efficiency of each of the two conversion stages must exceed 90 %. The front-end is a
universal input, active power factor boost stage delivering a constant output voltage of
385 V to the active clamp stage. The second stage consists of two, dc-dc converters. The
first down-stream converter processes 290 W required by the system in the form of
tightly regulated +/-12 V, +5 V and +3.3 V outputs. The second converter delivers 15 W
of standby power to another isolated 5 V rail.
ON Semiconductor has developed multiple power management controllers and MOSFET
devices in support of the ATX program. Web based data sheets, design tools and
technical resources are available to assist design optimization. The ICs, supporting the
ATX Generation 2 platform, are the NCP1653 PFC controller, the NCP1562 active clamp
controller, the NCP4330 post regulator, the NCP1027 standby controller, and the
NTP48xx family of MOSFET synchronous rectifiers. It is not possible to discuss the
tradeoffs involved in each conversion stage at length, but the selection of the active
8
clamp forward converter topology is a key one and will be covered in depth. Each
controller is highly integrated and offers the lowest external parts count available.
PFC Stage
There are a variety of PFC topologies available. These include discontinuous conduction
mode (DCM), critical conduction mode (CRM) and continuous conduction mode (CCM).
At this power level, CCM is the preferred choice and the NCP1653 will implement a
IEC1000-3-2 compliant, fixed frequency, peak current mode PFC boost converter with
very few external components.
DC to DC (Main) Converter
The selection of the dc-dc down stream converter is at the heart of the 80% solution. The
traditional work horse of the ATX market has been the single switch forward converter
operating at a switching frequency of 100 kHz. The converter and its associated drain
waveform are illustrated in Figure 2. This topology is robust and delivers good full load
efficiency performance at minimal cost. However, as power levels increase and
regulatory requirements and energy conservation agencies drive for higher efficiency
under all load conditions, the single switch forward topology in its simplest form is
reaching its limit.
Figure 2: One switch forward topology and associated waveform
9
There are several technical reasons for this. First, because the main transformer is reset
via an auxiliary winding across the input bus, the duty cycle is limited below 50%.
Second, because of this reset mechanism there is always a dead time interval, during each
converter cycle, when no power is flowing. These two constraints have negative
implications on the silicon utilization of the primary switch requiring a costly, large area
die to be selected. The primary switch’s conduction loss is given by (1)
Ploss(conduction) = D * I P 2 * RDS (on)
(1)
where, D is the duty cycle, IP is the primary current and RDS(on) is the switch on
resistance. The topology is a hard switched topology with the primary switch being
driven on with 385 V across it each switching cycle. The capacitive switch loss are given
by (2),
Ploss(capacitive) =
1
COSS * VDS 2 * f
2
(2)
where, COSS is the switch output capacitance, VDS is the drain to source voltage and f is
the operating frequency. Capacitive losses dominate at light load. Hence a switch
selected for full load performance will suffer at light load because of its large drain
source capacitance. Reviewing these two loss equations, it becomes apparent for
efficiency enhancement under both full load and light load operation, a topology is
required that allows the primary switch to operate at lower current and voltage stress. As
the loss terms appear as current and voltage squared, small reductions in primary current
IP and switch voltage VDS significantly improve performance.
The active clamp forward converter illustrated in Figure 3 represents the ultimate
extension of the single switch converter and provides these benefits. Instead of using an
auxiliary winding, transformer reset is achieved using a clamp capacitor and an auxiliary
switch. The reset period, controlled by the auxiliary switch now extends to the interval
(1− D)*TS , completely eliminating the previous dead time interval. To maintain flux
balance in the main transformer core, the reset voltage across the clamp capacitor is
Vin * D
determined by the expression (1 − D) . The duty cycle D of the single switch forward
converter can extend beyond 50%, limited only by the primary switch’s maximum
voltage rating.
10
Figure 3: Active clamp forward topology and associated waveform
For a given set of conditions and power throughput, operating at extended duty cycles
allows for a lower primary current. This in turn allows the selection of a smaller, lower
cost die. Let’s look at a design example to illustrate this point.
To reduce cost, a 150 μF bulk capacitor (instead of a 470 μF conventional value) is
selected to provide 20 ms of hold up time. Using the energy storage equation given by
(3),
(
)
Power Delivered * Hold up time
1
2
2
Energy = C * Vi − V f =
η
2
(3)
where, Vi and Vf are the initial and final voltages of the input capacitor, respectively.
The initial voltage is 385 V and converter efficiency is 90%, allows us to calculate the
final voltage Vf to be 250 V. In the case of a conventional single switch design, the
maximum duty cycle we can practically select and avoid transformer saturation is 0.45.
The switch voltage stress is 2 x 250 V. With the active clamp single switch forward, the
duty cycle can be extended to 0.67 and the voltage stress on the switch is Vin / (1-D) or
3.03 x 250 V. Each converter has to process 290 / 0.9 or 322 W from the primary bulk
source. At nominal 385 V bulk, the average primary current is 0.84 A. Factoring in the
primary switch duty cycle D, the peak current IP in the traditional forward converter is
0.65 / 0.45 or 1.44 times larger than the active clamp approach. Based on the conduction
loss equation given by (1), we see that the 1.44 ratio holds true for conduction loss in the
primary switch. Put another way, we can choose a MOSFET with 44% higher RDS(on) in
the active clamp topology and have the same conduction loss. This is significant, as we
can achieve better silicon utilization, lower cost and lower drain capacitance. By
reviewing the data sheets from high voltage MOSFET vendors, it is possible to compare
output capacitance COSS versus RDS(on) as a function of die size. For example as
MOSFET resistance increases from 3.6 Ω to 4.8 Ω, the output capacitance reduces from
11
100 pF to 70 pF. The resonant nature of the active clamp allows the switch be turned on
at 300 V instead of the conventional 400 V. These two effects allow a reduction in
capacitive switching loss of 39% over a conventional design. Again, a significant
improvement remembering that light load efficiency is determined predominately by
switching loss. The example above illustrates how small changes in switch stress can
impact overall cost and performance.
The same argument relating to increased duty cycle operation extends to the secondary
by proportionally reducing output rectifier loss. Since the secondary loss is a dominant
factor at full load, an additional efficiency improvement/ cost benefit is realized. To
achieve the ultimate efficiency, synchronous rectification is required on the +12 V and +5
V outputs. The single switch active clamp forward is very suitable to drive synchronous
rectifiers directly from the secondary windings without the need for expensive gate
drivers or additional delay timing circuitry.
To allow designers to capitalize on the benefits inherent in the active clamp topology, the
NCP1562 has been developed to capture all the necessary control features within a 16 pin
package. The full featured controller has been designed for tight tolerance on all
parameters, including the maximum duty cycle limit and the important soft stop function.
To boost efficiency and maintain tight regulation, instead of the conventional magnetic
amplifier post regulated approach, the 3.3 V output is derived from the 5 Volt winding of
the main transformer. The MOSFET drivers, timing, synchronization and control
functions to support this output are provided by the NCP4330 controller. A 6 W
improvement in the loss budget is achieved when this approach is adopted. Gate charge
and RDS(on) have been optimized in the NTP48xx family of MOSFETs and provide
synchronous rectification for both the 3.3 V and 5 V outputs.
Standby Power
The NCP1027 integrates a fixed frequency current mode controller and a 700 volt
MOSFET. The NCP1027 is an ideal part to implement a flyback topology delivering 15
W to an isolated 5 V output. At light loads the IC will operate in skip cycle mode,
thereby reducing its switching losses and delivering high efficiency throughout the load
range.
12
4. Performance Results
The evaluation of the reference design focused on several areas including efficiency,
power factor, cross regulation and transient load response. Design optimizations may be
needed to customize this reference design to meet specific requirements.
The converter efficiency is measured according to the operating conditions detailed in
Table 2. The converter efficiency is measured at 100 Vac, 115 Vac and 230 Vac at 50
Hz. The converter achieves over 80% efficiency with room to spare over all load
conditions as shown in Figure 4. The output voltages used for the efficiency calculations
are measured at the end of the power cables. The fan is disabled for measurements at or
below 20% load. The fan is automatically enabled once the load exceeds 60 W or 20%.
The fan is operational for 50% and 100% load measurements. Further increases in the
efficiency can be obtained for 50% and 100% load conditions through fan speed control.
Load
Condition
5%
10 %
15 %
20 %
50 %
100 %
5V
0.690
1.390
2.080
2.780
6.950
13.900
3.3 V
0.540
1.070
1.610
2.150
5.370
10.740
Output Current (A)
12 V1
12 V2
0.385
0.385
0.770
0.770
1.150
1.150
1.510
1.510
3.845
3.845
7.695
7.695
-12V
0.030
0.070
0.100
0.140
0.350
0.700
5 V SBY
0.070
1.390
0.210
0.280
0.700
1.400
Table 2: Load matrix for efficiency measurements
Efficiency (%)
90
80
70
100 V
115 V
230 V
60
20
30
40
50
60
70
80
90
100
% Load
Figure 4: Efficiency vs percentage load from 20% to full load
13
The power factor exceeds 0.9 over all operating conditions as shown in Figure 5.
1.00
0.98
0.96
Power Factor
0.94
0.92
0.90
0.88
0.86
0.84
100 V
115 V
230 V
0.82
0.80
20
30
40
50
60
70
80
90
100
% Load
Figure 5: Power factor vs percentage load
In Figure 6, the efficiency measurements are shown from 5% load to full-load. Note that
neither the 80 PLUS program nor the Energy Star specification require efficiencies above
80% for any output load below 20%. However, as can be seen in Figure 6, this reference
design achieved 80% efficiency down to 16 % load.
Efficiency (%)
90
80
70
100 V
115 V
230 V
60
5
10
15
20
% Load
Figure 6: Efficiency vs percentage load from 5% to full load
14
Output voltage cross regulation is measured according to the load conditions listed in
Table 3. The results of the cross regulation measurements are shown in
Figure 7 through Figure 10. Included in these figures are the tolerance requirements
based on the target specifications listed in Table 1. The margin for the 5 V and 5 V SBY
outputs can be increased by shifting up the regulation target for the 5 V outputs. It can
also be improved by changing the weight of the 12 V and 5 V outputs in the regulation
circuit.
Load
Condition
1
2
3
4
5
6
7
8
9
10
11
12
13
14
15
16
17
18
19
5V
(+/-3.3%)
0.3
7
0.3
0.3
7
4
18
18
4
18
4
14
18
4
18
4
22
4
22
3.3 V
(+/-4%)
0.3
3
0.3
3
0.3
0.3
12
12
12
0.3
0.2
17
17
17
0.3
2
17
17
2
Output Current (A)
12 V1
12 V2
(+/-5%)
(+/-5%)
0
0
2
2
0
0
2
2
2
2
1
1
5
5
1
1
5
5
5
5
1
1
8
6
1
1
8
6
8
6
5
5
5
5
5
5
5
5
-12 V
(+/-10%)
0
0.1
0
0.1
0.1
0.2
1
0.2
1
1
0.2
1
0.2
1
1
0.2
1
1
1
Table 3: Load matrix for cross regulation measurements
15
5 V SBY
(+/-3.3%)
0
0.5
0.5
0.5
0.5
0.2
2.5
2.5
2.5
2.5
0.2
2.5
2.5
2.5
2.5
1
2.5
2.5
2.5
5.20
5.15
Output Voltage (V)
5.10
5.05
5.00
5V
Min
Max
5 V SBY
4.95
4.90
4.85
4.80
0
5
10
Load Condition #
15
20
Figure 7: 5 V and 5 V SBY outputs cross regulation vs load conditions
3.45
Output Voltage (V)
3.40
3.35
3.30
3.25
3.3 V
Min
3.20
Max
3.15
0
5
10
Load Condition #
15
Figure 8: 3.3 V output cross regulation vs load conditions
16
20
12.8
12.6
12 V1
Min
Max
12 V2
Output Voltage (V)
12.4
12.2
12.0
11.8
11.6
11.4
11.2
0
5
10
Load Condition #
15
20
Figure 9: 12 V1 and 12 V2 outputs cross regulation vs load conditions
-10.0
Output Voltage (V)
-10.5
-11.0
-11.5
-12.0
-12 V
Min
Max
-12.5
-13.0
-13.5
0
5
10
15
20
Load Condition #
Figure 10: -12 V output cross regulation vs load conditions
17
The 5 V, 12 V and 3.3 V outputs are evaluated independently under transient load
conditions. Each output is loaded at 50% and the load is reduced to 25% or increased to
75% of the maximum rated current. The transient voltage tolerance of each of the 5 V,
12 V and 3.3 V outputs is +/- 5%. Table 4 summarizes the transient load conditions and
limits for each output. Transient waveforms are shown in Figure 11 through Figure 14.
Output
5V
3.3 V
12 V1
12 V2
Minimum Load (A)
5.5
4.25
4.5
4.5
Nominal Load (A)
11
8.5
9
9
Maximum Load (A)
16.5
12.75
13.5
13.5
Voltage under/overshoot (V)
±250mV, ≤0.5V pk-pk
±170mV, ≤0.34V pk-pk
±600mV, ≤1.2V pk-pk
±600mV, ≤1.2V pk-pk
Table 4: Transient load conditions
ΔILOAD = 11.5 A to 5.5 A
ΔILOAD = 11.5 A to 16.5 A
Figure 11: 5 V output transient load response
ΔILOAD = 9 A to 4.5 A
ΔILOAD = 9 A to 13.5 A
Figure 12: 12 V1 output transient load response
18
ΔILOAD = 9 A to 4.5 A
ΔILOAD = 9 A to 13.5 A
Figure 13: 12 V2 output transient load response
ΔILOAD = 8.5 A to 4.25 A
ΔILOAD = 8.5 A to 12.75 A
Figure 14: 3.3 V output transient load response
All the outputs meet the transient voltage requirements under the evaluated conditions.
The ripple voltage of each output is measured at the maximum load for each output. The
output ripple is measured across 10 μF/MLC parallel 1000 μF low ESR/ESL termination
capacitors. The target ripple is +/- 120 mV for the 12 V outputs and 50 mV for all other
outputs. Figure 15 through Figure 20 show the output voltage ripple measurements. All
outputs meet the voltage ripple requirements.
19
Figure 15: 5 V output voltage ripple at full load
Figure 16: 3.3 V output voltage ripple at full load
Figure 17: 12 V1 output voltage ripple at full load
20
Figure 18: 12 V2 output voltage ripple at full load
Figure 19: -12 V output voltage ripple at full load
Figure 20: 5 V SBY output voltage ripple at full load
21
The required holdup time at full load is 20 ms. Holdup time is measured from the
moment the AC power is removed to when the PWR_OK signal goes low. Figure 21
shows the holdup time at full load. Channel 1 is the AC power and Channel 2 is the
PWR_OK signal. Holdup time is measured at 22.5 ms.
Figure 21: Holdup time at full load
The input inrush current of the system at 230 Vac at full load is measured at 28.8 A as
shown in Figure 22.
Figure 22: Input inrush current
22
5. Evaluation Guidelines
Evaluation of the reference design should be attempted only by persons who are
intimately familiar with power conversion circuitry. Lethal mains referenced voltages
and high dc voltages are present within the primary section of the ATX circuitry. All
testing should be done using a mains high-isolation transformer to power the
demonstration unit so that appropriate test equipment probing will not affect or
potentially damage the test equipment or the ATX circuitry. The evaluation engineer
should also avoid connecting the ground terminal of oscilloscope probes or other test
probes to floating or switching nodes (e.g. the source of the active clamp MOSFET). It is
not recommended to touch heat sinks, on which primary active components are mounted,
to avoid the possibility of receiving RF burns or shocks. High impedance, low
capacitance test probes should be used where appropriate for minimal interaction with the
circuits under investigation. Particular care should be taken when probing the high
impedance input pins of the NCP1653 power factor controller and the NCP1562 active
clamp controller. As with all sensitive switchmode circuitry, the power supply under test
should be switched off from the ac mains whenever the test probes are connected and/or
disconnected.
The 3.3 V output does not have a minimum load requirement and a preload resistor is
included in the -12 V output.
The NCP1027 standby flyback converter will be operational as long as there is ac mains
voltage applied to the system. This auxiliary converter can be evaluated by merely
applying the mains voltage to the board. The supervisory IC enable input and monitoring
circuitry will have to be disabled. The supervisory circuitry will normally cause a
shutdown of the PFC (and the main converter) if the 3.3 V, the 5 V and the 12 V outputs
are not sensed at their nominal voltage.
The evaluating engineer should also be aware of the idiosyncrasies of constant current
type electronic loads when powering up the ATX demonstration unit. If the loads are
adjusted to be close to the ATX’s maximum rated output power, the unit could shut down
at turn on due to the instantaneous overloading effect of the constant current loads. As a
consequence, electronic loads should be set to constant resistance mode or rheostats
should be used for loads. The other alternative is to start the supply at light to medium
load and then increase the constant current electronic loads to the desired level.
The board is designed to fit in a traditional ATX enclosure as shown in Figure 23.
23
Figure 23: ATX solution boards in ATX enclosure
6. Schematics
The power supply is implemented using a single sided PCB board. Added flexibility is
provided by using daughter cards for the PFC (NCP1653), active clamp (NCP1562)
controllers. A PCB board is also used for the 3.3 V post regulator (NCP4330) and
supervisory controllers. This allows the use of newer generation controllers without the
need of a complete re-layout of the main board. An additional daughter card is used for
EMC components. The individual PCB board schematics are shown in Figure 24 through
Figure 27.
The schematic of the main PCB board is divided in three sections: PFC & standby
section, active clamp section, and the post regulator section as shown in Figure 28
through Figure 30, respectively.
24
Figure 24: PFC controller PCB board schematic
Figure 25: EMC component board
25
Figure 26: Active clamp controller PCB board schematic
26
Figure 27: Supervisory and 3.3 V post regulator controller PCB board schematic
Figure 28: Main PCB board schematic PFC and standby section
27
Figure 29: Main PCB board schematic active clamp stage section
Figure 30: Main PCB board schematic 3.3 V post regulator section
28
7. Parts List
The bill of materials (BOM) for the design is provided in this section. To reflect the
schematics shown in the previous section, the BOM have also been broken into different
sections and provided in separate tables – Table 5 through Table 9.
It should be noted that a number of components used during the development cycle were
based on availability. As a result, further cost reductions and better inventory
management can be achieved by component standardization. IE, the unique part numbers
can be SIGNIFICANTLY reduced by standardization and re-use of component values
and case sizes. This will result in a lower cost BOM and better inventory management.
Description
Part Numbers
0.1µF, ±10%, 500V, X7R, Case Size 1812
0.1µF, ±10%, 50V, X7R, Case Size1206
0.1µF, ±20%,300VAC, Interference Suppression CapX2
0.22uF, ±20% ,300VAC, Interference Suppression CapX2
270µF, ±20%, 400V, -40°C to +85°C, B43501 series , Snap-In, Pitch 10mm
100pF, ±10%, 1kVDC,High voltage ceramic disc Capacitor, -25°C to +85°C
100pF, ±5%, 50V, COG, Case Size1206
1nF, ±20% , 100V , Stacked-film capacitor, MMK series , 5mm Pitch
1nF, ±10%, 1kVDC,High voltage ceramic disc Capacitor,-25°C to +85°C
1nF, ±20%,, 440VAC,Interference Suppression CapY1
1nF,±20%, ,440/250VAC,Interference Suppression CapX1/Y2
1nF, ±10%, 100V, COG, Case Size1206
4.7nF, ±10%, 1kVDC, High voltage ceramic disc Capacitor, -25°C to +85°C
4.7nF,±10% ,440/250VAC,Interference Suppression CapX1/Y2
10nF, ±20% , 100V , Stacked-film capacitor, MMK series , 5mm Pitch
10nF, ±10%, 50V, X7R, Case Size1206
22nF, ±20% , 100V , Stacked-film capacitor, MMK series , 5mm Pitch
2n2F, ±5%, 50V, COG, Case Size1206
470pF, ±5%, 50V, COG, Case Size1206
10µF, ±20%, 16V,-40°C to +85°C, Type VR, Radial, Pitch 2mm, Pb Free
220µF, ±20%, 25V,-40°C to +85°C, Type VR, Radial, Pitch 3.5mm, Pb Free
3300µF, ±20%, 10V,-40°C to +85°C, Type VR, Radial, Pitch 5mm, Pb Free
47µF, ±20%, 25V,-40°C to +85°C, Type VR, Radial, Pitch 2mm, Pb Free
2200µF, ±20%, 10V,-40°C to +85°C, Type PM, Radial, Pitch 5mm, Pb Free
220µF, ±20%, 25V,-40°C to +85°C, Type PW, Radial, Pitch 3.5mm, Pb Free
470E, ±1%, 0.25W, Case Size 1206
0.2E, ±1%,1W, Case Size 2010
0E022, ±5%, 3W,Wire Wound Resister
100E, ±1%, 0.25W, Case Size 1206
100E, ±1%, 0.25W, MFR
10E0, ±1%, 0.25W, Case Size 1206
10E, ±1%, 0.5W, Case Size 2010
VJ1812Y104KXEAT
B37872K5104K060
PHE840EB6100MB05R17
PHE840EX6220MB06R17
B43501A9277M000
DEBB33A101KC1B
B37871K5101J060
MMK5 102M100J01L4 BULK
DEBB33A102KA2B
PME294RB4100MR30
2252 812 35 027
B37871K1102J560
DEBB33A472KA3B
2252 812 35 427
MMK5 103M100J01L4 BULK
B37872K5103K060
MMK5 223M100J01L4 BULK
B37871K5222J060
B37871K5471J060
UVR1C100MDD
UVR1E221MPD
UVR1A332MHD
UVR1E470MDD
UPM1A222MHD
UPW1E221MPD
MCR18 EZH F-4700
CRL1206-FW-0R20E_
BSI680E022±5%±100ppm/°C
MCR18 EZH F-1000
EROS2CHF1000
MCR18 EZH F-10R0
MCR50-JZH-J 10R0
29
Qty
3
18
2
1
1
2
1
2
2
2
1
5
1
1
1
1
1
1
1
4
1
1
1
2
2
1
3
1
1
2
2
5
10E,±1%, 0.25W, MFR
10E,±1%, 0.6W, MFR
10K, ±1%, 0.25W,Case Size 1206
120E, ±1%, 0.25W, Case Size 1206
15E, ±1%, 0.25W, Case Size 1206
1E0, ±5%, 0.5W, Case Size 2010
1K0, ±1%, 0.25W,Case Size 1206
1K0, ±1%, 0.25W, MFR
1M5, ±5%, 0.25W,Case Size 1206
1M5, ±5%, 0.25W,Case Size 1206
1M, ±1%, 0.25W, MFR
27K, ±1%, 0.25W,Case Size 1206
47E, ±1%, 0.25W, Case Size 1206
47E, ±1%, 0.25W, Case Size 1206
47E, ±1%, 0.5W, Case Size 2010
47E,±1%, 0.25W, MFR
4K7, ±1%, 0.25W,Case Size 1206
4K75,±1%, 0.25W, MFR
56E, ±1%, 0.25W, Case Size 1206
680K, ±1%, 0.25W,Case Size 1206
750E, ±1%, 0.25W, Case Size 1206
82K, ±1%, 0.25W,Case Size 1206
8K2, ±1%, 0.25W,Case Size 1206
2K7, ±1%, 0.25W,Case Size 1206
300E, ±1%, 0.25W, Case Size 1206
0.005E, WIRE
If(av) = 1A, V(rrm) = 1000V, Standard Rectifier.DO-41 Package
If(av) =200mA, V(rrm) =75V, Small Signal Diode,Axial Lead,DO-35 Pkg
If(av) =3A, V(rrm) =1000V, Standard recovery Diode,DO-201AD Pkg
If = 200mA, Vrrm = 70V, Dual Switching Diode,SOT-23 Package
If = 200mA, Vrrm = 70V, Dual Switching Diode,SOT-23 Package
If = 1A, Vrrm = 40V, Schottky Diode, SMA Package
If = 5A,Vrrm = 40V, SMC Package, Schottky Diode
If(av) =15A,V(rrm) =600V,Soft recovery diode ,TO-220AC Package
If(av) = 1A,V(rrm) = 600V,Ultra Fast Rectifier, DO-41 Package
If = 1A, Vrrm = 600V, Ultrafast Rectifier, SMA Package
Vceo=80V, Ic=3A, PNP Comp plastic Silicon Power Tr, TO-225AA
Vdss=800V,Id=2A, Rds-on=2.7E,N-Channel Mosfet,TO-220AB Pkg
Vdss=800V,Id=11A, Rds-on=0.45E, N-Channel Mosfet, TO-220 Pkg
Vdss=600V,Id=20A, Rds-on=0.25E,N-Channel Mosfet,TO-220 Pkg
Vdss=30 V, Rds-on=6 mE, N-Channel Mosfet,TO-220AB Pkg
Vdss=24V,Id=65A, Rds-on=0.0125E, N-Channel Mosfet, TO-220 Pkg
Vceo=60V, Ic=600mA, PNP Switching Transister, SOT-23 Pkg
Vceo=40V, Ic=600mA, NPN Switching Transistor, TO-92 Pkg
1uH, POST FILTER
Powdered Torroidal core AL= 105,Weight 14.48gms-Post Reg
Powdered Iron Core, AL=46-Input EMI Filter
CUSTOMER SAMPLE - PFC Inductor
30
EROS2CHF10R0
2322 186 3 1009
MCR18 EZH F-1002
MCR18 EZH F-1200
MCR18 EZH F-15R0
MCR50-JZH-J 1R0
MCR18 EZH F-1001
EROS2CHF1001
MCR18 EZP J-155
MCR18 EZH J-155
EROS2CHF1004
MCR18 EZH F-2702
MCR18 EZP F-47R0
MCR18 EZH F-47R0
MCR50-JZH-F 47R0
EROS2CHF47R0
MCR18 EZH F-4701
EROS2CHF4751
MCR18 EZH F-56R0
MCR18 EZH F-6803
MCR18 EZH F-7500
MCR18 EZH F-8202
MCR18 EZH F-8201
MCR18 EZH F-2701
MCR18 EZH F-3000
CUSTOMER SAMPLE
1N4007
1N4148
1N5408
BAV70LT1
BAV70
MBRA140T3
MBRS540T3
MSR1560
MUR160
MURA160T3
MJE172G
SPP02N80C3
SPP11N80C3
STP20NM60
_
NTP65N02R
MMBT2907A
2N4401
1uH_POSTFILTER
CS 234 125 E
T80-26
CUSTOMER SAMPLE
1
3
3
1
2
1
4
1
2
3
2
2
1
5
1
4
5
1
1
2
3
1
4
1
1
2
1
1
1
2
6
1
1
1
5
1
1
1
1
1
2
4
2
1
4
1
1
1
Powdered Torroidal core AL= 117,Weight 47gms-Ouput Coupled Inductor
E25,10Pin, Vertical coil former,E25/13/7 Yoke - Standby TX
ETD39, 16 PIN VERTICAL BOBBIN, N87 CORE - Main TX
Ferrite Torroidal Core,R-12.5, AL= 2200 ± 25%, N30-Gate Drive TX
Vbr=200V,Zener Transient Voltage Supressor, CASE 17-2.
100 deg celcius PTC Temperature senser
2E5, 8.4A, ±20%, NTC Inrush Current Limiter
EURO CONNECTOR ,DIN416 12 H15
2pin powermate
3 PIN MOLEX Connector
3 PIN MOLEX Connector
Vac=320V, Diameter14, Metal Oxide Varistor
EMI Suppression Bead 3.5mm Diameter, 3.25mm Length
8A,1000V, Bridge Rectifier, Peak Surge Curent=200A, GBU Pkg
Adjustable Precision Zener Shunt Reg,TO-92 Pkg, +/-2%
4 Pin Type Optocoupler,CTR 60% to 160%,DIP4 Pkg
High-Voltage Switcher, PDIP-8 Package, 0°C to 125°C, Pb-Free
4 Pin Type Optocoupler,CTR 60% to 160%,DIP4 Pkg,-30°C to 100°C
1A , -12V 3-Terminal Fixed Voltage regulator, TO-220 Package
Table 5: Main Section
31
CH 358 125 E
B66208J1110T001/A20100000
B64290L0044X830
P6KE200CA
B59901D0100A040
B57238S0259M000
AS PER APPROVED
SOURCES
CK
22-04-1.31
22-04-1.31
B72214S0321K101
2673000101
GBU8M
LM431ACZ
PC817A
NCP1027P065G
PC817A
LM7912CT
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
Description
47µF, ±20%, 25V,-40°C to +85°C, Type VR, Radial, Pitch 2mm, Pb Free
0.1µF, ±10%, 500V, X7R, Case Size 1812
0.1µF, ±10%, 50V, X7R, Case Size1206
0.1µF, ±10%, 50V, X7R, Case Size1206
0.47µF, ±10%, 50V, X7R, Case Size1206
10nF, ±10%, 50V, X7R, Case Size1206
1n2F, ±10%, 50V, X7R, Case Size1206
1nF, ±10%, 50V, X7R, Case Size1206
2n2F, ±10%, 50V, X7R, Case Size1206
470pF, ±5%, 50V, COG, Case Size1206
47nF, ±10%, 50V, X7R, Case Size1206
4n7F, ±10%, 50V, X7R, Case Size1206
10E0, ±1%, 0.25W, Case Size 1206
10K, ±1%, 0.25W,Case Size 1206
12K, ±1%, 0.25W,Case Size 1206
1K0, ±1%, 0.25W,Case Size 1206
220E, ±1%, 0.25W, Case Size 1206
220K, ±1%, 0.25W,Case Size 1206
221K,±1%, 0.25W, MFR
22K, ±1%, 0.25W,Case Size 1206
270K, ±1%, 0.25W,Case Size 1206
330K, ±1%, 0.25W,Case Size 1206
34K, ±1%, 0.25W,Case Size 1206
390K, ±1%, 0.25W,Case Size 1206
39K, ±1%, 0.25W,Case Size 1206
430K, ±1%, 0.25W,Case Size 1206
453K, ±1%, 0.25W,Case Size 1206
470E, ±1%, 0.25W, Case Size 1206
470K, ±1%, 0.25W,Case Size 1206
47E,±1%, 0.6W, MFR
47K, ±1%, 0.25W,Case Size 1206
560K, ±1%, 0.25W,Case Size 1206
5K6, ±1%, 0.25W,Case Size 1206
680E, ±1%, 0.25W, Case Size 1206
680E,±1%, 0.6W, MFR
68K, ±1%, 0.25W,Case Size 1206
82K, ±1%, 0.25W,Case Size 1206
If = 200mA, Vrrm = 70V, Dual Switching Diode,SOT-23 Package
Dual Operational Amplifier,SO-8 Package, 0°C to 70°C
Adjustable Precision Zener Shunt Reg,TO-92 Pkg, -0°C to 70°C, +/-2%
If = 1A, Vrrm = 40V, Schottky Diode, SMA Package
Vceo=40V, Ic=200mA, NPN General Purpose Transistor, SOT-23 Pkg
Active Clamp Mode PWM Controller , SO-16Package
4 Pin Type Optocoupler,CTR 60% to 160%,DIP4 Package,-30°C to 100°C
Table 6: Active Clamp Section
32
Part Numbers
UVR1E470MDD
VJ1812Y104KXEAT
B37872K5104K060
B37872K5104K060
B37872K5474K062
B37872K5103K060
VJ1206Y122KXAAT
B37872K5102K060
B37872K5222K060
B37871K5471J060
B37872K5473K060
B37872K5472K060
MCR18 EZH F-10R0
MCR18 EZH F-1002
MCR18 EZH F-1202
MCR18 EZH F-1001
MCR18 EZH F-2200
MCR18 EZP F-2203
EROS2CHF2213
MCR18 EZH F-2202
MCR18 EZH F-2703
MCR18 EZP F-3303
MCR18 EZH F-3402
MCR18 EZH F-3903
MCR18 EZP F-3902
MCR18 EZH F-4303
MCR18 EZH F-4533
MCR18 EZH F-4700
MCR18 EZH F-4703
2322 186 3 4709
MCR18 EZH F-4702
MCR18 EZH F-5603
MCR18 EZH F-5601
MCR18 EZH F-6800
2322 186 3 6801
MCR18 EZH F-6802
MCR18 EZP F-8202
BAV70LT1
LM358M
LM431ACZ
MBRA140T3
MMBT3904LT1
NCP1562A
PC817A
Qty
1
1
2
4
1
1
1
1
1
1
1
2
1
4
2
2
1
1
1
1
1
1
1
1
1
2
1
1
2
1
1
1
1
1
1
1
1
1
1
1
2
1
1
1
Description
47µF, ±20%, 25V,-40°C to +85°C, Type VR, Radial, Pitch 2mm, Pb
Free
1nF, ±10%, 50V, X7R, Case Size1206
0.1µF, ±10%, 50V, X7R, Case Size1206
1K0, ±1%, 0.25W,Case Size 1206
51K, ±1%, 0.25W,Case Size 1206
560K, ±1%, 0.25W,Case Size 1206
680K, ±1%, 0.25W,Case Size 1206
18V,1W,Zenerdiode ,DO-41 package
If = 1A, Vrrm = 40V, Schottky Diode, SMA Package
Fixed-Frequency Current-Mode Power Factor Correction Controller
Part Numbers
UVR1E470MDD
B37872K5102K060
B37872K5104K060
MCR18 EZH F-1001
MCR18 EZH F-5102
MCR18 EZH F-5603
MCR18 EZH F-6803
1N4746A
MBRA140T3
NCP1653
Qty
1
3
2
1
1
1
1
1
2
1
Table 7: PFC Section
Description
0.1µF, ±20%,300VAC, Interference Suppression CapX2,
0.22uF, ±20% ,300VAC, Interference Suppression CapX2 , -55°C to
+105°C
3 PIN MOLEX Connector
4.7nF,±10% ,440/250VAC,Interference Suppression CapX1/Y2
470K, ±1%, 0.25W,Case Size 1206
11.4 X 9.4 X 24.4mm,Semi Enclosed Fuse Holder
Ferrite Torroidal Core,R-25, AL= 4620 ± 25%, EMI Choke
Table 8: EMC Section
33
Part Numbers
PHE840EB6100MB05R17
PHE840EX6220MB06R17
22-04-1.31
2252 812 35 427
MCR18 EZH F-4703
Cat No: 4628
B64290L0618X830
Qty
1
1
2
1
2
1
1
Description
Part Numbers
0.1µF, ±10%, 50V, X7R, Case Size1206
0.1µF, ±10%, 50V, X7R, Case Size1206
0.47µF, ±10%, 50V, X7R, Case Size1206
10nF, ±10%, 50V, X7R, Case Size1206
4n7F, ±10%, 50V, X7R, Case Size1206
47µF, ±20%, 25V,-40°C to +85°C, Type VR, Radial, Pitch 2mm, Pb Free
10µF, ±20%, 50V,-40°C to +85°C, Type PW, Radial, Pitch 1.5mm, Pb
Free
0.1uF, ±10%,50V,X7R Multilayered Ceramic Capacitor, -55°C to +125°C
100E, ±1%, 0.25W, Case Size 1206
100K, ±1%, 0.25W,Case Size 1206
10K, ±1%, 0.25W,Case Size 1206
10K, ±1%, 0.25W,Case Size 1206
180E, ±1%, 0.25W, Case Size 1206
1K0, ±1%, 0.25W,Case Size 1206
1K5, ±1%, 0.25W,Case Size 1206
1K0, ±1%, 0.25W, MFR
200E, ±1%, 0.25W, Case Size 1206
200E, ±1%, 0.25W, Case Size 1206
22K, ±1%, 0.25W,Case Size 1206
2K2, ±1%, 0.25W,Case Size 1206
2K7, ±1%, 0.25W,Case Size 1206
3K0, ±1%, 0.25W,Case Size 1206
3K3, ±1%, 0.25W,Case Size 1206
3K6, ±1%, 0.25W,Case Size 1206
430E, ±1%, 0.25W, Case Size 1206
470E, ±1%, 0.25W, Case Size 1206
47K, ±1%, 0.25W,Case Size 1206
4K7, ±1%, 0.25W,Case Size 1206
5K62,±1%, 0.25W, MFR
620E, ±1%, 0.25W, Case Size 1206
62K, ±1%, 0.25W,Case Size 1206
75K, ±1%, 0.25W,Case Size 1206
820E, ±1%, 0.25W, Case Size 1206
5.1V,225mW,Zenerdiode ,SOT-23 package
8.2V,0.225W,Zenerdiode, SOT-23 package
If = 200mA, Vrrm = 70V, Dual Switching Diode,SOT-23 Package
Vceo=40V, Ic=200mA, NPN General Purpose Transistor, SOT-23 Pkg
4 Channel Secondary Monitoring IC, DIP-16 Package, -30°C to 90°C
Adjustable Precision Zener Shunt Reg,TO-92 Pkg, -0°C to 70°C, +/-2%
Post Regulation Driver
B37872K5104K060
B37872K5104K060
B37872K5474K062
B37872K5103K060
B37872K5472K060
UVR1E470MDD
UPW1H100MPD6
C322C104K5R5CA
MCR18 EZH F-1000
MCR18 EZH F-1003
MCR18 EZP F-1002
MCR18 EZH F-1002
MCR18 EZP F-1800
MCR18 EZH F-1001
MCR18 EZH F-1501
EROS2CHF1001
MCR18 EZH F-2000
MCR18 EZP F-2000
MCR18 EZP F-2202
MCR18 EZH F-2201
MCR18 EZH F-2701
MCR18 EZH F-3001
MCR18 EZH F-3301
MCR18 EZH F-3601
MCR18 EZH F-4300
MCR18 EZH F-4700
MCR18 EZH F-4702
MCR18 EZH F-4701
EROS2CHF5621
MCR18 EZH F-6200
MCR18 EZH F-6202
MCR18 EZH F-7502
MCR18 EZP F-8200
BZX84C5V1LT1
BZX84C8V2LT1
BAV70LT1
MMBT3904LT1
PS224
LM431ACZ
NCP4330
Table 9: Post Regulation Section
34
Qty
8
3
1
3
1
3
1
2
1
1
1
3
1
2
1
1
2
1
1
1
1
1
2
1
1
1
1
1
1
1
1
1
2
1
1
6
2
1
1
1
8. Critical Component Information
It is shown that an active clamp forward converter provides a higher efficiency compared
to a traditional forward converter. However, special attention has to be provided to
several blocks of the circuit to ease design. The areas are described below:
1. Power transformer: Contrary to traditional forward converters, a low
magnetizing inductance is required to achieve zero- or near-zero volt
switching. This is easily achieved by gapping the transformer. In this design,
a 6.7 mH primary inductance is used. The transformer datasheet is included
in the Appendix.
2. Active clamp capacitor: The active clamp capacitor stores voltage to reset the
transformer during the power switch off time. This capacitor sees the
magnetizing current. Therefore, the ESR of this capacitor should be
considered when selecting this capacitor. A high quality low ESR capacitor
should be used to prevent overheating. Ceramic or propylene are good
options.
3. Coupled inductor: A coupled inductor is used to regulate the 5 V, 12 V and 12 V outputs. Good cross regulation is achieved by using the same number of
turns on the inductor as in the transformer winding.
4. High side transformer for active clamp switch: High primary inductance is
required to reduce magnetizing current on the high side transformer and
provide adequate voltage to drive the active clamp switch. The control signal
for the active clamp switch is 1-D. Therefore, the high side transformer is
designed to operate at large duty cycles or volt-seconds without saturating.
The transformer datasheet is included in the Appendix.
9. Resources/Contact Information
Data sheets, applications information and samples for the ON Semiconductor
components are available at www.onsemi.com. Links to the datasheets of the main
components used in this design are included in the Appendix.
35
10.
Appendix
Link to ON Semiconductor’s web site:
ƒ ON Semiconductor Home Page
Industry Information Links
ƒ
ƒ
ƒ
ƒ
ƒ
ƒ
ƒ
ENERGY STAR
80 PLUS Efficiency Requirements
IEC1000-3-2 Requirements
ATX 12 V Form Factor
International Energy Agency
China Standard Certification Center (formerly CECP)
European Union (EU) Energy Star Page
36
MAGNETICS DESIGN DATA SHEET
Project / Customer: ON Semiconductor ATX project
Part Description: 300 W PFC choke - 4 A rms, 6 A pk, 600 uH, Rev. 2
Schematic ID: L4
Core Type: PQ32/30 (Mag Inc 43230), 100 kHz material
Core Gap: 0.075" (1.9 mm) total gap
Inductance: 550 - 650 uH
Bobbin Type: PC-B3230-LA (12 pin vertical mount)
Windings (in order):
Winding # / type
Turns / Material / Gauge / Insulation Data
1,2 - 5,6
73 turns of 4 strands of #26HN (or equiv. of
#21 Litz). Approx. 1 twist per inch; self terminate
to pins. Insulate with layer of mylar tape.
Hipot: NA
Lead Breakout / Pinout
Schematic
1,2
5,6
6 5
37
2 1
MAGNETICS DESIGN DATA SHEET
Project / Customer: ON Semiconductor ATX project
Part Description: Aux/standby flyback transformer; 65 kHz, Rev. 2
Schematic ID: T1
Core Type: E25/10/6 (E24-25)
Core Gap: 0.01" (0.25 mm) total
Inductance: 2.5 - 2.8 mH (primary)
Bobbin Type: Ferroxcube # E24-25PCB1-10 (10 pin horizontal mount)
Windings (in order):
Winding # / type
Turns / Material / Gauge / Insulation Data
30 V Secondary (10 - 9)
29 turns of #30HN over 1 layer; self-leads to pins;
Insulate with 1 or 2 layers of mylar tape.
Primary (3 - 1)
105 turns of #32HN, 35TPL x 3 layers; self-leads
to pins.
5 V Secondary (5 - 6)
5 turns of #22 triple insulated wire OR two strands
of #24HN spiral wound over window. Cuff ends with
tape if latter method is used for proper isolation from
primary.
Vacuum varnish
Hipot: 2.7 kV from 5 V secondary to primary and 30 V secondary
Lead Breakout / Pinout
Schematic
(top view)
10 9 8 7 6
1
5
3
6
10
12 3 4 5
9
38
MAGNETICS DESIGN DATA SHEET
Project / Customer:ON Semiconductor - ATX Project
Part Description: Main output choke; 3 output coupled inductor, 250 kHz, Rev. 2
Schematic ID: LX1
Core Type: PQ3230
Core Gap: 0.020" total (all in center leg preferred)
Inductance: 1.6 uH minimum on 5 V (foil) winding; 10 uH on 12 V windings
Bobbin Type: 12 pin vertical pc mount
Windings (in order):
Winding # / type
Turns / Material / Gauge / Insulation Data
5 volt winding (5, 6 - 1, 2)
Two turns of 4 strands of #20HN spiral wound
over 1 layer. Terminate 2 wires per pin at
both start and finish as shown below.
+12 volt winding (12, 11 - 8, 7)
- 12 volt winding (10 - 9)
Five turns of 5 strands of #20 HN with one strand
a different color for the -12 V winding. Terminate
the +12V windings at 2 wires per pin and the -12 V
winding ends to just one pin as shown below.
Hipot: 200 V between all windings clusters.Vacuum varnish
Lead Breakout / Pinout
Schematic
5
6
BOTTOM VIEW
1
2
12
11
10
12
starts 11
10
12 V side
9
finishes 8
7
9
7
8
39
1
finishes
2
3
5 V side
4
5
starts
6
MAGNETICS DESIGN DATA SHEET
Project / Customer: ON Semiconductor ATX project
Part Description: 3.3 V, 18 A output choke, 250 kHz, Rev. 2
Schematic ID: LX2
Core Type: E25/10/6 (E24-25)
Core Gap: 0.020" (0.51 mm) total; 10 mil thick paper across all legs
Inductance: 4.0 +/- 0.5 uH
Bobbin Type: Ferroxcube # E24-25PCB1-10 (10 pin horizontal mount)
Windings (in order):
Winding # / type
Turns / Material / Gauge / Insulation Data
Pins 2, 3, 4, 5 to 6, 7, 8, 9 respectively
6 turns of 4 strands of #20HN wound
quadrafilar on bobbin with ends terminated
as shown in drawings below.
Vacuum varnish
Hipot: NA
Lead Breakout / Pinout
Schematic
(top view)
2
3
4
5
10 9 8 7 6
6
7
8
9
12 3 4 5
Pins 1 and 10 not used
40
MAGNETICS DESIGN DATA SHEET
Project / Customer: ON Semiconductor - ATX Project
Part Description: 250 kHz forward converter transformer; 4 output, Rev. 2
Schematic ID: TX1
Core Type: PQ3230 (Ae = 1.6)
Core Gap: Gap to 550 to 650 uH
Inductance: 550 - 650 uH
Bobbin Type: Vertical 12 pin pcb mount
Windings (in order):
Winding # / type
Turns / Material / Gauge / Insulation Data
"A" Primary
28 turns of 3 strands of #30HN over one layer;
Self-leads to pins; insulate for 2.7 kV to next layer.
5 V Secondary
2 turns of 0.65" wide by 10 mil thick cu foil with
cuffed ends. Terminate with copper tabs.
+12/-12 V Secondary
5 turns of 13 strands of #28HN with one strand
being a different color for the -12 V winding. Selfleads to the pins with 6 strands per pin for the
+12 V strands. Wind over 1 layer. Insulate for
2.7 kV to next winding.
"B" Primary
28 turns of 3 strands of #30HN over one layer.
Self-leads to pins. Insulate for 1 kV to next layer.
Aux winding
3 turns of # 28HN spiral wound over "B" primary.
Self-leads to pins.
Hipot: 2.7 kV primary/aux to all secondaries. Vacuum varnish.
Lead Breakout / Pinout
Schematic
Bottom (pin side) view
12
Pri A
11
Pri B
10
9
Aux
8
Tab"S"
5V
Tab "F"
1
2
3 +12 V
4
5
-12 V
6
12
11
10
9
8
7
41
1
2
3
4
5
6
MAGNETICS DESIGN DATA SHEET
Project / Customer: ON Semiconductor ATX Project
Part Description: Active clamp gate driver transformer; 250 kHz, Rev 2
Schematic ID: TX2
Core Type: Ferrite toroid; approx 0.4" dia (OD)
Core Gap: NA
Inductance: 1.5 mH nominal
Bobbin Type: 6 pin header; 0.4" x 0.4" (existing Mesa Power Systems design)
Windings (in order):
Winding # / type
Turns / Material / Gauge / Insulation Data
Primary (1 - 3)
25 turns of #30 insulated wire, spread evenly over
entire core. Self-leads to pins.
Secondary (6 - 4)
41 turns of #32HN, spread evenly over entire core.
Self-leads to pins.
Varnish or epoxy coat.
Hipot: 1.5 kV between pri and sec. Note: Both winding are on primary side circuit
Lead Breakout / Pinout
Schematic
Top View
1
6
Pri
Sec
3
1
6
2
5
3
4
4
1 : 1.64
42
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