5 W CCCV AC-DC Adapter GreenPoint Reference Design

TND329/D
Rev. 4, FEB - 2008
5 W Cellular Phone CCCV (Constant
Current Constant Voltage)
AC-DC Adapter
Reference Design Documentation Package
© Semiconductor Components Industries, LLC, 2008
February, 2008 - Rev. 4
1
Publication Order Number:
TND329/D
Disclaimer: ON Semiconductor is providing this reference design documentation package “AS IS” and the recipient assumes
all risk associated with the use and/or commercialization of this design package. No licenses to ON Semiconductor's or any
third party's Intellectual Property is conveyed by the transfer of this documentation. This reference design documentation
package is provided only to assist the customers in evaluation and feasibility assessment of the reference design. It is expected
that users may make further refinements to meet specific performance goals.
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TND329
5 W Cellular Phone CCCV
(Constant Current Constant
Voltage) AC-DC Adapter
Reference Design Documentation
Package
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TECHNICAL NOTE
1 Overview
This reference document describes a built-and-tested,
GreenPointt solution for a cellular phone Constant Current
Constant Voltage (CCCV) AC-DC adapter. This design is
intended for isolated, low power, universal input off-line
applications where a constant current/constant voltage
output (CCCV) is required for charging NiCd, NiMH,
Lithium-ion or similar batteries. Typical applications would
include cell phone chargers or cordless phone chargers.
The reference design circuit consists of one single-sided
printed circuit board designed to fit into a standard cell
phone adapter plastic case.
As shown in Figure 1, the reference design offers a
simplified cell phone adapter power supply solution, where
by judicious choice of design tradeoffs, optimum
performance is achieved at minimum cost.
Figure 1. 5 W CCCV AC-DC Adapter
2 Introduction
Cell phones have become an ubiquitous device in our life.
In some developed countries, the percentage of penetration
of cell phones has reached almost 100% of the population.
With the growth of cell phones has come the proliferation of
small wall plug-in ac-dc adapters required for charging the
batteries (NiCd, NiMH, or Lithium-ion) of the cell phone.
A typical household will have anywhere from 4 to 10 ac-dc
adapters. In most households, these adapters remain plugged
in the socket continuously drawing power from the mains,
even though no phone may be attached to the adapter. For
this reason, the ac-dc adapter must be designed in such a
way that its power consumption in standby (no-load) mode
is very low. It is estimated that, on average, 25% of the
energy that passes through power supplies does so during
standby-mode (Source: NRDC).
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3.1 Regulatory Requirements for Standby (no-load)
Power Consumption and Active Mode Efficiency
3 Cell Phone AC-DC Adapter Requirements
The above paragraph showed the importance of reducing
the standby power. Not only the power consumption of a cell
phone ac-dc adapter in standby mode has to be very low but
the efficiency of the adapter, when it is charging the cell
phone batteries, has to be very high. High activemode
efficiency saves energy when electronic devices are `active',
which are the times when they consume the most energy.
(Examples: TV is turned on; computer is being used to play
a video game.) It is estimated that 75% of the energy that
passes through power supplies does so during active-mode
(Source: NRDC).
Several regulatory bodies around the world address low
standby power consumption and efficiency in active mode
for external power supply (EPS). These requirements target
two issues:
• Get rid of the losses in a no-load situation (e.g.: when
the ac-dc adapter is plugged in even when it is not
connected to the cell phone).
• Achieve good average active mode efficiency during
various active mode load conditions (25%, 50%, 75%
and 100%).
Many regulations have been proposed around the world.
Hereafter is the list of some of the most important ones:
ENERGY STAR): applicable in the US and international partners
http://www.energystar.gov/index.cfm?c=ext_power_supplies.power_supplies_consumers
Nameplate Output Power (Pno)
Minimum Average Efficiency in Active Mode (expressed as decimal)
ENERGY EFFICIENCY CRITERIA FOR ACTIVE MODE
0 to < 1 Watt
≥ 0.49 * Pno
> 1 and ≤ 49 Watts
≥ [0.09 * Ln(Pno)] + 0.49
> 49 Watts
≥ 0.84
ENERGY CONSUMPTION CRITERIA FOR NO LOAD
0 to <10 Watts
≤ 0.5 Watt
≥ 10 to ≤ 250 Watts
≤ 0.75 Watt
California Energy Commission: Effective January 1, 2007
Nameplate Output
Minimum Efficiency in Active Mode
0 to < 1 Watt
0.49 * Nameplate Output
> 1 and ≤49 Watts
[0.09 * Ln(Nameplate Output)] + 0.49
> 49 Watts
0.84
Maximum Energy Consumption in No-Load Mode
0 to <10 Watts
0.5 Watt
≥10 to ≤ 250 Watts
0.75 Watt
Where Ln (Nameplate Output) = Natural Logarithm of the nameplate output expressed in Watts
Effective July 1, 2008
Nameplate Output
Minimum Efficiency in Active Mode
0 to < 1 Watt
0.5 * Nameplate Output
> 1 and ≤ 51 Watts
[0.09 * Ln(Nameplate Output)] + 0.5
> 51 Watts
0.85
Maximum Energy Consumption in No-Load Mode
Any output
0.5 Watt
Where Ln (Nameplate Output) = Natural Logarithm of the nameplate output expressed in Watts
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European Union's Code of Conduct, version 2, November 24, 2004
No-load Power Consumption
No-load Power Consumption
Rated Output Power
Phase 1 (Jan. 1, 2005)
Phase 2 (Jan. 1, 2007)
> 0.3 W and < 15 W
0.30 W
0.30 W
> 15 W and < 50 W
0.50 W
0.30 W
> 50 W and < 60 W
0.75 W
0.30 W
> 60 W and < 150 W
1.00 W
0.50 W
Energy-Efficiency Criteria for Active Mode for Phase 1 (for the period January 1, 2005 to December 31, 2006)
Rated Output Power
Minimum Four Point Average (see Annex) or 100 % Load Efficiency in Active Mode
0 < W < 1.5
30
1.5 < W < 2.5
40
2.5 < W < 4.5
50
4.5 < W < 6.0
60
6.0 < W < 10.0
70
10.0 < W < 25.0
75
25.0 < W < 150.0
80
Energy-Efficiency Criteria for Active Mode for Phase 2 (valid after January 1, 2007)
Nameplate Output Power (Pno)
Minimum Four Point Average (see Annex) or 100 % Load Efficiency in Active Mode
(expressed as a decimal) (Note 1)
0<W<1
≥ 0.49 * Pno
1 < W < 49
≥ [0.09 * Ln(Pno)] + 0.49
49 < W < 150
≥ 0.84 (Note 2)
1. “Ln” refers to the natural logarithm. The algebraic order of operations requires that the natural logarithm calculation be performed first and
then multiplied by 0.09, with the resulting output added to 0.49. An efficiency of 0.84 in decimal form corresponds to the more familiar value
of 84% when expressed as a percentage.
2. Power supplies that have a power factor correction (PFC) to comply with IEC61000-3-2 (above 75 W input power) have a 0.04 (4%)
allowance, accordingly the minimum on mode load efficiency (100% or averaged) is relaxed to 0.80 (80%).
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Korea:
• External Power Supply - No load: 0.8 W
• Battery Charger - No load: 0.8 W
Worldwide legislation for EPS (external power supplies)
Country/State
Affected
Implementation
Date
Compliance
Required
(Mandatory
or
Voluntary)
ENERGY STAR
United States
January 1, 2005
Voluntary
http://www.energystar.gov/index.cfm?c=
ext_power_supplies.power_supplies_consumers
European Union
Europe
January 1, 2005
Voluntary
http://re.jrc.ec.europa.eu/energyefficiency/html/
standby_initiative_External%20Power%20Supplies.htm
China
January 1, 2005
Voluntary
Harmonized with ENERGY STAR,
http://www.cecp.org.cn/englishhtml/hlproductlist1.asp
California
January 1, 2007
Mandatory
http://www.energy.ca.gov/appliances/index.html
Australia,
New Zealand
October 1, 2008
Mandatory
Harmonized with ENERGY STAR,
http://www.energyrating.gov.au/eps2.html
Arizona
January 2008
Mandatory
Source: http://www.standardsasap.org
Massachusetts
January 2008
Mandatory
Source: http://www.standardsasap.org
New York
January 2008
Mandatory
Source: http://www.standardsasap.org
Regulatory
Agency/
Organization
China Standard
Certification Center
(CSC, ex-CECP)
California Energy
Commission
Australia Green‐
house Office (AGO)
Arizona
Massachusetts
New York
Oregon
Rhode Island
Vermont
Washington
Comments
Oregon
January 2008
Mandatory
Source: http://www.standardsasap.org
Rhode Island
January 2008
Mandatory
Source: http://www.standardsasap.org
Vermont
January 2008
Mandatory
Source: http://www.standardsasap.org
Washington
January 2008
Mandatory
Source: http://www.standardsasap.org
3. Sources: www.psma.com, www.standardsasap.org
4 Cell Phone AC-DC Adapter Specification
For cell phone OEM manufacturers, the ac-dc adapter is
a commodity. So, they impose their own stringent
specifications and de-rating guidelines while requiring low
costs. The key performance criteria for adapters are:
• Power density (driven by package size requirements)
• Safety
• Low case temperature
Also, since business travelers carry their cell phones
around the world, all of the ac-dc adapters for cell phones
are designed to cope with universal mains voltage: 90Vac
to 270 Vac, 47-63 Hz.
Input: 90 to 270 Vac, 50/60 Hz
Output: 5 Vdc ±2% at 1.0 A continuous (5 W); constant
voltage/constant current
Voltage Regulation: < 2% line and load combined
Current Regulation: < 10% lin and load combined
Output Ripple: Less than 100 mV p/p
Average Efficiency: > 0.09 * Ln (5) + 0.09 = 63.5% (per
ENERGY STAR)
Standby (no-load) power consumption < 300 mW
Operating Temperature: 0 to 50°C
Cooling: Convection
Input Protection: 18 ohm inrush limiting resistor
Output Protection: Over-current, over-voltage, and overtemperature
Safety Compliance: 3 kV I/O isolation
EMI Compliance: FCC Part 15 conducted EMI (Level B)
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5 Circuit Operation
Referring to the schematic in Figure 2, the charger is
designed around a simple flyback converter topology with
optocoupler feedback for both output voltage and current
sensing. The ac input is full-wave rectified by D1 and
R1
AC
input
C1
18, 2W
4.7nf
”x”
D1
1A
600V
filtered by C2A and C2B to provide a dc “bulk” bus to the
converter stage. R1 provides inrush current limiting at initial
supply turn-on while C1, L1, and C9 comprise a simple, yet
effective conducted EMI filter network.
L1
820 uH
1
4.7uf,
400Vdc
x2
C2A
7,8
C5
1.5 nf
1 kV
C2B
T1
MBRS360T3
R2
150K,
0.5W
D2
D3
MURS160
R4 Is
0.62
1W
C4
1000 uF
6.3V
C7
0.1
50V
_
5,6
Output
4
3
Q1
MMSD4148A 10
MMBT2907AW
C8
10uf
25V
D5
2
(4.3V)
MMSZ5229B
R7
D4
+
+
5.1V @ 1A
C9
NCP1014ST
R6
(Vtrim)
0
1nF
”Y”
R8
2.2K
U1
R5
3
2
4
U2
1
R3
200
1
4
+
C3
10uf
25V
NOTES:
1. L1 is Coilcraft part RFB0807- 821L (820 uH @ 300 mA)
2. U2 is 4 pin optocoupler with CTR of 50% minimum
3. See Magnetics Data Sheet for T1 construction details
4. U1 is 100 kHz version
5. D7 zener sets Vout: Vout = Vz + 0.85V
C6
1 nf
68
3
opto
2
6. R4 set max current: Imax = 0.65/R4
7. R6 allows for Vout trimming (increase only)
8. Fuse resistor recommended for R1
9. Crossed lines on schematic are not connected
Figure 2. 5 V / 1 A CC/CV Power Supply with Universal AC Input (Rev 3)
feedback loop closes and the output will be regulated. The
use of R3 forces the reference zener's current to be in a stable
part of the device's characteristic V/I curve such that
temperature effects are minimized. R6 can be used as an
option to trim the charger's output voltage up (only).
When the output current exceeds approximately 1 A, the
voltage drop across current sense resistor R4 is sufficient to
turn on PNP transistor Q1 and zener D5 is now bypassed and
the current level now activates the optocoupler and controls
the feedback loop. Although very simple, this current sense
circuit will provide a constant current output of
approximately 1 A all the way down to an output voltage of
1V. Beyond this the current will rise some but any output
cable resistance will prevent the current from exceeding
about 1.5 A maximum. Feedback loop compensation and
bandwidth is provided by capacitor C6.
Under constant current operation that would be typical of
a heavily discharged battery, the voltage on the auxiliary
winding could be sufficiently low that it is unable to
adequately power U1. In this case the NCP1014 derives its
operating bias from the internal DSS circuit (see device data
sheet for details of this feature). Although the output current
is limited via R4, the NCP1014 controller also has peak
current limiting internally. The controller employs current
mode control which limits the peak MOSFET current based
on the feedback signal from the optocoupler.
The flyback converter is comprised of the NCP1014
controller/MOSFET U1, flyback transformer T1, and output
rectifier/filter D2 and C4 respectively. An auxiliary winding
on T1 and associated components D4, C8, C3, R8, and R7
provide an operating bias (VCC) for the control chip and allow
for very low input standby power when the supply is in a
no-load or standby mode. Since the voltage produced by the
auxiliary winding tracks the main output voltage it is also
used to sense for overvoltage conditions in the event the
feedback loop opens. The OVP trip level can be adjusted by
the turns on the auxiliary winding and the value of R8. The
main secondary voltage is rectified (peak detected) by D2 and
filtered to a relatively smooth dc level by C4, the main output
capacitor. Capacitor C7 provides for additional high
frequency noise filtering for the output. A snubber network
composed of C5, R2 and D3 is implemented to clamp voltage
spikes caused by the primary leakage inductance of T1. This
network prevents potential damage to the MOSFET drain
terminal (pin 3) of U1 by limiting the peak voltage.
Constant output voltage and current regulation are
achieved by the combination of components Q1, D5, and R3
through R6. For output currents less than 1 A the circuit
performs as a constant voltage source. When the output
voltage reaches approximately 5.1 V, zener D5 conducts and
when sufficient current flows through R3 to produce the
0.9V necessary to turn the optocoupler diode on, the voltage
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6 Transformer Design
For low power applications it is desirable to have as small
a transformer as possible, however, as the transformer gets
smaller so does the core's cross sectional area. This forces
more primary turns in order to maintain an acceptable
magnetic flux density limit and can cause excessive turns
buildup in the bobbin such that effective primary to
secondary insulation becomes prohibitive. A large number
of primary turns also increase the primary leakage
inductance, not to mention the dc resistance of the windings
in general. Both of these factors contribute to lower
efficiency in the converter. In this design an EF16 ferrite
core (sometimes referred to as an E16/8/5) was used with a
satisfactory compromise with respect to the above
mentioned parametric issues. The transformer design is
shown in Figure 3. In this design there are sufficient primary
turns to allow operation with either the 65 kHz or 100 kHz
version of the NCP1014 controller. The turns ratio will also
allow flexible operation with outputs from 4 to 9 V. The
design shown in Figure 3 should be sufficient for any
magnetics fabrication house to produce the transformer.
Exact pinouts will depend on the specific layout, however,
the core selection, wire sizing, inductance value and turns
ratio should be adhered to for proper operation.
MAGNETICS DESIGN DATA SHEET
Project / Customer: ON Semiconductor - NCP1011/1014 Generic CP charger
Part Description: 5 watt flyback transformer, 4 - 9 volts out
(REV 3)
Schematic ID: T1
Core Type: EF16 (E16/8/5); 3C90 material or similar
Core Gap: Gap for 3.5 mH
Inductance: 3.5 mH +/-5%
Bobbin Type: 8 pin horizontal mount for EF16
Windings (in order):
Winding # / type
Turns / Material / Gauge / Insulation Data
Vcc/Boost (2 - 3)
28 turns of #35HN spiral wound over 1 layer. Insulate
with 1 layer of tape (500V insulation to next winding)
Primary (1 - 4)
150 turns of #35HN over 3 layers. Insulate for 3 kV
to the next winding.
5V Secondary (5, 6 - 7, 8)
14 turns of #25HN spiral wound over one layer with
0.050” (1.3mm) end margins.
Vacuum varinish assembly.
Hipot: 3 kV from boost/primary to secondary for 1 minute.
Vendor for xfmr: Mesa Power Systems (Escondido, CA) part # 131296
Lead Breakout / Pinout
Schematic
1
4
8
7
(Bottom View - facing pins)
6
5
4
3
2
1
3
2
Figure 3.
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5
6
7
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7 Test Results
7.1 Active Mode Efficiency
The efficiency curves with output loading at 25%, 50%,
75% and 100% for 120 and 230 Vac inputs are shown in
Figure 4.
90
Efficiency (%)
120Vac
230Vac
Efficiency (%)
80
70
20
30
40 50
% Load
60
70
80
90
25
72
61
50
70
65
75
70
67
100
68
67
Avg Eff. =
70%
65%
63.5%
63.5%
Note that the average efficiency for both ranges meets the
ENERGY STAR minimum requirement of 63.5% at this
particular power level. In the 230 Vac input case the
efficiency degradation occurs at light loading due to
increased circuit quiescent power, mainly due to higher
MOSFET switching losses at this input level.
50
10
230 Vac
ENERGY STAR Min =
60
0
% Load
120 Vac
100
Figure 4. 5 Watt CCCV Charger Efficiency
7.2 Standby (no load) Input Power Consumption
Input Power:
90 mW @ 230 Vac
75 mW @ 120 Vac
7.3 Output V/I Load Line Profiles
6
6
5
5
4
4
Vout (V)
V out (V)
Figures 5 and 6 show the output V/I load line profiles for 25°C and 50°C ambient temperatures.
3
2
3
2
1
1
0
0
0
0
0.2
0.4
0.6
0.8
1
1.2
0.2
0.4
0.6
0.8
1
1.2
Iout (A)
I out (A)
Figure 5. 5 Watt Cell Phone Charger V/I Profile @ 255C
Figure 6. 5 Watt Cell Phone Charger V/I Profile @ 505C
Note that despite the extremely simple current and voltage feedback circuit design, the voltage set point dropped
approximately 50 mV and the constant current level was less than 75 mA at the higher temperature. This temperature coefficient
variation is entirely acceptable for most applications, and is actually advantageous if the battery itself is in the same ambient
environment also.
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7.4 EMI Profile
converter operating just at the constant voltage/constant
current “knee”. Note that the conducted emissions are below
the Level B average limit.
The charger circuit was also tested at a local certified
EMI/EMC test facility for conducted EMI on the AC input
mains. The plot of Figure 7 shows the conducted EMI profile
for 120 Vac input with an output load of 1 A with the
Corrected Peak Data
M. Flom Associates, Inc.
CISPRB_AV
CISPRB_QP
EN 55022: 1998, Class B
Points of Interest
Line 2 (Phase)
90.0
80.0
Amplitude dBuV
70.0
60.0
50.0
40.0
30.0
20.0
10.0
0
100.0K
1.0M
10.0M
100.0M
Frequency MHz
Operator: LR
Job #: p0730008
09:18:23 AM, Wednesday, March 21, 2007
Figure 7.
7.5 Other Results
Figures 8 and 9 show the typical flyback voltage
waveforms on U1's internal MOSFET drain for 120 and
230Vac inputs respectively and 75% output loading. Note
that above approximately 50% load the flyback circuit
operates in continuous conduction mode (CCM).
Figure 8.
Figure 9.
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Figure 10 is the MOSFET drain waveform under no load conditions at 120 Vac input demonstrating skip-mode operation
for low input power consumption.
Figure 10. MOSFET Drain Waveform
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8 Bill of Materials
Part
Part Type
Quantity
ID
DFS (4 pin)
1
D1
1 A, 600 V Bridge Diode (Vishay)
MURS160T3
SMB
1
D3
1 A, 600 V UFR Diode
MBRS360T3G
SMC
1
D2
3 A, 60 V Schottky
MMSZ5229BT1
SOD-123
1
D5
4.3 V, 500 mW Zener (for 5 V output)
MMSD4148T1
SOD-123
1
D4
100 mA Signal Diode
SOT-23
1
Q1
PNP Signal xstr
4-pin
1
U2
Vishay SFH-615A-4 or Similar
SOT-223
1
U1
ON Semiconductor Controller
4.7 nF “X” Cap
Thru Hole, Disc
1
C1
4.7 nF “X” Capacitor, 250 Vac
1 nF “Y” Cap
Thru Hole, Disc
1
C9
1 nF “Y” Capacitor, 270 Vac
Ceramic Cap
Disc Cap
1
C5
1 nF, 1 kV Capacitor (snubber)
Ceramic Cap
SMD-0805
1
C6
1 nF, 100 V Ceramic Cap
Ceramic Cap
SMD-0805
1
C7
100 nF, 50 V Ceramic Cap
Electrolytic Cap
Radial Lead
2
C2A, C2B
Electrolytic Cap
Radial Lead
1
C4
Electrolytic Cap
Radial Lead
2
C3, C8
Resistor, 2 W
Axial Lead
1
R1
18 W, 2 W Metal Film or Wire Wound
Resistor, 1/4 W
SMD-1210
1
R2
150 k, 1/4 W
Resistor, 1/8 W
SMD-0805
1
R5
68 W
Resistor, 1/8 W
SMD-0805
1
R3
200 W
Resistor, 1/8 W
SMD-0805
1
R7
10 W
Resistor, 1/8 W
SMD-0805
1
R8
2k
Resistor, 1/4 W
Axial Lead
1
R6
TBD (jumper for 5 V output)
DF04S Bridge Diode
MMBT2907AWT1G
Optocoupler
NCP1014ST (100 kHz)
Description
4.7 or 6.8 mF, 400 Vdc
820 mF or 1000 mF, 6.3 V (low ESR)
10 or 22 mF, 25 V
Axial Lead
1
R4
0.62 W, 1 W Metal Film (for 1 A output)
Radial Lead
1
L1
Coilcraft RFB0807-821L
8-pin Thru Hole
1
T1
Mesa Power Systems # 13-1296 (custom)
AC Connector
Thru Hole
1
J1
DigiKey # 281-1435-ND (LS = 0.2″)
Output Connector
Thru Hole
1
J2
DigiKey # 281-1435-ND
Resistor, 1/2 W
EMI Inductor, 820 mH 300 mA
Transformer (see Figure 2)
(Top View)
Figure 11. Board Picture
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9 Appendix
References:
• Draft Commission Communication on Policy Instruments to Reduce Stand-by Losses of Consumer Electronic
Equipment (19 February 1999) - http://energyefficiency.jrc.cec.eu.int/pdf/consumer_electronics_communication.pdf
European Information & Communications Technology Industry Association - http://www.eicta.org/
•
• http://standby.lbl.gov/ACEEE/StandbyPaper.pdf
CSC (ex-CECP China):
• http://www.cecp.org.cn/englishhtml/index.asp
Energy Saving (Korea):
• http://weng.kemco.or.kr/efficiency/english/main.html#
Top Runner (Japan):
• http://www.eccj.or.jp/top_runner/index.html
EU Eco-label (Europe):
• http://europa.eu.int/comm/environment/ecolabel/index_en.htm
• http://europa.eu.int/comm/environment/ecolabel/product/pg_television_en.htm
EU Code of Conduct (Europe):
• http://energyefficiency.jrc.cec.eu.int/html/standby_initiative.htm
GEEA (Europe):
• http://www.efficient-appliances.org/
• http://www.efficient-appliances.org/Criteria.htm
ENERGY STAR:
• http://www.energystar.gov/
• http://www.energystar.gov/index.cfm?c=ext_power_supplies.power_supplies_consumers
1 Watt Executive Order:
• http://oahu.lbl.gov/
• http://oahu.lbl.gov/level_summary.html
Additional Collateral from ON Semiconductor:
• Design note DN06009/D: 5 W, CCCV Cell Phone
•
•
•
•
• Data sheet NCP1014/D: Self-Supply Monolithic
Battery Charger
Design note DN06017/D: Efficient, Low Cost, low
Standby Power (<100 mW), 2.5 W Cell Phone Charger
Design note DN06003/D: NCP1014: 8 W, 3-Output
Off-Line Switcher
Design note DN06005/D: NCP1014: 10 W, 3-Output
Off-line Power Supply
Design note DN06020/D: NCP1014: 10 W, Dual
Output Power Supply
•
•
•
•
•
Switcher for Low Standby-Power Offline SMPS
Data sheet MBRS360/D: 3 A, 60 V Schottky Rectifier
Data sheet MMSD4148/D: 100 V Switching Diode
Data sheet MURS160/D: 1 A, 600 V Ultrafast Rectifier
Data sheet MMSZ5229B/D: 500 mW Zener Diode
Data Sheet MMBT2907AWT1/D: PNP Transistor
GreenPoint is a trademark of Semiconductor Components Industries, LLC (SCILLC).
ON Semiconductor and
are registered trademarks of Semiconductor Components Industries, LLC (SCILLC). SCILLC reserves the right to make changes without further notice
to any products herein. SCILLC makes no warranty, representation or guarantee regarding the suitability of its products for any particular purpose, nor does SCILLC assume any liability
arising out of the application or use of any product or circuit, and specifically disclaims any and all liability, including without limitation special, consequential or incidental damages.
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TND329/D
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