Datasheet

ISL98002
®
Data Sheet
March 26, 2008
FN6535.0
Triple Video Digitizer with Digital PLL
Features
The ISL98002 3-Channel, 8-bit Analog Front End (AFE)
contains all the functions necessary to digitize analog YPbPr
video signals and RGB graphics signals from DVD players,
digital VCRs, video set-top boxes, and personal computers.
This product family’s conversion rates support HDTV
resolutions up to 1080p and PC monitor resolutions up to
UXGA, while the front end's programmable input bandwidth
ensures sharp, clear images at all resolutions.
• 140MSPS and 170MSPS maximum conversion rates
To maximize performance with the widest variety of video
sources, the ISL98002 features a fast-responding digital PLL
(DPLL), providing extremely low jitter with PC graphics signals
and quick recovery from VCR head switching with video
signals. Integrated HSYNC and SOG processing eliminate the
need for external slicers, sync separators, Schmitt triggers,
and filters.
• Programmable bandwidth (100MHz to 780MHz)
Glitchless, automatic Macrovision®- compliance is obtained
by a digital Macrovision® detection function that detects and
automatically removes Macrovision® from the HSYNC
signal.
• Pb-free (RoHS Compliant)
Ease of use is also emphasized with features such as the
elimination of PLL charge pump current/VCO range
programming and single-bit switching between RGB and
YPbPr signals. Automatic Black Level Compensation
(ABLC™) eliminates part-to-part offset variation, ensuring
perfect black level performance in every application.
• Projectors
• Glitchless Macrovision®-compliant sync separator
• Extremely fast recovery from VCR head switching
• Low PLL clock jitter (250ps peak-to-peak @ 170MSPS)
• 64 interpixel sampling positions
• 0.35VP-P to 1.4VP-P video input range
• RGB 4:4:4 and YUV 4:2:2 output formats
• Low power (535mW @ 170MSPS)
• Small 10mmx10mm 72 Ld QFN package
• Completely independent 8-bit gain/10-bit offset control
Applications
• Digital TVs
• Multifunction Monitors
• Digital KVM
• RGB Graphics Processing
Simplified Block Diagram
OFFSET
DAC
ABLC™
VOLTAGE
CLAMP
RGB/YPBPRIN
3
8
PGA
+
8-BIT ADC
RGB/YUVOUT
X3
HSYNCOUT
VSYNCOUT
SOGIN
HSOUT
HSYNCIN
SYNC PROCESSING
DIGITAL PLL
PIXELCLKOUT
VSYNCIN
AFE CONFIGURATION AND CONTROL
1
CAUTION: These devices are sensitive to electrostatic discharge; follow proper IC Handling Procedures.
1-888-INTERSIL or 1-888-468-3774 | Intersil (and design) is a registered trademark of Intersil Americas Inc.
Copyright Intersil Americas Inc. 2008. All Rights Reserved
All other trademarks mentioned are the property of their respective owners.
ISL98002
Ordering Information
PART NUMBER
(Note)
PART
MARKING
MAXIMUM
PIXEL RATE
TEMP RANGE (°C)
PACKAGE
(Pb-free)
PKG.
DWG. #
ISL98002CRZ-140
ISL98002CRZ -140
140MHz
0°C to +70°C
72 Ld QFN
L72.10x10B
ISL98002CRZ-170
ISL98002CRZ -170
170MHz
0°C to +70°C
72 Ld QFN
L72.10x10B
NOTE: These Intersil Pb-free plastic packaged products employ special Pb-free material sets; molding compounds/die attach materials and 100%
matte tin plate PLUS ANNEAL - e3 termination finish, which is RoHS compliant and compatible with both SnPb and Pb-free soldering operations.
Intersil Pb-free products are MSL classified at Pb-free peak reflow temperatures that meet or exceed the Pb-free requirements of IPC/JEDEC J STD020.
Block Diagram
VCLAMP
Offset
DAC
VIN+
8
VIN+
PGA
VIN-
RIN2
PGA
VIN-
RIN2
+
VCLAMP
8 bit ADC
OFFSET
Offset
DAC
10
10
DAC
GIN1
GIN2
PGA
VIN-
VIN-
+
+
VCLAMP
V
CLAMP
BIN2 BIN2
8 bit ADC
10
10
8
8
ABLC™
ABLC™
VIN+VIN+
VIN-VIN-
PGA
PGA
+
+
RP[7:0]
ABLC™
8-BIT ADC
Offset
OFFSET
DAC
DAC
R[7:0]
ABLC™
VIN+
PGA
8
8
VIN+
GIN2
BIN1 BIN1
8
8-BIT ADC
+
VCLAMP
GIN1
ABLC™
ADC
8 8-BIT
bit ADC
88
OUTPUT DATA FORMATTER
RIN1
10
ABLC™
Output Data Formatter
RIN1
10
OFFSET
DAC
VCLAMP
8
8
8 8
G[7:0]
GP[7:0]
BP[7:0]
B[7:0]
DATACLK
DATACLK
SOGIN1
DATACLK
SOGIN1
DATACLK
SOGIN2
SOGIN2
Sync
HSYNCIN1
HSYNCIN1
VSYNCIN1
SYNC
Processing
PROCESSING
AFE Configuration
AFE CONFIGURATION AND
and
Control
CONTROL
HSOUT
HSOUT
VSYNCIN1
HSYNCOUT
HSYNC
VSYNC
OUT OUT
CLOCKINV
CLOCKINV
XTAL
IN
XTALOUT
XTAL
IN
XTALOUT SCL
SCL
SDA
SADDR
SDA
Digital PLL
DIGITAL PLL
VSYNCOUT
XCLKOUT
XCLKOUT
Serial
Interface
SERIAL
INTERFACE
SADDR
2
FN6535.0
March 26, 2008
ISL98002
Absolute Maximum Ratings
Thermal Information
Voltage on VA, VD, or VX
(referenced to GND). . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 4.5V
Voltage on VADC, VCOREADC, VPLL, or VCORE
(referenced to GND). . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 2.5V
Voltage on any analog input pin
(referenced to GND). . . . . . . . . . . . . . . . . . . . . . . . . . . -0.3V to VA
Voltage on any digital input pin
(referenced to GND). . . . . . . . . . . . . . . . . . . . . . . . -0.3V to +6.0V
Current into any output pin. . . . . . . . . . . . . . . . . . . . . . . . . . . ±20mA
ESD Rating
Human Body Model . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .2000V
Machine Model . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .200V
Thermal Resistance
θJA (°C/W)
QFN Package (Note 1). . . . . . . . . . . . . . . . . . . . . . .
27
Maximum Biased Junction Temperature . . . . . . . . . . . . . . . . +125°C
Storage Temperature . . . . . . . . . . . . . . . . . . . . . . . .-65°C to +150°C
Pb-free reflow profile . . . . . . . . . . . . . . . . . . . . . . . . . .see link below
http://www.intersil.com/pbfree/Pb-FreeReflow.asp
Recommended Operating Conditions
Temperature (Commercial) . . . . . . . . . . . . . . . . . . . . . 0°C to +70°C
Supply Voltage. . . . . . . . . . . . . . . . . . . . . . . 3.3V ±10%, 1.8V ±10%
CAUTION: Do not operate at or near the maximum ratings listed for extended periods of time. Exposure to such conditions may adversely impact product reliability and
result in failures not covered by warranty.
NOTE:
1. θJA is measured with the component mounted on a high effective thermal conductivity test board in free air. See Tech Brief TB379 for details.
Electrical Specifications Specifications apply for VA = VD = VX = 3.3V, VCORE = VCOREADC = VADC = VPLL = 1.8V, pixel rate = 140MHz for
ISL98002-140, 170MHz for ISL98002-170, fXTAL = 25MHz, TA = +25°C, unless otherwise noted.
SYMBOL
PARAMETER
COMMENT
MIN
TYP
MAX
UNIT
FULL CHANNEL CHARACTERISTICS
Conversion Rate
Per Channel
MHz
ISL98002-140
10
140
MHz
ISL98002-170
10
170
MHz
ADC Resolution
8
Missing Codes
Bits
Guaranteed monotonic
DNL
Differential Non-Linearity
(Full-Channel)
ISL98002-140
None
(Note 3)
ISL98002-170
INL
Integral Non-Linearity
(Full-Channel)
ISL98002-140
±0.5
+1.0/-0.9
LSB
±0.5
+1.0/-0.9
LSB
±1.1
±2.75
LSB
±1.1
±3.25
LSB
(Note 3)
ISL98002-170
Gain Adjustment Range
Gain Adjustment Resolution
Gain Matching Between Channels
Percent of full-scale
Full Channel Offset Error,
ABLC™ Enabled
ADC LSBs,
over time and temperature
Offset Adjustment Range
(ABLC™ Enabled or Disabled)
ADC LSBs (See “Automatic Black Level
Compensation (ABLC™) and Gain
Control” on page 16)
±6
dB
8
Bits
±1
%
±0.125
±0.5
±127
LSB
LSB
ANALOG VIDEO INPUT CHARACTERISTICS (RIN, GIN, BIN)
Input Range
0.35
Input Bias Current
DC restore clamp off
Input Capacitance
Full Power Bandwidth
Programmable
0.7
1.4
VP-P
±0.01
±1
µA
5
pF
780
MHz
0 to 0.3
V
40
mV
5
pF
INPUT CHARACTERISTICS (SOGIN)
VIH/VIL
Input Threshold Voltage
Programmable - see “Register Listing”
on page 10
Hysteresis
Centered around threshold
Input Capacitance
3
FN6535.0
March 26, 2008
ISL98002
Electrical Specifications Specifications apply for VA = VD = VX = 3.3V, VCORE = VCOREADC = VADC = VPLL = 1.8V, pixel rate = 140MHz for
ISL98002-140, 170MHz for ISL98002-170, fXTAL = 25MHz, TA = +25°C, unless otherwise noted. (Continued)
SYMBOL
PARAMETER
COMMENT
MIN
TYP
MAX
UNIT
INPUT CHARACTERISTICS (HSYNCIN)
VIH/VIL
Input Threshold Voltage
Programmable - see “Register Listing”
on page 10
Hysteresis
Centered around threshold voltage
0.4 to 3.2
V
240
mV
RIN
Input Impedance
1.2
kΩ
CIN
Input Capacitance
5
pF
DIGITAL INPUT CHARACTERISTICS (SDA, SADDR, CLOCKINVIN, RESET)
VIH
Input HIGH Voltage
VIL
Input LOW Voltage
I
Input Leakage Current
2.0
V
0.8
RESET has a 70kΩ pull-up to VD
Input Capacitance
V
±10
nA
5
pF
SCHMITT DIGITAL INPUT CHARACTERISTICS (SCL, VSYNCIN)
VT+
Low to High Threshold Voltage
VT-
High to Low Threshold Voltage
I
1.45
V
0.95
Input Leakage Current
Input Capacitance
V
±10
nA
5
pF
DIGITAL OUTPUT CHARACTERISTICS (DATACLK, DATACLK)
VOH
Output HIGH Voltage, IO = 16mA
VOL
Output LOW Voltage, IO = -16mA
2.4
V
0.4
V
DIGITAL OUTPUT CHARACTERISTICS (R, G, B, HSOUT, HSYNCOUT, VSYNCOUT)
VOH
Output HIGH Voltage, IO = 8mA
VOL
Output LOW Voltage, IO = -8mA
RTRI
Pull-down to GNDD When Three-state
2.4
V
0.4
RP, GP, BP, RS, GS, BS only
56
V
kΩ
DIGITAL OUTPUT CHARACTERISTICS (SDA)
VOH
Output HIGH Voltage, IO = 4mA
VOL
Output LOW Voltage, IO = -4mA
XCLKOUT only; SDA is open-drain
2.4
V
0.4
V
POWER SUPPLY REQUIREMENTS
VA
Analog 3.3V Supply Voltage
3
3.3
3.6
V
VD
Digital 3.3V Supply Voltage
3
3.3
3.6
V
VX
Crystal Oscillator 3.3V Supply Voltage
3
3.3
3.6
V
IA
Analog 3.3V Supply Current
45
55
mA
ID
Digital 3.3V Supply Current
5
22
mA
IX
Crystal Oscillator 3.3V Supply Current
0.8
1.2
mA
1.8
2.0
V
VADC
VCORE
ADC Analog 1.8V Supply Voltage
With grayscale ramp input
1.65
Digital 1.8V Supply Voltage
1.65
1.8
2.0
V
ADC Digital 1.8V Supply Voltage
1.65
1.8
2.0
V
VPLL
PLL 1.8V Supply Voltage
1.65
1.8
2.0
V
IADC
ADC Analog 1.8V Supply Current
110
120
mA
Digital 1.8V Supply Current
70
80
mA
ADC Digital 1.8V Supply Current
11
20
mA
2.25
3
mA
VCOREADC
ICORE
ICOREADC
IPLL
PLL 1.8V Supply Current
4
FN6535.0
March 26, 2008
ISL98002
Electrical Specifications Specifications apply for VA = VD = VX = 3.3V, VCORE = VCOREADC = VADC = VPLL = 1.8V, pixel rate = 140MHz for
ISL98002-140, 170MHz for ISL98002-170, fXTAL = 25MHz, TA = +25°C, unless otherwise noted. (Continued)
SYMBOL
PD
PARAMETER
COMMENT
MIN
TYP
MAX
UNIT
Total Power Dissipation
ISL98002-140
With grayscale ramp input
525
575
mW
ISL98002-170
With grayscale ramp input
535
600
mW
Standby Mode
ADCs, PLL powered down
35
80
mW
PLL Jitter
(Note 4)
250
450
ps p-p
Sampling Phase Steps
5.6° per step
64
AC TIMING CHARACTERISTICS
Sampling Phase Tempco
Sampling Phase
Differential Nonlinearity
fXTAL
Degrees out-of-phase 360°
HSYNC Frequency Range
10
±1
ps/°C
±3
°
150
kHz
Crystal Frequency Range
23
25
27
MHz
fXTALIN
Frequency Range with External 3.3V Clock
Signal Driving XTALIN
23
25
33.5
MHz
tSETUP
DATA Valid Before Rising Edge of DATACLK 15pF DATACLK load, 15pF DATA load
(Note 2)
1.3
ns
tHOLD
DATA Valid After Rising Edge of DATACLK
2.0
ns
15pF DATACLK load, 15pF DATA load
(Note 2)
AC TIMING CHARACTERISTICS (2-WIRE INTERFACE)
fSCL
SCL Clock Frequency
0
Maximum Width of a Glitch on SCL That Will 2 XTAL periods min
Be Suppressed
80
400
kHz
ns
tAA
SCL LOW to SDA Data Out Valid
tBUF
Time the Bus Must Be Free Before a New
Transmission Can Start
1.3
µs
tLOW
Clock LOW Time
1.3
µs
tHIGH
Clock HIGH Time
0.6
µs
5 XTAL periods plus SDA’s RC time
constant
See
comment
µs
tSU:STA
Start Condition Set-up Time
0.6
µs
tHD:STA
Start Condition Hold Time
0.6
µs
tSU:DAT
Data In Set-up Time
100
ns
tHD:DAT
Data In Hold Time
tSU:STO
Stop Condition Set-up Time
tDH
Data Output Hold Time
4 XTAL periods min
0
ns
0.6
µs
160
ns
NOTES:
2. Setup and hold times are specified for a 170MHz DATACLK rate.
3. Linearity tested at room temperature and guaranteed across commercial temperature range by correlation to characterization.
4. Jitter tested at rated frequencies (170MHz, 140MHz) and at minimum frequency (10MHz).
5
FN6535.0
March 26, 2008
ISL98002
tHIGH
tF
SCL
tLOW
tR
tSU:DAT
tSU:STA
tHD:DAT
tSU:STO
tHD:STA
SDA IN
tAA
tDH
tBUF
SDA OUT
FIGURE 1. 2-WIRE INTERFACE TIMING
DATACLK
DATACLK
tHOLD
tSETUP
Pixel Data
FIGURE 2. DATA OUTPUT SETUP AND HOLD TIMING
The HSYNC edge (programmable leading or trailing) that the DPLL is locked to.
The sampling phase setting determines its relative position to the rest of the AFE’s output signals
HSYNCIN
tHSYNCin-to-HSout = 7.5ns + (PHASE/64 +8.5)*tPIXEL
Analog
Video In
P0
P1
P2
P3
P4
P5
P6
P7
P8
P9
P10
P11
P12
DATACLK
8 DATACLK Pipeline Latency
RP/GP/BP[7:0]
D0
D1
D2
D3
RS/GS/BS[7:0]
Programmable
Width and Polarity
HSOUT
FIGURE 3. OUTPUT MODE
6
FN6535.0
March 26, 2008
ISL98002
The HSYNC edge (programmable leading or trailing) that the DPLL is locked to.
The sampling phase setting determines its relative position to the rest of the AFE’s output signals
HSYNCIN
tHSYNCin-to-HSout = 7.5ns + (PHASE/64 +8.5)*tPIXEL
Analog
Video In
P0
P1
P2
P3
P4
P5
P6
P7
P8
P9
P10
P11
P12
DATACLK
8.5 DATACLK Pipeline Latency
GP[7:0]
G0 (Yo)
G1 (Y1)
G2 (Y2)
RP[7:0]
B0 (Uo)
R1 (V1)
B2 (U2)
BP[7:0]
Programmable
Width and Polarity
HSOUT
FIGURE 4. 4:2:2 OUTPUT MODE (FOR YUV SIGNALS)
7
FN6535.0
March 26, 2008
ISL98002
Pinout
VSYNCOUT
HSYNCOUT
HSOUT
VD
DATACLK
DATACLK
R0
R1
R2
R3
R4
R5
R6
R7
VD
VCORE
VD
NC
72
71
70
69
68
67
66
65
64
63
62
61
60
59
58
57
56
55
ISL98002
(72 LD QFN)
TOP VIEW
G7
VA
10
45
VD
B IN 1
11
44
VD
VA
12
43
B0
R IN 2
13
42
B1
G IN 2
14
41
B2
SOG IN 2
15
40
B3
B IN 2
16
39
B4
V COREADC
17
38
B5
HSYNC IN 1
18
37
B6
VA
8
36
46
B7
9
35
V ADC
VD
G6
34
47
GND
8
33
SOG IN 1
NC
G5
32
48
VCORE
7
31
G IN 1
SCL
G4
30
49
SDA
6
29
VA
SADDR
G3
28
50
RESET
5
27
V ADC
VSYNCIN1
G2
26
51
VPLL
4
25
R IN 1
CLOCKINVIN
G1
24
52
XTALOUT
3
23
VA
GND
NC
22
53
XTALIN
2
21
NC
VX
G0
20
54
NC
1
19
V ADC
FN6535.0
March 26, 2008
ISL98002
Pin Descriptions
SYMBOL
QFN PIN #(s)
DESCRIPTION
RIN1
4
Analog input. Red channel. DC couple or AC couple through 0.1µF.
GIN1
7
Analog input. Green channel. DC couple or AC couple through 0.1µF.
BIN1
11
Analog input. Blue channel. DC couple or AC couple through 0.1µF.
SOGIN1
8
Analog input. Sync on Green. Connect to GIN through a 0.01µF capacitor in series with a 500Ω resistor.
HSYNCIN1
18
Digital input, 5V tolerant, 240mV hysteresis, 1.2kΩ impedance to GND. Connect to HSYNC signal through a
680Ω series resistor.
VSYNCIN1
27
Digital input, 5V tolerant, 500mV hysteresis. Connect to VSYNC signal.
RIN2
13
Analog input. Red channel. DC couple or AC couple through 0.1µF.
GIN2
14
Analog input. Green channel. DC couple or AC couple through 0.1µF.
BIN2
16
Analog input. Blue channel. DC couple or AC couple through 0.1µF.
SOGIN2
15
Analog input. Sync on Green. Connect to GIN through a 0.01µF capacitor in series with a 500Ω resistor.
CLOCKINVIN
25
Digital input, 5V tolerant. When high, inverts the pixel sampling phase by 180°. Tie to GND if unused.
RESET
28
Digital input, 5V tolerant, active low, 70kΩ pull-up to VD. Take low for at least 1µs and then high again to reset
the ISL98002. This pin is not necessary for normal use and may be tied directly to the VD supply.
XTALIN
22
Analog input. Connect to external 24.5MHz to 27MHz crystal and load capacitor (see “Electrical
Specifications” table on page 5 for recommended loading). Typical oscillation amplitude is 1.0VP-P centered
around 0.5V.
XTALOUT
24
Analog output. Connect to external 24.5MHz to 27MHz crystal and load capacitor (see “Electrical
Specifications” table on page 5 for recommended loading). Typical oscillation amplitude is 1.0VP-P centered
around 0.5V.
SADDR
29
Digital input, 5V tolerant. Address = 0x4C when tied low. Address = 0x4D when tied high.
SCL
31
Digital input, 5V tolerant, 500mV hysteresis. Serial data clock for 2-wire interface.
SDA
30
Bidirectional Digital I/O, open drain, 5V tolerant. Serial data I/O for 2-wire interface.
R7 thru R0
59 thru 66
G7 thru G0
46 thru 52, 54
B7 thru B0
36 thru 43
3.3V digital output. Red channel, primary pixel data. 56k pull-down when three-stated.
3.3V digital output. Green channel, primary pixel data. 56k pull-down when three-stated.
3.3V digital output. Blue channel, primary pixel data. 56k pull-down when three-stated.
DATACLK
67
3.3V digital output. Data clock output. Equal to pixel clock rate.
DATACLK
68
3.3V digital output. Inverse of DATACLK.
HSOUT
70
3.3V digital output. HSYNC output aligned with pixel data. Use this output to frame the digital output data.
This output is always purely horizontal sync (without any composite sync signals).
HSYNCOUT
71
3.3V digital output. Buffered HSYNC (or SOG or CSYNC) output. This is typically used for measuring HSYNC
period. This output will pass composite sync signals and Macrovision signals if present on HSYNCIN or
SOGIN.
VSYNCOUT
72
3.3V digital output. Buffered VSYNC output. For composite sync signals, this output will be asserted for the
duration of the disruption of the normal HSYNC pattern. This is typically used for measuring VSYNC period.
VA
3, 6, 10, 12, 19
Power supply for the analog section. Connect to a 3.3V supply and bypass each pin to GNDA with 0.1µF.
VD
35, 44, 45, 56,
58, 69
Power supply for all digital I/Os. Connect to a 3.3V supply and bypass each pin to GNDD with 0.1µF.
VX
21
GND
PAD, 23, 34
VADC
1, 5, 9
VCOREADC
17
VCORE
32, 57
VPLL
NC
Power supply for crystal oscillator. Connect to a 3.3V supply and bypass to GNDX with 0.1µF.
Ground return.
Internal power for the ADC’s analog. Connect to a 1.8V supply and bypass to GND with 0.1µF.
Internal power for the ADC’s digital logic. Connect to a 1.8V supply and bypass to GND with 0.1µF.
Internal power for core logic. Connect to a 1.8V supply and bypass each pin to GND with 0.1µF.
26
Internal power for the PLL’s digital logic. Connect to a 1.8V supply and bypass to GND with 0.1µF.
2, 20, 33, 53, 55 Reserved. Do not connect anything to these pins.
9
FN6535.0
March 26, 2008
ISL98002
Register Listing
ADDRESS
0x00
0x01
0x02
0x03
REGISTER (DEFAULT VALUE)
Device ID
(read only)
SYNC Status
(read only)
SYNC Polarity
(read only)
HSYNC Slicer (0x33)
BIT(S)
SOG Slicer (0x16)
Device Revision
1 = initial silicon, 2 = second revision, etc.
7:4
Device ID
1 = ISL98002
0
HSYNC1 Active
0: HSYNC is Inactive
1: HSYNC is Active
1
N/A
Returns 0
2
VSYNC1 Active
0: VSYNC is Inactive
1: VSYNC is Active
3
N/A
Returns 0
4
SOG1 Active
0: SOG is Inactive
1: SOG is Active
5
SOG2 Active
0: SOG is Inactive
1: SOG is Active
6
PLL Locked
0: PLL is unlocked
1: PLL is locked to incoming HSYNC
7
CSYNC Detect at
Sync Splitter
0: Composite Sync signal not detected
1: Composite Sync signal is detected
0
HSYNC
Polarity
0: HSYNC is Active High
1: HSYNC is Active Low
1
N/A
Returns 0
2
VSYNC
Polarity
0: VSYNC is Active High
1: VSYNC is Active Low
3
N/A
Returns 0
4
SOG1 TriLevel
0: SOG is BiLevel Sync
1: SOG is TriLevel Sync
5
SOG2 TriLevel
0: SOG is BiLevel Sync
1: SOG is TriLevel Sync
7:6
N/A
Returns 0
2:0
HSYNC Threshold
000 = lowest (0.4V)
011 = default (1.6V)
111 = highest (3.2V)
Note: All values referred to voltage at HSYNC
input pin, 240mV hysteresis
6:3
Reserved
Set to 0
Disable Glitch Filter
0: HSYNC/VSYNC Glitch Filter Enabled (default)
1: HSYNC/VSYNC Glitch Filter Disabled
3:0
SOG
Threshold
0x0 = lowest (0mV)
0x6 = default (120mV) 20mV step size
0xF = highest (300mV)
4
SOG Filter
Enable
0: SOG low pass filter disabled
1: SOG low pass filter enabled, 14MHz corner
(default)
5
SOG Hysteresis
Disable
0: 40mV SOG hysteresis enabled (default)
1: 40mV SOG hysteresis disabled
Reserved
Set to 00.
7:6
10
DESCRIPTION
3:0
7
0x04
FUNCTION NAME
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ISL98002
Register Listing (Continued)
ADDRESS
0x05
REGISTER (DEFAULT VALUE)
Input configuration (0x00)
BIT(S)
FUNCTION NAME
DESCRIPTION
0
Reserved
Set to 0.
1
Input Coupling
0: AC coupled (positive input connected to clamp
DAC during clamp time, negative input disconnected
from outside pad and always internally tied to
appropriate clamp DAC)
1: DC coupled (+ and - inputs are brought to pads and
never connected to clamp DACs). Analog clamp
signal is turned off in this mode.
2
RGB/YPbPr
0: RGB inputs
Base ABLC target code = 0x00 for R, G, and B)
1: YPbPr inputs
Base ABLC target code = 0x00 for G (Y)
Base ABLC target code = 0x80 for R (Pr) and B (Pb)
3
Sync Type
0: Separate HSYNC/VSYNC
1: Composite (from SOG or CSYNC on HSYNC)
4
Composite Sync
Source
0: SOGIN
1: HSYNCIN
Note: If Sync Type = 0, the multiplexer will pass
HSYNCIN regardless of the state of this bit.
5
COAST CLAMP
enable
0: DC restore clamping and ABLC™ suspended
during COAST
1: DC restore clamping and ABLC™ continue during
COAST
6
Sync Mask Disable
0: Interval between HSYNC pulses masked
(preventing PLL from seeing Macrovision and any
spurious glitches)
1: Interval between HSYNC pulses not masked
(Macrovision will cause PLL to lose lock)
7
HSYNCOUT Mask
Disable
0: HSYNCOUT signal is masked (any Macrovision,
sync glitches on incoming SYNC are stripped from
HSYNCOUT)
1: HSYNCOUT signal is not masked (any
Macrovision, sync glitches on incoming SYNC
appear on HSYNCOUT)
If Sync Mask Disable = 1, HSYNCOUT is not masked.
Channel gain, where:
gain (V/V) = 0.5 + [7:0]/170
0x06
Red Gain (0x55)
7:0
Red Gain
0x07
Green Gain (0x55)
7:0
Green Gain
0x08
Blue Gain (0x55)
7:0
Blue Gain
0x00: gain = 0.5V/V
(1.4VP-P input = full range of ADC)
0x55: gain = 1.0V/V
(0.7VP-P input = full range of ADC)
0xFF: gain = 2.0V/V
(0.35VP-P input = full range of ADC)
11
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Register Listing (Continued)
ADDRESS
REGISTER (DEFAULT VALUE)
BIT(S)
FUNCTION NAME
0x09
Red Offset (0x80)
7:0
Red Offset
0x0A
Green Offset (0x80)
7:0
Green Offset
0x0B
Blue Offset (0x80)
7:0
Blue Offset
0x0C
Offset DAC Configuration (0x00)
0x0D
AFE Bandwidth (0x2E)
DESCRIPTION
ABLC™ enabled: digital offset control. A 1 LSB
change in this register will shift the ADC output by
1 LSB. ABLC™ disabled: analog offset control. These
bits go to the upper 8-bits of the 10-bit offset DAC. A
1 LSB change in this register will shift the ADC output
approximately 1 LSB (Offset DAC range = 0) or
0.5LSBs (Offset DAC range = 1).
0x00 = min DAC value or -0x80 digital offset,
0x80 = mid DAC value or 0x00 digital offset,
0xFF = max DAC value or +0x7F digital offset
0
Offset DAC Range
0: ±½ ADC full-scale (1 DAC LSB ~ 1 ADC LSB)
1: ±¼ ADC full-scale (1 DAC LSB ~ ½ ADC LSB)
1
Reserved
Set to 0.
3:2
Red Offset DAC
LSBs
5:4
Green Offset DAC
LSBs
These bits are the LSBs necessary for 10-bit manual
offset DAC control.
Combine with their respective MSBs in registers
0x09, 0x0A, and 0x0B to achieve 10-bit offset DAC
control.
7:6
Blue Offset DAC
LSBs
0
Unused
Value doesn’t matter
3:1
AFE BW
3dB point for AFE lowpass filter
000b: 100MHz
111b: 780MHz (default)
7:4
Peaking
0x0: Peaking off
0x1: Moderate peaking
0x2: Maximum recommended peaking (default)
Values above 2 are not recommended.
14-bit HTOTAL (number of active pixels) value
The minimum HTOTAL value supported is 0x200.
HTOTAL to PLL is updated on LSB write only.
0x0E
PLL Htotal MSB (0x03)
5:0
PLL Htotal MSB
0x0F
PLL Htotal LSB (0x20)
7:0
PLL Htotal LSB
0x10
PLL Sampling Phase (0x00)
5:0
PLL Sampling Phase Used to control the phase of the ADC’s sample point
relative to the period of a pixel. Adjust to obtain
optimum image quality. One step = 5.625° (1.56% of
pixel period).
0x11
PLL Pre-coast (0x04)
7:0
Pre-coast
Number of lines the PLL will coast prior to the start of
VSYNC.
0x12
PLL Post-coast (0x04)
7:0
Post-coast
Number of lines the PLL will coast after the end of
VSYNC.
12
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Register Listing (Continued)
ADDRESS
0x13
REGISTER (DEFAULT VALUE)
PLL Misc (0x04)
BIT(S)
FUNCTION NAME
DESCRIPTION
0
PLL Lock Edge
HSYNC
0: Lock on trailing edge of HSYNC (default)
1: Lock on leading edge of HSYNC
1
Reserved
Set to 0
2
Reserved
Set to 0
3
CLKINVIN Pin
Disable
0: CLKINVIN pin enabled (default)
1: CLKINVIN pin disabled (internally forced low)
5:4
CLKINVIN Pin
Function
00: CLKINV (default)
01: External CLAMP (See Note)
10: External COAST
11: External PIXCLK
Note: the CLAMP pulse is used to
- perform a DC restore (if enabled)
- start the ABLC™ function (if enabled), and
- update the data to the Offset DACs (always).
In the default internal CLAMP mode, the ISL98002
automatically generates the CLAMP pulse. If External
CLAMP is selected, the Offset DAC values only
change on the leading edge of CLAMP. If there is no
internal clamp signal, there will be up to a 100ms
delay between when the PGA gain or offset DAC
register is written to, and when the PGA or offset DAC
is actually updated.
6
Reserved
Set to 0
7
Reserved
Set to 1
Pixel after HSYNCIN trailing edge to begin
DC restore and ABLC™ functions. 13-bits.
Set this register to the first stable black pixel following
the trailing edge of HSYNCIN.
0x14
DC Restore and ABLC™ starting pixel
MSB (0x00)
4:0
DC Restore and
ABLC™ starting
pixel (MSB)
0x15
DC Restore and ABLC™ starting pixel LSB
(0x03)
7:0
DC Restore and
ABLC™ starting
pixel (LSB)
0x16
DC Restore Clamp Width
(0x10)
7:0
DC Restore clamp
width (pixels)
Width of DC restore clamp used in AC-coupled
configurations. Has no effect on ABLC™. Minimum
value is 0x02 (a setting of 0x01 or 0x00 will not
generate a clamp pulse).
0x17
ABLC™ Configuration (0x40)
0
ABLC™ disable
0: ABLC™ enabled (default)
1: ABLC™ disabled
1
Reserved
Set to 0.
3:2
ABLC™ pixel width
Number of black pixels averaged every line for
ABLC™ function
00: 16 pixels [default]
01: 32 pixels
10: 64 pixels
11: 128 pixels
6:4
ABLC™ bandwidth
ABLC™ Time constant (lines) = 2(5+[6:4])
000 = 32 lines
100 = 256 lines (default)
111 = 4096 lines
Reserved
Set to 0.
7
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Register Listing (Continued)
ADDRESS
0x18
REGISTER (DEFAULT VALUE)
Output Format (0x00)
0x19
HSOUT Width (0x10)
0x1A
Output Signal Disable (0x00)
0x1B
0x1C
Power Control (0x00)
PLL Tuning (0x49)
14
BIT(S)
FUNCTION NAME
DESCRIPTION
0
Reserved
Set to 0
1
Reserved
Set to 0
2
Reserved
Set to 0
3
UV order
(422 mode only)
0: U0 V0 U2 V2 U4 V4 U6 V6… (default)
1: U0 V1 U2 V3 U4 V5 U6 V7… (X980xx)
4
422 mode
0: Data is formatted as 4:4:4 (RGB, default)
1: Data is decimated to 4:2:2 (YUV), blue channel is
driven low
5
DATACLK
Polarity
0: HSOUT and Pixel Data changes on falling edge of
DATACLK (default)
1: HSOUT and Pixel Data changes on rising edge of
DATACLK
6
Reserved
Set to 0
7
HSOUT Polarity
0: Active High (default)
1: Active Low
HSOUT Width
HSOUT width, in pixels. Minimum value is 0x01
0
Three-state R[7:0]
0 = Output byte enabled
1 = Output byte three-stated
These bits override all other I/O settings
Output data pins have 56kΩ pull-down resistors to
GND.
1
Reserved
Set to 1
2
Three-state G[7:0]
3
Reserved
4
Three-state B[7:0]
5
Reserved
Set to 1
6
Three-state
DATACLK
0 = DATACLK enabled
1 = DATACLK three-stated
7
Three-state
DATACLK
0 = DATACLK enabled
1 = DATACLK three-stated
0
Red
Power-down
0 = Red ADC operational (default)
1 = Red ADC powered down
1
Green
Power-down
0 = Green ADC operational (default)
1 = Green ADC powered down
2
Blue
Power-down
0 = Blue ADC operational (default)
1 = Blue ADC powered down
3
PLL
Power-down
0 = PLL operational (default)
1 = PLL powered down
7:4
Reserved
Set to 0
7:0
Reserved
Use default setting of 0x49 for all PC and video
modes except signals coming from an analog VCR.
Set to 0x4C for analog videotape compatibility.
7:0
Set to 1
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Register Listing (Continued)
ADDRESS
REGISTER (DEFAULT VALUE)
BIT(S)
FUNCTION NAME
DESCRIPTION
0x1D
Red ABLC Target (0x00)
7:0
Reserved
This is a 2's complement number controlling the
target code of the Red ADC output when ABLC is
enabled.
In RGB mode, the Red ADC output will be servoed to
0x00 + the number in this register (-0x00 to +0x7F).
In YPbPr mode, the Red ADC output will be servoed
to 0x80 + the number in this register (-0x80 to +0x7F).
Note: This register does NOT disable the digital offset
adder. Both functions can be used simultaneously.
0x1E
Green ABLC Target (0x00)
7:0
Reserved
This is a 2's complement number controlling the
target code of the Green ADC output when ABLC is
enabled.
In RGB and YPbPr modes, the Green ADC output will
be servoed to 0x00 + the number in this register
(-0x00 to +0x7F).
Note: This register does NOT disable the digital offset
adder. Both functions can be used simultaneously.
0x1F
Blue ABLC Target (0x00)
7:0
Reserved
This is a 2's complement number controlling the
target code of the Blue ADC output when ABLC is
enabled.
In RGB mode, the Blue ADC output will be servoed to
0x00 + the number in this register (-0x00 to +0x7F).
In YPbPr mode, the Blue ADC output will be servoed
to 0x80 + the number in this register (-0x80 to +0x7F).
Note: This register does NOT disable the digital offset
adder. Both functions can be used simultaneously.
0x23
DC Restore Clamp (0x18)
3:0
Reserved
Set to 1000
6:4
DC Restore Clamp
Impedance
DC Restore clamp's ON-resistance.
Shared for all three channels
0: Infinite (clamp disconnected) (default)
1: 1600Ω
2: 800Ω
3: 533Ω
4: 400Ω
5: 320Ω
6: 267Ω
7: 228Ω
Reserved
Set to 0
7
15
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Register Listing (Continued)
ADDRESS
0x25
REGISTER (DEFAULT VALUE)
Sync Separator Control (0x00)
BIT(S)
DESCRIPTION
0
Three-state Sync
Outputs
0: VSYNCOUT, HSYNCOUT, HSOUT are active
(default)
1: VSYNCOUT, HSYNCOUT, HSOUT are in three-state
1
COAST Polarity
0: Coast active high (default)
1: Coast active low
Set to 0 for internal VSYNC extracted from CSYNC.
Set to 0 or 1 as appropriate to match external VSYNC
or external COAST.
2
HSOUT Lock Edge
0: HSOUT's trailing edge is locked to selected
HSYNCIN's lock edge. Leading edge moves
backward in time as HSOUT width is increased
(X980xx default)
1: HSOUT's leading edge is locked to selected
HSYNCIN's lock edge. Trailing edge moves forward
in time as HSOUT width is increased
3
Reserved
Set to 0
4
VSYNCOUT Mode
0: VSYNCOUT is aligned to HSYNCOUT edge,
providing “perfect” VSYNC signal (default)
1: VSYNCOUT is “raw” integrator output
5
Reserved
Set to 0
6
Reserved
Set to 0
7
Reserved
Set to 0
Technical Highlights
The ISL98002 provides all the features of traditional triple
channel video AFEs, but adds several next-generation
enhancements, bringing performance and ease of use to
new levels.
DPLL
All video AFEs must phase lock to an HSYNC signal,
supplied either directly or embedded in the video stream
(Sync On Green). Historically, this has been implemented as
a traditional analog PLL. At SXGA and lower resolutions, an
analog PLL solution has proven adequate, if somewhat
troublesome (due to the need to adjust charge pump
currents, VCO ranges and other parameters to find the
optimum trade-off for a wide range of pixel rates).
As display resolutions and refresh rates have increased,
however, the pixel period has shrunk. An XGA pixel at a
60Hz refresh rate has 15.4ns to change and settle to its new
value. But at UXGA 75Hz, the pixel period is 4.9ns. Most
consumer graphics cards (even the ones with “350MHz”
DACs) spend most of that time slewing to the new pixel
value. The pixel may settle to its final value with 1ns or less
before it begins slewing to the next pixel. In many cases, it
rings and never settles at all. Thus precision, low-jitter
sampling is a fundamental requirement at these speeds, and
a difficult one for an analog PLL to meet.
The ISL98002's DPLL has less than 250ps of jitter,
peak-to-peak, and independent of the pixel rate. The DPLL
generates 64 phase steps per pixel (vs the industry standard
16
FUNCTION NAME
32), for fine, accurate positioning of the sampling point. The
crystal-locked NCO inside the DPLL completely eliminates
drift due to charge pump leakage, so there is inherently no
frequency or phase change across a line. An intelligent
all-digital loop filter/controller eliminates the need for the user
to have to program or change anything (except for the number
of pixels) to lock over a range from interlaced video (10MHz or
higher) to UXGA 60Hz (170MHz, with the ISL98002-170).
The DPLL eliminates much of the performance limitations and
complexity associated with noise-free digitization of high
speed signals.
Automatic Black Level Compensation (ABLC™)
and Gain Control
Traditional video AFEs have an offset DAC prior to the ADC,
to both correct for offsets on the incoming video signals and
add/subtract an offset for user “brightness control” without
sacrificing the 8-bit dynamic range of the ADC. This solution
is adequate, but it places significant requirements on the
system's firmware, which must execute a loop that detects
the black portion of the signal and then serves the offset
DACs until that offset is nulled (or produces the desired ADC
output code). Once this has been accomplished, the offset
(both the offset in the AFE and the offset of the video card
generating the signal) is subject to drift (the temperature
inside a monitor or projector can easily change +50°C)
between power-on/offset calibration on a cold morning and
the temperature reached once the monitor and the monitor's
environment has reached a steady state. Offset can drift
significantly over +50°C, reducing image quality and
FN6535.0
March 26, 2008
ISL98002
requiring that the user do a manual calibration once the
monitor has warmed up.
In addition to drift, many AFEs exhibit interaction between
the offset and gain controls. When the gain is changed, the
magnitude of the offset is changed as well. This again
increases the complexity of the firmware as it tries to
optimize gain and offset settings for a given video input
signal. Instead of adjusting just the offset then the gain, both
have to be adjusted interactively until the desired ADC
output is reached.
The ISL98002 simplifies offset and gain adjustment and
completely eliminates offset drift using its Automatic Black
Level Compensation (ABLC™) function. ABLC™ monitors the
black level and continuously adjusts the ISL98002's 10-bit
offset DACs to null out the offset. Any offset, whether due to
the video source or the ISL98002's analog amplifiers, is
eliminated with 10-bit (1/4 of an ADC LSB) accuracy. Any drift
is compensated for well before it can have a visible effect.
Manual offset adjustment control is still available (an 8-bit
register allows the firmware to adjust the offset ±64 codes) in
exactly 1 ADC LSB increments. Gain is now completely
independent of offset (adjusting the gain no longer affects the
offset) so there is no longer a need to program the firmware to
cope with interactive offset and gain controls.
Finally, there should be no concerns over ABLC™ itself
introducing visible artifacts; it doesn't. ABLC™ functions at a
very low frequency, changing the offset in 1/4 LSB
increments, so it can't cause visible brightness fluctuations.
Once ABLC™ is locked, if the offset doesn't drift, the DACs
won't change. If desired, ABLC™ can be disabled, allowing
the firmware to work in the traditional way, with 10-bit offset
DACs under the firmware's control.
Gain and Offset Control
To simplify image optimization algorithms, the ISL98002
features fully-independent gain and offset adjustment.
Changing the gain does not affect the DC offset, and the
weight of an offset DAC LSB does not vary depending on the
gain setting.
The full-scale gain is set in the three 8-bit registers
(0x06-0x08). The ISL98002 can accept input signals with
amplitudes ranging from 0.35VP-P to 1.4VP-P.
The offset controls shift the entire RGB input range, changing
the input image brightness. Three separate registers provide
independent control of the R, G, and B channels. Their
nominal setting is 0x80, which forces the ADC to output code
0x00 (or 0x80 for the R (Pr) and B (Pb) channels in YPbPr
mode) during the back porch period when ABLC™ is enabled.
Functional Description
Inputs
The ISL98002 digitizes analog video inputs in both RGB
and Component (YPbPr) formats, with or without
embedded sync (SOG).
RGB Inputs
For RGB inputs, the black/blank levels are identical and equal
to 0V. The range for each color is typically 0V to 0.7V from
black to white. HSYNC and VSYNC are separate signals.
Component YPbPr Inputs
In addition to RGB and RGB with SOG, the ISL98002 has an
option that is compatible with the component YPbPr video
inputs typically generated by DVD players. While the
ISL98002 digitizes signals in these color spaces, it does not
perform color space conversion; if it digitizes an RGB signal,
it outputs digital RGB, while if it digitizes a YPbPr signal, it
outputs digital YCbCr, also called YUV.
The Luminance (Y) signal is applied to the Green Channel
and is processed in a manner identical to the Green input
with SOG described previously. The color difference signals
Pb and Pr are bipolar and swing both above and below the
black level. When the YPbPr mode is enabled, the black
level output for the color difference channels shifts to a mid
scale value of 0x80. Setting configuration register
0x05[2] = 1 enables the YPbPr signal processing mode of
operation as shown in Table 1.
TABLE 1. YUV MAPPING (4:4:4)
INPUT
SIGNAL
ISL98002
INPUT
CHANNEL
ISL98002
OUTPUT
ASSIGNMENT
OUTPUT
SIGNAL
Y
Green
Green
Y0Y1Y2Y3
Pb
Blue
Blue
U0U1U2U3
Pr
Red
Red
V0V1V2V3
The ISL98002 can optionally decimate the incoming data to
provide a 4:2:2 output stream (configuration register
0x18[4] = 1), as shown in Table 2.
TABLE 2. YUV MAPPING (4:2:2)
INPUT
SIGNAL
ISL98002
INPUT
CHANNEL
ISL98002
OUTPUT
ASSIGNMENT
OUTPUT
SIGNAL
Y
Green
Green
Y0Y1Y2Y3
Pb
Blue
Blue
driven low
Pr
Red
Red
U0V0U2V2
There is also a “compatibility mode” (enabled by setting bit 3
of register 0x18 to a 1) that outputs the U and V data with the
format used by the previous generation (“X980xx”) series of
AFEs, shown in Table 3.
17
FN6535.0
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ISL98002
TABLE 3. YUV MAPPING (4:2:2)
INPUT
SIGNAL
ISL98002
INPUT
CHANNEL
ISL98002
OUTPUT
ASSIGNMENT
OUTPUT
SIGNAL
Y
Green
Green
Y0Y1Y2Y3
Pb
Blue
Blue
driven low
Pr
Red
Red
U0V1U2V3
Input Coupling
Inputs can be either AC-coupled (default) or DC-coupled
(see register 0x05[1]). AC coupling is usually preferred since
it allows video signals with substantial DC offsets to be
accurately digitized. The ISL98002 provides a complete
internal DC-restore function, including the DC restore clamp
(see Figure 5) and programmable clamp timing (registers
0x14, 0x15, 0x16, and 0x23).
When AC-coupled, the DC restore clamp is applied at every
line, a programmable number of pixels after the trailing edge
of HSYNC. If register 0x05[5] = 0 (the default), the clamp will
not be applied while the DPLL is coasting, preventing any
clamp voltage errors from composite sync edges,
equalization pulses, or Macrovision signals.
After the trailing edge of HSYNC, the DC restore clamp is
turned on after the number of pixels specified in the DC
Restore and ABLC™ Starting Pixel registers (0x14 and
0x15) has been reached. The clamp is applied for the
number of pixels specified by the DC Restore Clamp Width
Register (0x16). The clamp can be applied to the back porch
of the video, or to the front porch (by increasing the DC
Restore and ABLC™ Starting Pixel registers so all the active
video pixels are skipped).
If DC-coupled operation is desired, the input to the ADC will
be the difference between the input signal (RIN, for example)
and that channel’s ground reference (RGBGND in that
example).
AUTOMATIC BLACK LEVEL
COMPENSATION (ABLC™) LOOP
DC RESTORATION
CLAMP
GENERATION
DC
RESTORE
CLAMP
DAC
TO ABLC
BLOCK
OFFSET
DAC
FIXED
OFFSET
10
ABLC™
10
OFFSET
CONTROL
REGISTERS
10
0X00
VCLAMP
8
FIXED
OFFSET
ABLC™
8
VIN+
R(GB)IN
R(GB)GND
8
ABLC™
PGA
VIN-
INPUT
BANDWIDTH
8-BIT ADC
8
8
TO OUTPUT
FORMATTER
BANDWIDTH
CONTROL
FIGURE 5. VIDEO FLOW (INCLUDING ABLC™)
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ISL98002
SOG
The ISL98002 has SYNC activity detect functions to help the
firmware determine which sync source is available.
For component YPbPr signals, the sync signal is embedded
on the Y-Channel’s video, which is connected to the green
input, hence the name SOG (Sync on Green). The horizontal
sync information is encoded onto the video input by adding
the sync tip during the blanking interval. The sync tip level is
typically 0.3V below the video black level.
Macrovision
The ISL98002 automatically detects the presence of
Macrovision-encoded video. When Macrovision is detected,
it generates a mask signal that is ANDed with the incoming
SOG CSYNC signal to remove the Macrovision before the
HSYNC goes to the PLL. No additional programming is
required to support Macrovision.
To minimize the loading on the Green channel, the SOG input
for each of the Green channels should be AC-coupled to the
ISL98002 through a series combination of a 10nF capacitor
and a 500Ω resistor. Inside the ISL98002, a window
comparator compares the SOG signal with an internal 4-bit
programmable threshold level reference ranging from 0mV to
300mV below the minimum sync level. The SOG threshold
level, hysteresis, and low-pass filter is programmed via
register 0x04. If the Sync On Green function is not needed,
the SOGIN pin(s) may be left unconnected.
If desired (it is never necessary in normal operation), this
function can be disabled by setting the Sync Mask Disable
(register 0x05 bit 6) to a 1.
The mask signal is also applied to the HSYNCOUT signal.
When Sync Mask Disable = 0, any Macrovision present on
the incoming sync will not be visible on HSYNCOUT. If the
application requires the Macrovision pulses to be visible on
HSYNCOUT, set the HSYNCOUT Mask Disable bit (register
0x05 bit 7).
SYNC Processing
The ISL98002 can process sync signals from 3 different
sources: discrete HSYNC and VSYNC, composite sync on
the HSYNC input, or composite sync from a Sync On Green
(SOG) signal embedded on the Green video input. Due to
the reduced number of pins in the 72 Ld QFN package,
Channel-2 on the ISL98002 only accepts sync input on SOG.
Headswitching from Analog Videotape Signals
Occasionally this AFE may be used to digitize signals
coming from analog videotape sources. The most common
example of this is a Digital VCR (which for best signal quality
would be connected to this AFE with a component YPbPr
ACTIVITY 0X01[6:0]
AND
POLARITY 0X02[5:0]
DETECT
HSYNCOUT
CSYNC
SOURCE
HSYNCIN
SOGIN
HSYNC1
SLICER
0X03[2:0]
HSYNCIN
SOG
SLICER
0X1C
SOGIN
00, 10,
11:
HSYNCIN
SYNC
TYPE
SYNC
SPLITTER
0X05[4:3
]
VSYNC
01:
SOGIN
1:
SYNC
SPLTR
VSYNC OUT
0X05[3]
VSYNCIN
VSYNC IN
0:
VSYNCIN
COAST
GENERATION
0X11, 0X12,
0X13[2]
R[7:0]
PIXEL
DATA FROM
AFE
24
G[7:0]
CLOCKINVIN
PLL
XTALIN
HS
0X0E THROUGH 0X13
PIXCLK
0: ÷1
XTALOUT
0X18,
0X19,
0X1A
B[7:0]
DATACLK
DATACLK
0X13
[6]
÷2
OUTPUT
FORMATTER
HSOUT
1: ÷2
XTALCLOCKOUT
FIGURE 6. SYNC FLOW
19
FN6535.0
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ISL98002
connection). If the digital VCR is playing an older analog
VHS tape, the sync signals from the VCR may contain the
worst of the traditional analog tape artifacts: headswitching.
Headswitching is traditionally the enemy of PLLs with large
capture ranges, because a headswitch can cause the
HSYNC period to change by as much as ±90%. To the PLL,
this can look like a frequency change of -50% to greater than
+900%, causing errors in the output frequency (and
obviously the phase) to change. Subsequent HSYNCs have
the correct, original period, but most analog PLLs will take
dozens of lines to settle back to the correct frequency and
phase after a headswitch disturbance. This causes the top of
the image to “tear” during normal playback. In “trick modes”
(fast forward and rewind), the HSYNC signal has multiple
headswitch-like discontinuities, and many PLLs never settle
to the correct value before the next headswitch, rendering
the image completely unintelligible.
Intersil’s DPLL has the capability to correct large phase
changes almost instantly by maximizing the phase error gain
while keeping the frequency gain relatively low. This is done
by changing the contents of register 0x1C to 0x4C. This
increases the phase error gain to 100%. Because a phase
setting this high will slightly increase jitter, the default setting
(0x49) for register 0x1C is recommended for all other sync
sources.
PGA
The ISL98002’s Programmable Gain Amplifier (PGA) has a
nominal gain range from 0.5V/V (-6dB) to 2.0V/V (+6dB).
The transfer function is calculated in Equation 1:
V
GainCode
Gain ⎛ ----⎞ = 0.5 + ----------------------------⎝ V⎠
170
(EQ. 1)
where GainCode is the value in the Gain register for that
particular color. Note that for a gain of 1V/V, the GainCode
should be 85 (0x55). This is a different center value than the
128 (0x80) value used by some other AFEs, so the firmware
should take this into account when adjusting gains.
The PGAs are updated by the internal clamp signal once per
line. In normal operation, this means that there is a
maximum delay of one HSYNC period between a write to a
Gain register for a particular color and the corresponding
change in that channel’s actual PGA gain. If there is no
regular HSYNC/SOG source, or if the external clamp option
is enabled (register 0x13[5:4]) but there is no external clamp
signal being generated, it may take up to 100ms for a write
to the Gain register to update the PGA. This is not an issue
in normal operation with RGB and YPbPr signals.
Offset DAC
The ISL98002 features a 10-bit Digital-to-Analog Converter
(DAC) per channel to provide extremely fine control over the
full channel offset. The DAC is placed after the PGA to
eliminate interaction between the PGA (controlling
“contrast”) and the Offset DAC (controlling “brightness”).
In normal operation, the Offset DAC is controlled by the
ABLC™ circuit, ensuring that the offset is always reduced
to sub-LSB levels (see “ABLC™” for more information).
When ABLC™ is enabled, the Offset registers (0x09, 0x0A,
0x0B) control a digital offset added to or subtracted from
the output of the ADC. This mode provides the best image
quality and eliminates the need for any offset calibration.
If desired, ABLC™ can be disabled (0x17[0] = 1) and the
Offset DAC programmed manually, with the 8 most
significant bits in registers 0x09, 0x0A, 0x0B, and the 2 least
significant bits in register 0x0C[7:2].
The default Offset DAC range is ±127 ADC LSBs. Setting
0x0C[0] = 1 reduces the swing of the Offset DAC by 50%,
making 1 Offset DAC LSB the weight of 1/8th of an ADC
LSB. This provides the finest offset control and applies to
both ABLC™ and manual modes.
Automatic Black Level Compensation (ABLC™)
ABLC™ is a function that continuously removes all offset
errors from the incoming video signal by monitoring the
offset at the output of the ADC and servoing the 10-bit
analog DAC to force those errors to zero. When ABLC™ is
enabled, the user offset control is a digital adder, with 8-bit
resolution (see Table 4).
When the ABLC™ function is enabled (0x17[0] = 0), the
ABLC function is executed every line after the trailing edge
of HSYNC. If register 0x05[5] = 0 (the default), the ABLC™
function will be not be triggered while the DPLL is coasting,
TABLE 4. OFFSET DAC RANGE AND OFFSET DAC ADJUSTMENT
OFFSET
DAC RANGE
0X0C[0]
10-BIT
OFFSET DAC
RESOLUTION
ABLC™
0x17[0]
USER OFFSET CONTROL RESOLUTION
USING REGISTERS 0x09 - 0X0B ONLY
(8-BIT OFFSET CONTROL)
USER OFFSET CONTROL RESOLUTION
USING REGISTERS 0X09 - 0x0B AND
0X0C[7:2](10-BIT OFFSET CONTROL)
0
0.25 ADC LSBs
(0.68mV)
0
(ABLC on)
1.0 ADC LSB
(digital offset control)
N/A
1
0.125 ADC LSBs
(0.34mV)
0
(ABLC on)
1.0 ADC LSB
(digital offset control)
N/A
0
0.25 ADC LSBs
(0.68mV)
1
(ABLC off)
1.0 ADC LSB
(analog offset control)
0.25 ADC LSB
(analog offset control)
1
0.125 ADC LSBs
(0.34mV)
1
(ABLC off)
0.5 ADC LSB
(analog offset control)
0.125 ADC LSB
(analog offset control)
20
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ISL98002
preventing any composite sync edges, equalization pulses,
or Macrovision signals from corrupting the black data and
potentially adding a small error in the ABLC™ accumulator.
Relative to a 5V input, the hysteresis will be 240mV*5V/3.3V
= 360mV, and the slicer step size will be 400mV*5V/3.3V =
600mV per step.
After the trailing edge of HSYNC, the start of ABLC™ is
delayed by the number of pixels specified in registers 0x14
and 0x15. After that delay, the number of pixels specified
by register 0x17[3:2] are averaged together and added to
the ABLC™’s accumulator. The accumulator stores the
average black levels for the number of lines specified by
register 0x17[6:4], which is then used to generate a 10-bit
DAC value.
SOG Slicer
The default values provide excellent results with offset
stability and absolute accuracy better than 1 ADC LSB for
most input signals.
SYNC Status and Polarity Detection
ADC
The ISL98002 features 3 fully differential, high-speed 8-bit
ADCs.
Clock Generation
A Digital Phase Lock Loop (DPLL) is employed to generate
the pixel clock frequency. The HSYNC input and the external
XTAL provide a reference frequency to the PLL. The PLL
then generates the pixel clock frequency that is equal to the
incoming HSYNC frequency times the HTOTAL value
programmed into registers 0x0E and 0x0F.
The stability of the clock is very important and correlates
directly with the quality of the image. During each pixel time
transition, there is a small window where the signal is
slewing from the old pixel amplitude and settling to the new
pixel value. At higher frequencies, the pixel signal transitions
at a faster rate, which makes the stable pixel time even
smaller. Any jitter in the pixel clock reduces the effective
stable pixel time and thus the sample window in which pixel
sampling can be made accurately.
Sampling Phase
The ISL98002 provides 64 low-jitter phase choices per pixel
period, allowing the firmware to precisely select the optimum
sampling point. The sampling phase register is 0x10.
HSYNC Slicer
To further minimize jitter, the HSYNC inputs are treated as
analog signals, and brought into a precision slicer block with
thresholds programmable in 400mV steps with 240mV of
hysteresis, and a subsequent digital glitch filter that ignores
any HSYNC transitions within 100ns of the initial transition.
This processing greatly increases the AFE’s rejection of
ringing and reflections on the HSYNC line and allows the
AFE to perform well, even with pathological HSYNC signals.
Voltages given previously and in the “HSYNC Slicer” on
page 21 (register description), are with respect to a 3.3V
sync signal at the HSYNCIN input pin. To achieve 5V
compatibility, a 680Ω series resistor should be placed
between the HSYNC source and the HSYNCIN input pin.
21
The SOG input has programmable threshold, 40mV of
hysteresis, and an optional low pass filter that can be used to
remove high frequency video spikes (generated by
overzealous video peaking in a DVD player, for example)
that can cause false SOG triggers. The SOG threshold sets
the comparator threshold relative to the sync tip (the bottom
of the SOG pulse).
The SYNC Status register (0x01) and the SYNC Polarity
register (0x02) continuously monitor all 3 sync inputs
(VSYNCIN, HSYNCIN, and SOGIN) and report their status.
However, accurate sync activity detection is always a
challenge. Noise and repetitive video patterns on the Green
channel may look like SOG activity when there actually is no
SOG signal, while non-standard SOG signals and trilevel
sync signals may have amplitudes below the default SOG
slicer levels and not be easily detected. As a consequence,
not all of the activity detect bits in the ISL98002 are correct
under all conditions.
Table 5 on page 22 shows how to use the SYNC Status
register (0x01) to identify the presence and type of sync
source. The firmware should go through the table in the
order shown, stopping at the first entry that matches the
activity indicators in the SYNC Status register.
Final validation of composite sync sources (SOG or
Composite sync on HSYNC) should be done by setting the
Input Configuration register (0x05) to the composite sync
source determined by Table 5, and confirming that the
CSYNC detect bit is set.
The accuracy of the Trilevel Sync Detect bit can be
increased by multiple reads of the Trilevel Sync detect bit.
See “TriLevel Sync Detect” on page 22 for more details.
For best SOG operation, the SOG low pass filter (register
0x04[4] should always be enabled to reject the high
frequency peaking often seen on video signals.
HSYNC and VSYNC Activity Detect
Activity on these bits always indicates valid sync pulses, so
they should have the highest priority and be used even if the
SOG activity bit is also set.
SOG Activity Detect
The SOG Activity Detect bit monitors the output of the SOG
slicer, looking for 64 consecutive pulses with the same
period and duty cycle. If there is no signal on the Green
(or Y) channel, the SOG slicer will clamp the video to a DC
level and will reject any sporadic noise. There should be no
false positive SOG detects if there is no video on Green
(or Y-Channel).
FN6535.0
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ISL98002
If there is video on Green (or Y-Channel) with no valid SOG
signal, the SOG activity detect bit may sometimes report
false positives (it will detect SOG when no SOG is actually
present). This is due to the presence of video with a
repetitive pattern that creates a waveform similar to SOG.
For example, the desktop of a PC operating system is black
during the front porch, horizontal sync, and back porch, then
increases to a larger value for the video portion of the
screen. This creates a repetitive video waveform very similar
to SOG that may falsely trigger the SOG Activity detect bit.
However, in these cases where there is active video without
SOG, the SYNC information will be provided either as
separate H and V sync on HSYNCIN and VSYNCIN, or
composite sync on HSYNCIN. HSYNCIN and VSYNCIN
should therefore be used to qualify SOG. The SOG Active bit
should only be considered valid if HSYNC Activity
Detect = 0. Note: Some pattern generators can output
HSYNC and SOG simultaneously, in which case both the
HSYNC and the SOG activity bits will be set, and valid. Even
in this case, however, the monitor should still choose
HSYNC over SOG.
TriLevel Sync Detect
Unlike SOG detect, the TriLevel Sync Detect function does
not check for 64 consecutive trilevel pulses in a row, and is
therefore less robust than the SOG detect function. It will
report false positives for SOG-less video for the same
reasons the SOG activity detect does, and should therefore
be qualified with both HSYNC and SOG. TriLevel Sync
Detect should only be considered valid if HSYNC Activity
Detect = 0 and SOG Activity Detect = 1.
If there is a SOG signal, the TriLevel Detect bit will operate
correctly for standard trilevel sync levels (600mVP-P). In
some real-world situations, the peak-to-peak sync amplitude
may be significantly smaller, sometimes 300mVp-p or less.
In these cases the sync slicer will continue to operate
correctly, but the TriLevel Detect bit may not be set. Trilevel
detection accuracy can be enhanced by polling the trilevel
bit multiple times. If HSYNC is inactive, SOG is present, and
the TriLevel Sync Detect bit is read as a 1, there is a high
likelihood there is trilevel sync.
TABLE 5. SYNC SOURCE DETECTION TABLE
HSYNC
DETECT
VSYNC
DETECT
SOG
DETECT
TRILEVEL
DETECT
1
1
X
X
Sync is on HSYNC and VSYNC
1
0
X
X
Sync is composite sync on HSYNC. Set Input configuration register to CSYNC on
HSYNC and confirm that CSYNC detect bit is set.
0
0
1
0
Sync is composite sync on SOG. It is possible that trilevel sync is present but amplitude
is too low to set TriLevel Detect bit. Use video mode table to determine if this video
mode is likely to have TriLevel sync, and set clamp start, width values appropriately if
it is.
0
0
1
1
Sync is composite sync on SOG. Sync is likely to be trilevel.
0
0
0
X
No valid sync sources on any input.
22
RESULT
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March 26, 2008
ISL98002
CSYNC Present
HSOUT
If a composite sync source (either CSYNC on HSYNC or
SOG) is selected through bits 3 and 4 of register 0x05, the
CSYNC Present bit in register 0x01 should be set. CSYNC
Present detects the presence of a low frequency, repetitive
signal inside HSYNC, which indicates a VSYNC signal. The
CSYNC Present bit should be used to confirm that the signal
being received is a reliable composite sync source.
HSOUT is generated by the ISL98002’s control logic and is
synchronized to the output DATACLK and the digital pixel
data on the output databus. Its trailing edge is aligned with
pixel 0. Its width, in units of pixels, is determined by register
0x19, and its polarity is determined by register 0x18[7]. As
the width is increased, the trailing edge stays aligned with
pixel 0, while the leading edge is moved backwards in time
relative to pixel 0. HSOUT is used by the scaler to signal the
start of a new line of pixels.
SYNC Output Signals
The ISL98002 has 2 types of SYNC signals, HSYNCOUT
and VSYNCOUT, and HSOUT.
HSYNCOUT and VSYNCOUT are buffered versions of the
incoming sync signals; no synchronization is done. These
signals are used for mode detection.
HSOUT is generated by the ISL98002’s logic and is
synchronized to the output DATACLK and the digital pixel
data on the output databus. HSOUT is used to signal the start
of a new line of digital data.
Both HSYNCOUT and VSYNCOUT (including the sync
separator function) remain active in power-down mode. This
allows them to be used in conjunction with the Sync Status
registers to detect valid video without powering up the
ISL98002.
HSYNCOUT
HSYNCOUT is an unmodified, buffered version of the incoming
HSYNCIN or SOGIN signal of the selected channel, with the
incoming signal’s period, polarity, and width to aid in mode
detection. HSYNCOUT will be the same format as the incoming
sync signal: either horizontal or composite sync. If a SOG input
is selected, HSYNCOUT will output the entire SOG signal,
including the VSYNC portion, pre- and post-equalization pulses
if present, and Macrovision pulses if present. HSYNCOUT
remains active when the ISL98002 is in power-down mode.
HSYNCOUT is generally used for mode detection.
VSYNCOUT
VSYNCOUT is an unmodified, buffered version of the
incoming VSYNCIN signal of the selected channel, with the
original VSYNC period, polarity, and width to aid in mode
detection. If a SOG input is selected, this signal will output
the VSYNC signal extracted by the ISL98002’s sync slicer.
Extracted VSYNC will be the width of the embedded VSYNC
pulse plus pre- and post-equalization pulses (if present).
Macrovision pulses from an NTSC DVD source will lengthen
the width of the VSYNC pulse. Macrovision pulses from
other sources (PAL DVD or videotape) may appear as a
second VSYNC pulse encompassing the width of the
Macrovision. See the “Macrovision” on page 19 for more
information. VSYNCOUT (including the sync separator
function) remains active in power-down mode. VSYNCOUT
is generally used for mode detection, start of field detection,
and even/odd field detection.
23
The HSOUT Width register (0x19) controls the width of the
HSOUT pulse. The pulse width is nominally 1 pixel clock
period times the value in this register.
Crystal Oscillator
An external 22MHz to 27MHz crystal supplies the low-jitter
reference clock to the DPLL. The absolute frequency of this
crystal within this range is unimportant, as is the crystal’s
temperature coefficient, allowing use of less expensive,
lower-grade crystals.
As an alternative to a crystal, the XTALIN pin can be driven
with a 3.3V CMOS-level external clock source at any
frequency between 22MHz and 33.5MHz. The ISL98002’s
jitter specification assumes a low-jitter crystal source. If the
external clock source has increased jitter, the sample clock
generated by the DPLL may exhibit increased jitter as well.
EMI Considerations
There are two possible sources of EMI on the ISL98002 as
explained in the following::
Crystal Oscillator - The EMI from the crystal oscillator is
negligible. This is due to an amplitude-regulated, low voltage
sine wave oscillator circuit, instead of the typical high-gain
square wave inverter-type oscillator, so there are no harmonics.
Note: The crystal oscillator is not a significant source of EMI.
Digital Output Switching - This is the largest potential source
of EMI. However, the EMI is determined by the PCB layout and
the loading on the databus. The way to control this is to put
series resistors on the output of all the digital pins (as our demo
board and reference circuits show). These resistors should be
as large as possible, while still meeting the setup and hold
timing requirements of the scaler. We recommend starting with
22Ω. If the databus is heavily loaded (long traces, many other
part on the same bus), this value may need to be reduced. If
the databus is lightly loaded, it may be increased.
Intersil’s recommendations to minimize EMI are:
• Minimize the databus trace length
• Minimize the databus capacitive loading.
If EMI is a problem in the final design, increase the value of the
digital output series resistors to reduce slew rates on the bus.
This can only be done as long as the scaler’s setup and hold
timing requirements continue to be met.
FN6535.0
March 26, 2008
ISL98002
Reducing Power Dissipation
Communication is accomplished in three steps:
It is possible to reduce the total power consumption of the
ISL98002 in applications where power is a concern. There are
several techniques that can be used to reduce power
consumption:
1. The Host selects the ISL98002 it wishes to communicate
with.
• Buffering Digital Outputs. Switching data output pins into a
capacitive bus can consume significant current. The higher
the capacitance on the external databus, the higher the
switching current. To minimize current consumption inside
the ISL98002, minimize bus capacitance and/or insert data
buffers such as the SN64AVC16827 between the ISL98002’s
data outputs and the external databus.
3. The Host writes to or reads from the ISL98002’s
Configuration Register. The ISL98002’s internal address
pointer auto increments, so to read registers 0x00
through 0x1B, for example, one would write 0x00 in
Step 2, then repeat Step 3 28x, with each read returning
the next register value.
• Internal Reference Frequency. The crystal frequency is
multiplied by the value in register 0x2B to generate an
internal high frequency reference clock. This internal
frequency should be set to 400MHz ±10% for minimum
power consumption. For example, for a 33MHz frequency at
XTALIN, register 0x2B should be set to a value of 0x0C to
minimize power.
Standby Mode
The ISL98002 can be placed into a low power standby mode
by writing a 0x0F to register 0x1B, powering down the triple
ADCs, the DPLL, and most of the internal clocks.
To allow input monitoring and mode detection during
power-down, the following blocks remain active:
• Serial interface (including the crystal oscillator) to enable
register read/write activity
• Activity and polarity detect functions (registers 0x01 and
0x02)
• The HSYNCOUT and VSYNCOUT pins (for mode
detection)
Initialization
The ISL98002 initializes with default register settings for an
AC-coupled, RGB input.
Reset
The ISL98002 has a Power-On Reset (POR) function that
resets the chip to its default state when power is initially
applied, including resetting all the registers to their default
settings as described in the “Register Listing” beginning on
page 10. The external RESET pin duplicates the reset
function of the POR without having to cycle the power
supplies. The RESET pin does not need to be used in
normal operation and can be tied high.
2. The Host writes the initial ISL98002 Configuration
Register address it wishes to write to or read from.
The ISL98002 has a 7-bit address on the serial bus. The
upper 6-bits are permanently set to 100110, with the lower
bit determined by the state of pin 29. This allows two
ISL98002s to be independently controlled while sharing the
same bus.
The bus is nominally inactive, with SDA and SCL high.
Communication begins when the host issues a START
command by taking SDA low while SCL is high
(see Figure 7). The ISL98002 continuously monitors the
SDA and SCL lines for the start condition and will not
respond to any command until this condition has been met.
The host then transmits the 7-bit serial address plus a R/W
bit, indicating if the next transaction will be a Read (R/W = 1)
or a Write (R/W = 0). If the address transmitted matches that
of any device on the bus, that device must respond with an
ACKNOWLEDGE (see Figure 8).
Once the serial address has been transmitted and
acknowledged, one or more bytes of information can be
written to or read from the slave. Communication with the
selected device in the selected direction (read or write) is
ended by a STOP command, where SDA rises while SCL is
high (see Figure 7), or a second START command, which is
commonly used to reverse data direction without
relinquishing the bus.
Data on the serial bus must be valid for the entire time SCL
is high (see Figure 9). To achieve this, data being written to
the ISL98002 is latched on a delayed version of the rising
edge of SCL. SCL is delayed and deglitched inside the
ISL98002 for three crystal clock periods (120ns for a 25MHz
crystal) to eliminate spurious clock pulses that could disrupt
serial communication.
When the contents of the ISL98002 are being read, the SDA
line is updated after the falling edge of SCL, delayed and
deglitched in the same manner.
ISL98002 Serial Communication
Configuration Register Write
Overview
Figure 10 shows two views of the steps necessary to write
one or more words to the Configuration Register.
The ISL98002 uses a 2-wire serial bus for communication
with its host. SCL is the Serial Clock line, driven by the host,
and SDA is the Serial Data line, which can be driven by all
devices on the bus. SDA is open drain to allow multiple
devices to share the same bus simultaneously.
24
Configuration Register Read
Figure 11 shows two views of the steps necessary to read
one or more words from the Configuration Register.
FN6535.0
March 26, 2008
ISL98002
SCL
SDA
START
STOP
FIGURE 7. VALID START AND STOP CONDITIONS
SCL FROM
HOST
1
8
9
DATA OUTPUT
FROM TRANSMITTER
DATA OUTPUT
FROM RECEIVER
START
ACKNOWLEDGE
FIGURE 8. ACKNOWLEDGE RESPONSE FROM RECEIVER
SCL
SDA
DATA STABLE
DATA CHANGE
DATA STABLE
FIGURE 9. VALID DATA CHANGES ON THE SDA BUS
25
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March 26, 2008
ISL98002
Signals the beginning of serial I/O
START Command
ISL98002 Serial Bus
R/W
A
0
ISL98002 Serial Bus Address Write
This is the 7-bit address of the ISL98002 on the 2-wire bus. The
address is 0x4C if pin 29 is low, 0x4D if pin 29 is high. Shift this
value left to when adding the R/W bit.
0
1
0
0
1
1
A7
A6
A5
A4
A3
A2
A1
A0
D7
D6
D5
D4
D3
D2
D1
D0
(pin 29)
ISL98002 Register Address Write
This is the address of the ISL98002’s configuration register that
the following byte will be written to.
ISL98002 Register Data Write(s)
This is the data to be written to the ISL98002’s configuration register.
Note: The ISL98002’s Configuration Register’s address pointer auto
increments after each data write: repeat this step to write multiple
sequential bytes of data to the Configuration Register.
(Repeat if desired)
Signals the ending of serial I/O
STOP Command
Signals from
the Host
SDA Bus
Signals from
the ISL98002
S
T Serial Bus
A
R Address
T
Register
Address
aaaaaaaa
1 0 0 1 1 0A0
A
C
K
S
T
O
P
Data
Write*
* The data write step may be repeated to write to the
ISL98002’s Configuration Register sequentially, beginning at
the Register Address written in the previous step.
dddddddd
A
C
K
A
C
K
FIGURE 10. CONFIGURATION REGISTER WRITE
26
FN6535.0
March 26, 2008
ISL98002
Signals the beginning of serial I/O
START Command
ISL98002 Serial Bus
R/W
A
0
1
0
0
1
1
A7
A6
A5
A4
A3
0
(pin 29)
ISL98002 Serial Bus Address Write
This is the 7-bit address of the ISL98002 on the 2-wire bus. The
address is 0x4C if pin 29 is low, 0x4D if pin 29 is high. R/W = 0,
indicating next transaction will be a write.
ISL98002 Register Address Write
A2
A1
A0
START Command
ISL98002 Serial Bus
R/W
A
0
1
0
0
1
1
D7
D6
D5
D4
D3
1
(pin 29)
D2
D1
D0
SDA Bus
Signals from
the ISL98002
R
E
S
T Serial Bus
A Address
R
T
1 0 0 1 1 0A1
Register
Address
1 0 0 1 1 0A0
aaaaaaaa
A
C
K
ISL98002 Register Data Read(s)
This is the data read from the ISL98002’s configuration register.
Signals the ending of serial I/O
STOP Command
S
T Serial Bus
A
R Address
T
ISL98002 Serial Bus Address Write
This is the 7-bit address of the ISL98002 on the 2-wire bus. The
address is 0x4C if pin 29 is low, 0x4D if pin 29 is high. R/W = 1,
indicating next transaction(s) will be a read.
Note: The ISL98002’s Configuration Register’s address pointer
auto increments after each data read: repeat this step to read
multiple sequential bytes of data from the Configuration Register.
(Repeat if desired)
Signals from
the Host
This sets the initial address of the ISL98002’s configuration
register for subsequent reading.
Ends the previous transaction and starts a new one
A
C
K
Data
Read*
S
T
O
AP
C
K
* The data read step may be repeated to read
from the ISL98002’s Configuration Register
sequentially, beginning at the Register
Address written in the previous two steps.
Adddddddd
C
K
FIGURE 11. CONFIGURATION REGISTER READ
27
FN6535.0
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ISL98002
Quad Flat No-Lead Plastic Package (QFN)
Micro Lead Frame Plastic Package (MLFP)
L72.10x10
72 LEAD QUAD FLAT NO-LEAD PLASTIC PACKAGE
MILLIMETERS
SYMBOL
MIN
NOMINAL
MAX
NOTES
A
0.80
0.90
1.00
-
A1
-
0.02
0.05
-
A2
-
0.65
1.00
9
0.30
5, 8
A3
b
0.20 REF
0.18
0.25
9
D
10.00 BSC
-
D1
9.75 BSC
9
D2
5.85
E
E1
E2
6.00
6.15
7, 8
10.00 BSC
-
9.75 BSC
5.85
e
6.00
9
6.15
7, 8
0.50 BSC
-
k
0.20
-
-
-
L
0.30
0.40
0.50
8, 10
N
72
2
Nd
18
3
Ne
18
3
P
-
-
0.60
9
θ
-
-
12
9
Rev. 1 11/04
NOTES:
1. Dimensioning and tolerancing conform to ASME Y14.5-1994.
2. N is the number of terminals.
3. Nd and Ne refer to the number of terminals on each D and E.
4. All dimensions are in millimeters. Angles are in degrees.
5. Dimension b applies to the metallized terminal and is measured
between 0.15mm and 0.30mm from the terminal tip.
6. The configuration of the pin #1 identifier is optional, but must be
located within the zone indicated. The pin #1 identifier may be
either a mold or mark feature.
7. Dimensions D2 and E2 are for the exposed pads which provide
improved electrical and thermal performance.
8. Nominal dimensions are provided to assist with PCB Land Pattern
Design efforts, see Intersil Technical Brief TB389.
9. Features and dimensions A2, A3, D1, E1, P & θ are present when
Anvil singulation method is used and not present for saw
singulation.
10. Compliant to JEDEC MO-220VNND-3 except for the "L" min
dimension.
All Intersil U.S. products are manufactured, assembled and tested utilizing ISO9000 quality systems.
Intersil Corporation’s quality certifications can be viewed at www.intersil.com/design/quality
Intersil products are sold by description only. Intersil Corporation reserves the right to make changes in circuit design, software and/or specifications at any time without
notice. Accordingly, the reader is cautioned to verify that data sheets are current before placing orders. Information furnished by Intersil is believed to be accurate and
reliable. However, no responsibility is assumed by Intersil or its subsidiaries for its use; nor for any infringements of patents or other rights of third parties which may result
from its use. No license is granted by implication or otherwise under any patent or patent rights of Intersil or its subsidiaries.
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28
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