Datasheet UM1665 Rev05

UM1665
Low Power DC/DC Boost Converter
UM1665S SOT23-5
UM1665DA TDFN6 3.0×3.0
General Description
The UM1665 is a PFM controlled step-up DC-DC converter with a switching frequency up to
1MHz. The device is ideal to generate output voltage for small to medium LCD bias supplies and
white LED backlight supplies from a single cell Li-ion battery. The part can also be used to
generate standard 3.3V/5V to 12V power conversions.
With a high switching frequency of 1MHz, a low profile and small board area solution can be
achieved using a chip coil and an ultra small ceramic output capacitor. The UM1665 has an
internal 400mA switch current limit, offering lower output voltage ripple. The low quiescent
current (typically 36µA) together with an optimized control scheme, allows device operation at
very high efficiencies over the entire load current range.
The UM1665 is available in SOT23-5 and TDFN6 3.0×3.0 with only 0.60mm (TYP) thickness
packages. The UM1665 is appropriate to be applied in small electronic equipments and wearable
devices.
Applications
Features














LCD Bias Supply
White LED Supply for LCD Backlights
Digital Still Cameras
PDAs, Organizers and Handheld PCs
Cellular Phones
Standard 3.3V/5V to 12V Conversion
Pin Configurations
2.0V to 6.0V Input Voltage Range
Adjustable Output Voltage up to 28V
400mA Internal Switch Current
Up to 1MHz Switching Frequency
36µA Typical No Load Quiescent Current
1µA Maximum Shutdown Current
Internal Soft-Start
Available in Tiny SOT23-5 and Thin DFN6
3.0×3.0 with 0.60mm (TYP) Thickness
Packages
Top View
5
1
GND
2
FB
3
5
VIN
PHO
1
4
EN
M
SW
4
2
3
M: Month Code
UM1665S
SOT23-5
(Top View)
VIN
1
6
SW
GND
2
5
NC
EN
3
4
FB
1665
XX
XX: Week Code
UM1665DA
TDFN6 3.0×3.0
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UM1665
Ordering Information
Part Number
Packaging Type
Marking Code
UM1665S
SOT23-5
PHO
UM1665DA
TDFN6 3.0×3.0
1665
Shipping Qty
3000pcs/7 Inch
Tape & Reel
3000pcs/13 Inch
Tape & Reel
Pin Description
Pin Number
Symbol
Function
UM1665S
UM1665DA
1
6
SW
2
2
GND
3
4
FB
4
3
EN
5
1
VIN
Connect the inductor and the Schottky diode to this pin.
This is the switch pin and is connected to the drain of the
internal power MOSFET.
Ground
This is the feedback pin of the device. Connect this pin to
the external voltage divider to program the desired output
voltage.
This is the enable pin of the device. Pulling this pin to
ground forces the device into shutdown mode reducing the
supply current to less than 1µA. This pin should not be left
floating and needs to be terminated.
Supply Voltage Pin
-
5
NC
Not Connected
Absolute Maximum Ratings
Over operating free-air temperature (unless otherwise noted) (Note 1)
Symbol
VIN
VFB, VEN
VSW
Parameter
Supply Voltage on VIN (Note 2)
Voltages on FB, EN (Note 2)
Switch Voltage on SW (Note 2)
PD
Continuous Power Dissipation SOT23-5
at TA=25°C
TDFN6 3.0×3.0
TJ
Operating Junction Temperature
Value
Unit
-0.3 to +7.0
V
-0.3 to VIN+0.3
V
30
V
0.35
1.4
-40 to +150
W
°C
TSTG
Storage Temperature Range
-65 to +150
°C
Maximum Lead Temperature for Soldering 10
TL
+260
°C
Seconds
Note 1: Stresses beyond those listed under absolute maximum ratings may cause permanent
damage to the device. These are stress ratings only, and functional operation of the
device at these or any other conditions beyond those indicated under recommended
operating conditions is not implied. Exposure to absolute-maximum-rated conditions for
extended periods may affect device reliability.
Note 2: All voltage values are with respect to network ground terminal.
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UM1665
Recommended Operating Conditions
Symbol
Parameter
VIN
Input Voltage Range
VOUT
Output Voltage Range
L
Inductor (Note 3)
f
Switching Frequency (Note 3)
CIN
Input Capacitor (Note 3)
COUT
Output Capacitor (Note 3)
TA
Operating Ambient Temperature
TJ
Operating Junction Temperature
Note 3: Refer to application section for further information.
Min
2.0
Typ
2.2
10
Max
6.0
28
22
1
4.7
1
-40
-40
85
125
Unit
V
V
μH
MHz
μF
μF
°C
°C
Function Block Diagram
SW
Under Voltage
Lockout
Bias Supply
VIN
400ns Min
Off Time
Error Comparator
-
FB
S
+
RS Latch
Logic
VREF=1.233V
Power MOSFET
N-Channel
Gate
Driver
R
Current Limit
+
EN
-
6μs Max
On Time
RSENSE
Soft Start
GND
Figure 1. UM1665 Function Block Diagram
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UM1665
Electrical Characteristics
(VIN=2.4V, EN=VIN, CIN=4.7μF, COUT=1μF, L=10μH, TA=-40°C to 85°C, typical values are at
TA=25°C, unless otherwise noted)
Symbol
Parameter
SUPPLY CURRENT
VIN
Input Voltage Range
IQ
ISD
VUVLO
Operating Quiescent
Current
Shutdown Current
Under-Voltage
Lockout Threshold
Test Conditions
Min
Typ
Max
Unit
6.0
V
36
70
μA
0.1
1
μA
1.5
1.8
V
2.0
IOUT=0mA,
not switching,
VFB=1.3V
EN=GND
ENABLE
EN High Level Input
1.3
Voltage
EN Low Level Input
VIL
0.4
Voltage
EN Input Leakage
IL
EN=GND or VIN
0.1
1
Current
POWER SWITCH AND CURRENT LIMIT
Maximum Switch
VSW
28
Voltage
tON
Maximum On Time
4
6
7.5
tOFF
Minimum Off Time
250
400
550
MOSFET On
RDS(ON)
VIN=2.4V, ISW=50mA
750
1200
Resistance
MOSFET Leakage
VSW=28V
1
10
Current
MOSFET Current
ILIM
350
400
500
Limit
OUTPUT
Adjustable Output
VOUT
VIN
28
Voltage Range
Internal Voltage
VREF
1.233
Reference
Feedback Input Bias
IFB
VFB=1.3V
1
Current
Feedback Trip Point
VFB
2.0V≤VIN≤6.0V
1.196 1.233 1.270
Voltage
2.0V≤VIN≤6.0V,
Line Regulation
VOUT=18V,
0.05
(Note 4)
ILOAD=10mA
VIN=2.4V,
Load Regulation
VOUT=18V,
0.15
(Note 4)
0mA<IOUT<25mA
Note 4: The line and load regulation depend on the external component selection.
VIH
V
V
μA
V
μs
ns
mΩ
μA
mA
V
V
μA
V
%/V
%/mA
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UM1665
Operation
The UM1665 features a constant off-time control scheme. Operation can be best understood by
referring to the function block diagram. The converter monitors the output voltage, and as soon as
the feedback voltage falls below the reference voltage of typically 1.233V, the internal switch
turns on and the current ramps up. The switch turns off as soon as the inductor current reaches the
internally set peak current of typically 400mA. The second criteria that turns off the switch is the
maximum on-time of 6µs (typical). This is just to limit the maximum on-time of the converter to
cover for extreme conditions. As the switch is turned off the external Schottky diode is forward
biased delivering the current to the output. The switch remains off for a minimum of 400ns
(typical), or until the feedback voltage drops below the reference voltage again. Using this PFM
peak current control scheme the converter operates in discontinuous conduction mode (DCM)
where the switching frequency depends on the output current, which results in very high
efficiency over the entire load current range.
Peak Current Control
The internal switch turns on until the inductor current reaches the typical dc current limit (ILIM) of
400mA. There is approximately a 100ns delay from the time the current limit is reached and when
the internal logic actually turns off the switch. During this 100ns delay, the peak inductor current
will increase. This increase demands a larger saturation current rating for the inductor. This
saturation current can be approximated by the following equation:
V
I P EAK( TYP)  I LIM  IN 100 ns
L
It means higher input voltage and lower inductor value lead to greater SW peak current.
Soft-Start
All inductive step-up converters exhibit high inrush current during start-up if no special
precaution is made. This can cause voltage drops at the input rail during start up and may result in
an unwanted or early system shut down. The UM1665 limits this inrush current by increasing the
current limit in two steps from ILIM/4 for 256 cycles to ILIM/2 for the next 256 cycles, and then full
current limit.
Enable
Pulling the enable pin (EN) to ground shuts down the device reducing the shutdown current to
1µA (typical). Since there is a conductive path from the input to the output through the inductor
and Schottky diode, the output voltage is equal to the input voltage during shutdown. The enable
pin needs to be terminated and should not be left floating. Using a small external transistor
disconnects the input from the output during shutdown as shown in the figure below.
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UM1665
R3
47k
L1
10µH
VIN=2.0-6.0V
SW
VIN
C1
4.7µF
EN
R1
2.2M
C2
1µF
UM1665
GPIO
VOUT
18V/10mA
D1
CFF
22pF
FB
GND
C2
0.1µF
(Optional)
R2
160k
Figure 2. Disconnect the Input from the Output during Shutdown Using External Transistor
Under-Voltage Lockout
An under-voltage lockout prevents misoperation of the device at input voltages below typical 1.5V.
When the input voltage is below the under-voltage threshold the main switch is turned off.
Typical Application Circuit
L1
10µH
VIN=2.0-6.0V
VIN
VOUT
D1
SW
R1
CIN
4.7µF
CFF
UM1665
EN
COUT
1µF
FB
GND
R2
Figure 3. Standard DC/DC Boost Supply
The output voltage is calculated as:
VOUT  1.233  (1 
R1
)
R2
We can use a PWM signal on the enable pin of UM1665 to adjust the white LED brightness (see
figure 4 below). When adding the PWM signal to EN pin, the UM1665 is turned on or off by the
PWM signal, so the LEDs operate at either zero or full current. The average LED current
increases proportionally with the duty cycle of the PWM signal. The magnitude of the PWM
signal should be higher than the minimum enable voltage of EN pin (1.3V) and lower than VIN, in
order to let the dimming control perform correctly. The frequency range of the PWM signal is
from 50Hz to 10 kHz.
Actually, the number of LEDs driven by using the UM1665 is closely related with several factors,
such as the input voltage (VIN), LED characteristics and the value of the inductor. For example, if
L=10μH, the maximum current of WLED is 20mA and VF=3.2V, then when VIN=2V, the UM1665
can drive at most 4WLEDs, and when VIN=3V, the number of WLEDs driven by the UM1665
turns out to be up to 6.
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UM1665
L1
10µH
VIN=2.0-6.0V
CIN
4.7µF
D1
SW
VIN
COUT
1µF
D2
30V
(Optional)
UM1665
PWM
FB
EN
50 Hz to 10kHz
RS
82Ω
GND
Figure 4. White LED Supply with Adjustable Brightness Control
Using a PWM Signal on the Enable Pin
We also can adjust the white LED brightness using an analog signal on the feedback pin (see
figure 5 below). Add a DC voltage to the FB pin, and adjust the LED current by change the DC
voltage, which control the brightness. The LED current is calculated as:
I RS 
VFB R1  R 2   VADJ R1
R S R 2
L1
10µH
VIN=2.0-6.0V
D1
VIN
CIN
4.7µF
SW
UM1665
FB
EN
D2
30V
(Optional )
COUT*
100nF
VFB
R1
GND
Rs
VADJ
R2
*A smaller output capacitor value for COUT causes a larger LED ripple.
Figure 5. White LED Supply with Adjustable Brightness Control
Using an Analog Signal on the Feedback Pin
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UM1665
Typical Operating Characteristics
(CIN=4.7μF, COUT=1μF, L=10μH, TA=25°C, unless otherwise noted)
Efficiency vs. Output Current
100%
90%
90%
80%
80%
70%
70%
Efficiency (%)
Efficiency (%)
Efficiency vs. Output Current
100%
60%
50%
60%
50%
40%
40%
30%
VOUT=18V, L=10μH
20%
VINVIN=5.0V
=5.0V
30%
VINVIN=3.7V
=3.7V
VINVIN=2.4V
=2.4V
20%
10%
L=10μH
L=10uH
L=3.3μH
L=3.3uH
VIN=3.7V, VOUT=18V
10%
0.1
1
10
100
0.1
1
Output Current (mA)
10
100
Output Current (mA)
Efficiency vs. Input Voltage
Quiescent Current vs. Input Voltage
50
90%
45
Quiescent Current (uA)
Efficiency (%)
85%
80%
75%
70%
Io=10mA
IOUT=10mA
IOUT=5mA
Io=5mA
VOUT=18V, L=10μH
65%
40
35
30
25
20
15
TATA=-30℃
= -30°C
TATA=25℃
=+25°C
TA=+85°C
TA=85℃
10
5
0
60%
1
2
3
4
5
1
6
2
3
4
5
6
Input Voltage (V)
Input Voltage (V)
Feedback Voltage vs. Temperature
Switch Current Limit vs. Temperature
430
1.28
410
1.27
390
Switch Current Limit (mA)
Feedback Voltage (V)
1.26
1.25
1.24
1.23
VINVIN=2.4V
=2.4V
VINVIN=3.6V
=3.6V
VINVIN=5.0V
=5.0V
1.22
1.21
-20
0
20
40
Temperature (℃)
60
80
350
330
310
290
270
250
1.2
-40
370
100
230
-40
VIN=5.0V
-20
0
20
40
60
80
100
Tem perature (℃)
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UM1665
Typical Operating Characteristics (Continued)
(CIN=4.7μF, COUT=1μF, L=10μH, TA=25°C, unless otherwise noted)
Output
vs.
Temperature
OutputVoltage
Voltage vs
Temperature
RDS(ON) vs. Temperature
Static Drain-Source on-state Resistance (mΩ)
19.00
18.80
Output Voltage (V)
18.60
18.40
18.20
18.00
17.80
17.60
VIN=5.0V,
IOUT=10mA
17.40
17.20
17.00
-40
-20
0
20
40
60
80
100
1100
1000
900
800
700
600
500
VIN=3.6V
400
300
-40
-20
0
Temperature(℃)
40
60
80
100
Temperature (℃)
RDS(ON) vs. Input Voltage
Static Drain-Source on-state Resistance (mΩ)
20
Line Transient Response
1100
VIN=2.4V to 3.4V
1000
900
800
700
VOUT 100mV/div
600
500
400
200μs/div
300
1
2
3
4
5
VOUT=18V,
IOUT=10mA
6
Input Voltage (V)
Load Transient Response
Start-up Behavior
IOUT=1mA to 10mA
VOUT 5V/div
VOUT 100mV/div
200μs/div
VIN=3.3V,
VOUT=18V
VEN 2V/div
200μs/div
VIN=3.6V,
VOUT=18V,
IOUT=10mA
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UM1665
Applications Information
Inductor Selection, Maximum Load Current
Since the PFM peak current control scheme is inherently stable, the inductor value does not
affect the stability of the regulator. The selection of the inductor together with the nominal load
current, input and output voltage of the application determines the switching frequency of the
converter. Depending on the application, inductor values between 2.2μH up to 22μH are
recommended. The maximum inductor value is determined by the maximum on time of the
switch, typically 6μs. The peak current limit of 400mA (typically) should be reached within
this 6μs period for proper operation.
The inductor value determines the maximum switching frequency of the converter. Therefore,
select the inductor value that ensures the maximum switching frequency at the converter
maximum load current is not exceeded. The maximum switching frequency is calculated by the
following formula:
V
 (VOUT VIN )
fs max  IN min
I P  L VOUT
Where:
IP=Peak current as described in the previous peak current control section
L=Selected inductor value
VINmin=The minimum input voltage when the highest switching frequency occurs
If the selected inductor value does not exceed the maximum switching frequency of the converter,
the next step is to calculate the switching frequency at the nominal load current using the following
formula:
2  I LOAD (VOUT  VIN  VD )
fs(ILOAD) 
2
IP  L
Where:
IP=Peak current as described in the previous peak current control section
L=Selected inductor value
ILOAD=Nominal load current
VD=Rectifier diode forward voltage (typically 0.3V)
A smaller inductor value gives a higher converter switching frequency, but lowers the efficiency.
The inductor value has less effect on the maximum available load current and is only of
secondary order. The best way to calculate the maximum available load current under certain
operating conditions is to estimate the expected converter efficiency at the maximum load current.
This number can be taken out of the efficiency graphs shown in page 6. The maximum load
current can then be estimated as follows:
2
I  L fs max
I LOADmax  η P
2  (VOUT  VIN )
Where:
IP=Peak current as described in the previous peak current control section
L=Selected inductor value
fsmax=Maximum switching frequency as calculated previously
η=Expected converter efficiency. Typically 70% to 85%
The maximum load current of the converter is the current at the operation point where the
converter starts to enter the continuous conduction mode. Usually the converter should always
operate in discontinuous conduction mode.
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UM1665
Last, the selected inductor should have a saturation current that meets the maximum peak current
of the converter (as calculated in the peak current control section). Use the maximum value for
ILIM for this calculation.
Another important inductor parameter is the dc resistance. The lower the DC resistance, the
higher the efficiency of the converter.
Setting the Output Voltage
The output voltage is calculated as:
VOUT  1.233 V (1 
R1
)
R2
For battery powered applications, a high impedance voltage divider should be used with a typical
value for R2 of 200kΩ and a maximum value for R1 of 2.2MΩ. Smaller values might be used to
reduce the noise sensitivity of the feedback pin.
A feedforward capacitor across the upper feedback resistor R1 is required to provide sufficient
overdrive for the error comparator.
The lower the switching frequency of the converter, the larger the feedforward capacitor value
required. A good starting point is to use a 10pF feedforward capacitor. As a first estimation, the
required value for the feedforward capacitor at the operation point can also be calculated using the
following formula:
1
C FF 
fs
2 π  R 1
20
Where:
R1=Upper resistor of voltage divider
fS=Switching frequency of the converter at the nominal load current (See previous section for
calculating the switching frequency)
CFF=Choose a value that comes closest to the result of the calculation
The larger the feedforward capacitor, the worse the line regulation of the device. Therefore, when
concern for line regulation is paramount, the selected feedforward capacitor should be as small as
possible.
Output Capacitor Selection
The output capacitor limits the output ripple and maintains the output voltage during large load
transitions. Ceramic capacitors with X5R or X7R temperature characteristics are highly
recommended due to their small size, low ESR, and small temperature coefficients. For most
applications, a 1μF ceramic capacitor is sufficient. For some applications a reduction in output
voltage ripple can be achieved by increasing the output capacitor.
Input Capacitor Selection
For good input voltage filtering, low ESR ceramic capacitors are recommended. A 4.7µF ceramic
input capacitor is sufficient for most of the applications. For better input voltage filtering this
value can be increased.
Diode Selection
Schottky diode is a good choice for UM1665 because of its low forward voltage drop and fast
reverse recovery. Using Schottky diode can get better efficiency. The current rating of the diode
should meet the peak current rating of the converter as it is calculated in the peak current control
section. Use the maximum value for ILIM for this calculation.
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UM1665
Layout Considerations
High switching frequencies and relatively large peak currents make the PCB layout a very
important part of design. Good design minimizes excessive EMI on the feedback paths and
voltage gradients in the ground plane, resulting in a stable and well-regulated output. Good layout
for the UM1665 can be implemented by following a few simple design rules.
1. The input capacitor should be placed as close as possible to the input pin for good input
voltage filtering.
2. The inductor and diode should be placed as close as possible to the switch pin to minimize
the noise coupling into other circuits.
3. The feedback network should be routed away from the inductor. The feedback pin and
feedback network should be shielded with a ground plane or trace to minimize noise coupling
into this circuit.
4. Wide traces should be used for connections in bold as shown in the figure below. A star
ground connection or ground plane minimizes ground shifts and noise.
L1
VIN
D1
SW
VIN
R1
UM1665
CIN
VOUT
EN
CFF
COUT
FB
GND
R2
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UM1665
Package Information
UM1665S: SOT23-5
Outline Drawing
θ
D
b
L
Symbol
4
E
E1
5
1
2
3
e1
c
Top View
End View
A1
A2
A
e
Side View
A
A1
A2
b
c
D
E
E1
e
e1
L
θ
DIMENSIONS
MILLIMETERS
INCHES
Min Typ Max Min
Typ
Max
1.013 1.15 1.40 0.040 0.045 0.055
0.00 0.05 0.10 0.000 0.002 0.004
1.00 1.10 1.30 0.039 0.043 0.051
0.30
0.50 0.012
0.020
0.10 0.15 0.20 0.004 0.006 0.008
2.82
3.10 0.111
0.122
1.50 1.60 1.70 0.059 0.063 0.067
2.60 2.80 3.00 0.102 0.110 0.118
0.95REF
0.037REF
1.90REF
0.075REF
0.30
0.60 0.012
0.024
0°
8°
0°
8°
Land Pattern
2.35
0.56
1.20
NOTES:
1. Compound dimension: 2.92×1.60;
2. Unit: mm;
3. General tolerance ±0.05mm unless otherwise
specified;
4. The layout is just for reference.
0.95
0.95
PHO
M
Tape and Reel Orientation
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UM1665
UM1665DA: TDFN6 3.0×3.0
Outline Drawing
D2
E
E2
45
º(0
.3
5
Symbol
*0
.3
5
L(6X)
D
)
(Pin #1 ID)
Z(4X)
e
b(6X)
Bottom View
A3
Side View
A1
A
Top View
A
A1
A3
b
D
D2
E
E2
e
L
Z
DIMENSIONS
MILLIMETERS
Min Typ Max Min
0.57 0.60 0.63 0.022
0.00 0.02 0.05 0.000
0.15TYP
0.35 0.40 0.45 0.014
2.95 3.00 3.05 0.116
2.25 2.35 2.45 0.089
2.95 3.00 3.05 0.116
1.48 1.58 1.68 0.058
0.95TYP
0.35 0.40 0.45 0.014
0.35TYP
INCHES
Typ
0.024
0.0008
0.006TYP
0.016
0.118
0.093
0.118
0.062
0.037TYP
0.016
0.014TYP
Max
0.025
0.002
0.018
0.120
0.096
0.120
0.066
0.018
Land Pattern
3.00
3.40
0.65
1.58
3.00
0.20
2.35
0.95
0.56
NOTES:
1. Compound dimension: 3.00×3.00;
2. Unit: mm;
3. General tolerance ±0.05mm unless otherwise
specified;
4. The layout is just for reference.
Tape and Reel Orientation
1665
XX
________________________________________________________________________
http://www.union-ic.com Rev.05 Mar.2016
14/15
UM1665
GREEN COMPLIANCE
Union Semiconductor is committed to environmental excellence in all aspects of its
operations including meeting or exceeding regulatory requirements with respect to the use
of hazardous substances. Numerous successful programs have been implemented to
reduce the use of hazardous substances and/or emissions.
All Union components are compliant with the RoHS directive, which helps to support
customers in their compliance with environmental directives. For more green compliance
information, please visit:
http://www.union-ic.com/index.aspx?cat_code=RoHSDeclaration
IMPORTANT NOTICE
The information in this document has been carefully reviewed and is believed to be
accurate. Nonetheless, this document is subject to change without notice. Union assumes
no responsibility for any inaccuracies that may be contained in this document, and makes
no commitment to update or to keep current the contained information, or to notify a
person or organization of any update. Union reserves the right to make changes, at any
time, in order to improve reliability, function or design and to attempt to supply the best
product possible.
Union Semiconductor, Inc
Add: Unit 606, No.570 Shengxia Road, Shanghai 201210
Tel: 021-51093966
Fax: 021-51026018
Website: www.union-ic.com
________________________________________________________________________
http://www.union-ic.com Rev.05 Mar.2016
15/15
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