10W 5V Mini USB Adapter Reference Board with ICE2QS03G

A N-REF -10W A DAPTER
10W 5V Adapter Reference Board
with ICE2QS03G & IPU60R950C6
AN-PS0080
Appl ic ati on Note AN - REF -10W ADAP TER
V1.1, 2014-02-20
Power Management & M ultim arket
Edition 2014-02-20
Published by Infineon Technologies AG,
81726 Munich, Germany.
© 2014 Infineon Technologies AG
All Rights Reserved.
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(INCLUDING WITHOUT LIMITATION WARRANTIES OF NON-INFRINGEMENT OF INTELLECTUAL
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THIS APPLICATION NOTE.
Information
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Warnings
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10W 5V Adapter Reference Board with ICE2QS03G & IPU60R950C6
AN-PS0080
Trademarks of Infineon Technologies AG
AURIX™, C6 6™, CanPAK™, CIPOS™, CIPURSE™, EconoPACK™, CoolMOS™, CoolSET™,
CORECONTROL™, CROSSAVE™, DAVE™, DI-POL™, EasyPIM™, EconoBRIDGE™, EconoDUAL™,
EconoPIM™, EconoPACK™, EiceDRIVER™, eupec™, FCOS™, HITFET™, HybridPACK™, I²RF™,
ISOFACE™, IsoPACK™, MIPAQ™, ModSTACK™, my-d™, NovalithIC™, OptiMOS™, ORIGA™,
POWERCODE™; PRIMARION™, PrimePACK™, PrimeSTACK™, PRO-SIL™, PROFET™, RASIC™,
ReverSave™, SatRIC™, SIEGET™, SINDRION™, SIPMOS™, SmartLEWIS™, SOLID FLASH™,
TEMPFET™, thinQ!™, TRENCHSTOP™, TriCore™.
Other Trademarks
Advance Design System™ (ADS) of Agilent Technologies, AMBA™, ARM™, MULTI-ICE™, KEIL™,
PRIMECELL™, REALVIEW™, THUMB™, µVision™ of ARM Limited, UK. AUTOSAR™ is licensed by
AUTOSAR development partnership. Bluetooth™ of Bluetooth SIG Inc. CAT-iq™ of DECT Forum.
COLOSSUS™, FirstGPS™ of Trimble Navigation Ltd. EMV™ of EMVCo, LLC (Visa Holdings Inc.). EPCOS™
of Epcos AG. FLEXGO™ of Microsoft Corporation. FlexRay™ is licensed by FlexRay Consortium.
HYPERTERMINAL™ of Hilgraeve Incorporated. IEC™ of Commission Electrotechnique Internationale. IrDA™
of Infrared Data Association Corporation. ISO™ of INTERNATIONAL ORGANIZATION FOR
STANDARDIZATION. MATLAB™ of MathWorks, Inc. MAXIM™ of Maxim Integrated Products, Inc.
MICROTEC™, NUCLEUS™ of Mentor Graphics Corporation. MIPI™ of MIPI Alliance, Inc. MIPS™ of MIPS
Technologies, Inc., USA. muRata™ of MURATA MANUFACTURING CO., MICROWAVE OFFICE™ (MWO) of
Applied Wave Research Inc., OmniVision™ of OmniVision Technologies, Inc. Openwave™ Openwave Systems
Inc. RED HAT™ Red Hat, Inc. RFMD™ RF Micro Devices, Inc. SIRIUS™ of Sirius Satellite Radio Inc.
SOLARIS™ of Sun Microsystems, Inc. SPANSION™ of Spansion LLC Ltd. Symbian™ of Symbian Software
Limited. TAIYO YUDEN™ of Taiyo Yuden Co. TEAKLITE™ of CEVA, Inc. TEKTRONIX™ of Tektronix Inc.
TOKO™ of TOKO KABUSHIKI KAISHA TA. UNIX™ of X/Open Company Limited. VERILOG™, PALLADIUM™
of Cadence Design Systems, Inc. VLYNQ™ of Texas Instruments Incorporated. VXWORKS™, WIND RIVER™
of WIND RIVER SYSTEMS, INC. ZETEX™ of Diodes Zetex Limited.
Last Trademarks Update 2011-11-11
Application Note AN-REF-10W ADAPTER
3
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10W 5V Adapter Reference Board with ICE2QS03G & IPU60R950C6
AN-PS0080
Revision History
Major changes since previous revision
Date
Version
Changed By
Change Description
20 Feb 2014
1.1
Kyaw Zin Min
Update to new format
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Application Note AN-REF-10W ADAPTER
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Table of Contents
Revision History .................................................................................................................................................... 4
Table of Contents .................................................................................................................................................. 5
1
Abstract .............................................................................................................................................. 7
2
Evaluation Board Photos ................................................................................................................. 7
3
List of Features of ICE2QS03G ........................................................................................................ 8
4
Technical Specifications for Reference Board .............................................................................. 8
5
5.1
5.2
5.3
5.4
5.5
Circuit Description ............................................................................................................................ 9
Mains Input Rectification and Filtering ................................................................................................ 9
PWM Control and switching MOSFET ................................................................................................ 9
Snubber Network ................................................................................................................................ 9
Output Stage ....................................................................................................................................... 9
Feedback Loop ................................................................................................................................... 9
6
6.1
6.2
6.3
6.4
6.5
Circuit Operation ............................................................................................................................. 10
Startup Operation .............................................................................................................................. 10
Normal Mode Operation .................................................................................................................... 10
Primary side peak current control ..................................................................................................... 10
Digital Frequency Reduction ............................................................................................................. 10
Burst Mode Operation ....................................................................................................................... 10
7
7.1
7.2
7.3
7.4
7.5
7.6
Protection Features ........................................................................................................................ 11
VCC over voltage and under voltage protection ............................................................................... 11
Foldback point protection .................................................................................................................. 11
Over load/Open loop protection ........................................................................................................ 11
Adjustable output overvoltage protection .......................................................................................... 11
Short winding protection.................................................................................................................... 11
Auto restart for over temperature protection ..................................................................................... 11
8
8.1
8.2
Circuit diagram ................................................................................................................................ 12
1st PCB artwork (top) ......................................................................................................................... 13
2nd PCB artwork (bottom) .................................................................................................................. 13
9
Component List ............................................................................................................................... 14
10
Transformer Construction.............................................................................................................. 15
11
11.1
11.2
11.3
11.4
11.5
11.6
Test Results ..................................................................................................................................... 16
Efficiency ........................................................................................................................................... 16
Input standby power .......................................................................................................................... 16
Line regulation ................................................................................................................................... 17
Load regulation ................................................................................................................................. 17
Maximum input power between low and high line ............................................................................ 17
EMI test results ................................................................................................................................. 18
12
12.1
12.2
12.3
12.4
Waveforms and Scope Plots .......................................................................................................... 19
Startup at Full Load ........................................................................................................................... 19
Drain and VCS voltage at maximum load ........................................................................................... 19
Zero Crossing Point during Normal Operation .................................................................................. 20
Load Transient Response ................................................................................................................. 20
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12.5
12.6
Burst Mode Operation ....................................................................................................................... 21
Protection Mode ................................................................................................................................ 21
13
References ....................................................................................................................................... 22
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Abstract
This application note is an engineering report of a very small form factor reference design for universal input
10.5W 5V USB adapter. The adapter is using IFX ICE2QS03G, a second generation current mode control
quasi-resonant flyback topology controller and IFX IPU60R950C6, a sixth generation of high voltage power
CoolMOS™. The distinguishing features of this reference design are very small form factor, best in class low
standby power, high efficiency, good EMI performance without using input common mode choke, very tight
maximum input power control between low and high line and variious modes of protection for high reliable
system.
2
Evaluation Board Photos
ICE2QS03G
22.6mm
IPU60R950C6
30.5mm
30.0mm
Figure 1 – REF-ICE2QS03G & IPU60R950C6 10W ADAPTER (Dimensions LxWxH: 30.5x22.6x30 mm3)
This document contains the list of features, the power supply specification, schematic, bill of material and the
transformer construction documentation. Typical operating characteristics such as performance curve and
scope waveforms are showed at the rear of the report.
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List of Features of ICE2QS03G
Quasi resonant operation till very low load
Active burst mode operation at light/no load for low standby input power (< 50mW)
Digital frequency reduction with decreasing load
HV startup cell with constant charging current
Built-in digital soft-start
Foldback correction and cycle-by-cycle peak current limitation
Auto restart mode for VCC Overvoltage protection
Auto restart mode for VCC Undervoltage protection
Auto restart mode for openloop/overload protection
Auto restart mode for Over temperature protection
Latch-off mode for adjustable output overvoltage protection
4
Technical Specifications for Reference Board
Input voltage
90Vac~264Vac
Input frequency
50/60Hz
Input Standby Power
< 50mW @ no load
Maximum input power(Peak Power) for full input range
< ±5% of input power
Output voltage
5V
Output current
2.1A
Output power
10.5W
Active mode average efficiency(25%,50%,75% & 100%load)
>78% at full load
Minimum switching frequency at full load and minimum input voltage
40kHz
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Circuit Description
5.1
Mains Input Rectification and Filtering
The AC line input side comprises the input fuse F1 as overcurrent protection. A rectified DC voltage (127V ~
373V) is obtained through a bridge rectifier BR1 and a pi filter C1, L1, R13 and C2. The pi filer also
attenuates the differential mode conducted EMI.
5.2
PWM Control and switching MOSFET
The PWM pulse is generated by the Quasi Resonant PWM current-mode Controller ICE2QS03G and this
PWM pulse drives the high power CoolMOS™, IPU60R950C6 (C6) which designed according to the
revolutionary Superjunction (SJ) principle. The CoolMOS™ C6 provides all benefits of a fast switching SJ
MOSFET while not sacrificing ease of use. It achieves extremely low conduction and switching losses and
can make switching applications more efficient, more compact, lighter and cooler. The PWM switch-on is
determined by the zero-crossing input signal and the value of the up/down counter. The PWM switch-off is
determined by the feedback signal VFB and the current sensing signal VCS. ICE2QS03G also performs all
necessary protection functions in flyback converters. Details about the information mentioned above are
illustrated in the product datasheet.
5.3
Snubber Network
A snubber network R3, C3 and D1 dissipate the energy of the leakage inductance and suppress ringing on
the SMPS transformer. Due to the resonant capacitor (MOSFET’s drain source capacitance), the overshoot
is relatively smaller than fixed frequency flyback converter. Thus the snubber resistor can be used with a
larger one which will reduce the snubber loss.
5.4
Output Stage
On the secondary side, 5V output, the power is coupled out via a schottky diode D3. The capacitors C8 and
C10 provide energy buffering to reduce the output ripple and prevent interference between SMPS switching
frequency and line frequency considerably. Storage capacitors C8 and C10 are designed to have an internal
resistance (ESR) as small as possible. This is to minimize the output voltage ripple caused by the triangular
current.
5.5
Feedback Loop
For feedback, the output is sensed by the voltage divider of R1, R2 and R12 and compared to TL431 internal
reference voltage. C17 and R11 comprise the compensation network. The output voltage of TL431 is
converted to the current signal via optocoupler U1 and two resistors R9 and R14 for regulation control.
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6
Circuit Operation
6.1
Startup Operation
Since there is a built-in startup cell in the ICE2QS03G, there is no need for external start up resistor, which
can improve standby performance significantly.
When VCC reaches the turn on voltage threshold 18V, the IC begins with a soft start. The soft-start
implemented in ICE2QS03G is a digital time-based function. The preset soft-start time is 12ms with 4 steps.
If not limited by other functions, the peak voltage on CS pin will increase step by step from 0.32V to 1V
finally. After IC turns on, the Vcc voltage is supplied by auxiliary windings of the transformer.
6.2
Normal Mode Operation
The secondary output voltage is built up after startup. The secondary regulation control is adopted with
TL431 and optocoupler. The compensation network C17 and R11 constitutes the external circuitry of the
error amplifier of TL431. This circuitry allows the feedback to be precisely controlled with respect to
dynamically varying load conditions, therefore providing stable control.
6.3
Primary side peak current control
The MOSFET drain source current is sensed via external resistor R8 and buffer network R7, C6. Since
ICE2QS03G is a current mode controller, it would have a cycle-by-cycle primary current and feedback
voltage control which can make sure the maximum power of the converter is controlled in every switching
cycle.
6.4
Digital Frequency Reduction
During normal operation, the switching frequency for ICE2QS03G is digitally reduced with decreasing load.
At light load, the CoolMOS™ IPU60R950C6 will be turned on not at the first minimum drain-source voltage
time, but on the nth. The counter is in range of 1 to 7, which depends on feedback voltage in a time-base.
The feedback voltage decreases when the output power requirement decreases, and vice versa. Therefore,
the counter is set by monitoring voltage VFB. The counter will be increased with low VFB and decreased with
high VFB. The thresholds are preset inside the IC.
6.5
Burst Mode Operation
At light load condition, the SMPS enters into Active Burst Mode. At this stage, the controller is always active
but the Vcc must be kept above the switch off threshold. During active burst mode, the efficiency increase
significantly and at the same time it supports low ripple on Vout and fast response on load jump.
For determination of entering Active Burst Mode operation, three conditions apply:
1. The feedback voltage is lower than the threshold of VFBEB(1.25V). Accordingly, the peak current sense
voltage across the shunt resistor is 0.1667;
2. The up/down counter is 7;
3. And a certain blanking time (tBEB=24ms).
Once all of these conditions are fulfilled, the Active Burst Mode flip-flop is set and the controller enters Active
Burst Mode operation. This multi-condition determination for entering Active Burst Mode operation prevents
mis-triggering of entering Active Burst Mode operation, so that the controller enters Active Burst Mode
operation only when the output power is really low during the preset blanking time.
During active burst mode, the maximum current sense voltage is reduced from 1V to 0.34V so as to reduce
the conduction loss and the audible noise. At the burst mode, the FB voltage is changing like a sawtooth
between 3.0 and 3.6V.
The feedback voltage immediately increases if there is a high load jump. This is observed by one
comparator. As the current limit is 34% during Active Burst Mode a certain load is needed so that feedback
voltage can exceed VLB (4.5V). After leaving active burst mode, maximum current can now be provided to
stabilize VO. In addition, the up/down counter will be set to 1 immediately after leaving Active Burst Mode.
This is helpful to decrease the output voltage undershoot
Application Note AN-REF-10W ADAPTER
10
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7
Protection Features
7.1
VCC over voltage and under voltage protection
During normal operation, the Vcc voltage is continuously monitored. When the Vcc voltage increases up to
VVCCOVP or Vcc voltage falls below the under voltage lock out level VVCCoff, the IC will enter into autorestart
mode.
7.2
Foldback point protection
For a quasi-resonant flyback converter, the maximum possible output power is increased when a constant
current limit value is used for all the mains input voltage range. This is usually not desired as this will
increase additional cost on transformer and output diode in case of output over power conditions.
The internal foldback protection is implemented to adjust the VCS voltage limit according to the bus voltage.
Here, the input line voltage is sensed using the current flowing out of ZC pin, during the MOSFET on-time.
As the result, the maximum current limit will be lower at high input voltage and the maximum output power
can be well limited versus the input voltage.
7.3
Over load/Open loop protection
In case of open control loop, feedback voltage is pulled up with internally block. After a fixed blanking time,
the IC enters into auto restart mode. In case of secondary short-circuit or overload, regulation voltage VFB will
also be pulled up, same protection is applied and IC will auto restart.
7.4
Adjustable output overvoltage protection
During off-time of the power switch, the voltage at the zero-crossing pin ZC is monitored for output
overvoltage detection. If the voltage is higher than the preset threshold 3.7V for a preset period 100μs, the
IC is latched off.
7.5
Short winding protection
The source current of the MOSFET is sensed via external resistor R8. If the voltage at the current sensing
pin is higher than the preset threshold VCSSW of 1.68V during the on-time of the power switch, the IC is
latched off. This constitutes a short winding protection. To avoid an accidental latch off, a spike blanking time
of 190ns is integrated in the output of internal comparator.
7.6
Auto restart for over temperature protection
The IC has a built-in over temperature protection function. When the controller’s temperature reaches 140
°C, the IC will shut down switch and enters into autorestart. This can protect power MOSFET from
overheated.
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8
Circuit diagram
Figure 2 – Schematics
Application Note
12
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8.1
1st PCB artwork (top)
Figure 3 – View from component side (left) and solder side (right)
8.2
2nd PCB artwork (bottom)
Figure 4 – View from component side (left) and solder side (right)
Application Note
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Component List
9
Component List
Items
1
2
3
4
5
6
7
8
9
10
11
12
13
14
15
16
17
18
19
20
21
22
23
24
25
26
27
28
29
30
31
32
33
34
35
36
37
38
39
40
41
42
43
44
45
46
47
Designator
BD1
C1
C10
C11
C17
C2
C3
C4
C5
C6
C7
C8
C9
CY1
D1
D2
D3
F1
IC1
L1
Q1
R1
R10
R11
R12
R13
R14
R2
R3
R4
R5
R6
R7
R8
R9
RA
RB
RC
RD
RD1
T1
U1
U2
USBPORT
ZD1
L
N
Application Note
Part Value
B10S/0.5A, 1000V (bridge rectifier)
15uF/400V/105℃
820uF/6.3V
10uF/25V/X7R
100nF/X7R
6.8uF/400V/105℃
4.7nF/630V/X7R
2.2uF/25V/X7R
68pF/50V/NP0
100pF/50V/NP0
1nF/50V/X7R
820uF/6.3V
1nF/50V/X7R
2.2nF/250Vac
F1J-600V/1A/1.25V
BAV21W
SBR10U45SP5-45V/10.0A/0.42V
T1A/250V
ICE2QS03G
0.9mH/0.1A/φ0.12
N MOS-IPU60R950C6
10K/0805,±1%
22.1R/0805,±5%
22.1K/0805,±5%
N.A
51.1R/1206, ±1%
562R/0805, ±1%
10K/0805,±1%
56.2K/1206, ±1%
4R02/0805, ±5%
51.1K/0805, ±1%
10K/0805,±1%
100R/0805, ±1%
1.5R/0.5W, ±1%
150R/0805,±5%
43.2K/0805, ±1%
51.1K/0805, ±1%
75K/0805, ±1%
51.1K/0805, ±1%
47.5R/0805, ±1%
750341723 (EE19)
SFH617A-3
TL431
6Pin-USB,90℃
MMSZ22T1G
37MM-UL1007 22#-red
37MM-UL1007 22#-black
14
Q'ty
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
Manufacturer
Murata
Murata
Murata
Murata
Murata
Infineon
Infineon
Wurth Electronics Midcom
20 February 2014
10W 5V Adapter Reference Board with ICE2QS03G & IPU60R950C6
AN-PS0080
Transformer Construction
10
Transformer Construction
Core and material: EE19, 3C90 (other equivalent ferrite)
Bobbin: EE19 Vertical Version
Primary Inductance: Lp=1.6mH (±10%), measured between pin 6 and pin 4
Manufacturer and part number: Wurth Electronics Midcom (750341723)
Transformer structure:
Start
7
2
5
S
5
6
End No. of Turns
Wire size
5
27
Ø0.20mm
4
65
Ø0.20mm
x
1.1
0.05mm*7mm
Copper foil
F
9
Ø0.65mm T.I.W
x
1.1
0.05mm*7mm
Copper foil
2
70
Ø0.20mm
Layer
Auxiliary
½ Primary
Shielded
Secondary
Shielded
½ Primary
Notes: The transformer has 2 shielded winding and 1
Faraday Shield. The Faraday Shield is 1 layer
0.05mm*7mm copper foil over the core and connected
to Pin5.
Figure 5 – Transformer structure
Application Note
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Test Results
11
Test Results
11.1
Efficiency
Figure 6 – Efficiency vs. AC line voltage
11.2
Input standby power
Figure 7 – Input standby power @ no load Vs. AC line input voltage ( measured by Yokogawa WT210 power
meter - integration mode )
Application Note
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Test Results
11.3
Line regulation
Figure 8 – Line regulation Vout @ full load vs. AC line input voltage
11.4
Load regulation
Figure 9 – Load regulation Vout vs. output power
11.5
Maximum input power between low and high line
Figure 10 – Maximum input power ( before overload protection ) vs. AC line input voltage
Application Note
17
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Test Results
11.6
EMI test results
The conducted EMI was measured by Schaffner (SMR4503) under test standard EN55022 or CISPR22 Class
B. The demo board was set up at 10.5W with the input voltage at 115Vac and 230Vac. The Red curve(upper
one) is the Quasi Peak data and the Green curve(lower one) is the Average data. Both of them can meet the
regulations, pass conducted emissions EN55022 (CISPR 22) class B with > 6dB margin.
Figure 11 – 230V Line results
Figure 12 – 115V Line results
Application Note
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Waveforms and Scope Plots
12
Waveforms and Scope Plots
12.1
Startup at Full Load
Figure 13 – Constant Charging VCC at Startup
CH1(Yellow) Supply Voltage, VCC
CH2(Red) Zero Crossing Voltage, VZC
CH3(Blue) Current Sense Voltage, VCS
CH4(Green) Feedback Voltage, VFB
12.2
Figure 14 – Step Softstart
CH1(Yellow) Supply Voltage, VCC
CH2(Red) Zero Crossing Voltage, VZC
CH3(Blue) Current Sense Voltage, VCS
CH4(Green) Feedback Voltage, VFB
Drain and VCS voltage at maximum load
Figure 15 - Operation @ 90Vac and max. load
Ch1=Vcs(Yellow), Ch3=Vds(Blue)
Vin=90Vac, Iout=2.1A(full load)
Vds_max=264V
Application Note
Figure 16 - Operation @ 264Vac and max. load
Ch1=Vcs(Yellow), Ch3=Vds(Blue)
Vin=264Vac, Iout=2.1A(full load)
Vds_max=516V
19
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Waveforms and Scope Plots
12.3
Zero Crossing Point during Normal Operation
Figure 17 – Working at 1st ZC
CH1(Yellow) Current Sense Voltage, VCS
CH3(Blue) MOSFET Dain-Source Voltage, VDS
12.4
Figure 18 – Working at 7th ZC
CH1(Yellow) Current Sense Voltage, VCS
CH2 MOSFET Dain-Source Voltage, VDS
Load Transient Response
Figure 19 – AC Output Ripple Undershoot
10%  100% load, 0.4A/us
VO_max=5.026V
VO_min=4.917V
Vripple_pk_pk=109mV
CH1 Output Voltage, Vo
CH2 Output Current, Io
Application Note
Figure 20 – AC Output Ripple Overshoot
100%  10% load, 0.4A/us
VO_max=5.051V
VO_min=4.942V
Vripple_pk_pk=109mV
CH1 Output Voltage, Vo
CH2 Output Current, Io
20
20 February 2014
10W 5V Adapter Reference Board with ICE2QS03G & IPU60R950C6
AN-PS0080
Waveforms and Scope Plots
12.5
Burst Mode Operation
6th
7th
Figure 22 – Leaving Burst Mode
CH1(Yellow) Feedback Voltage, VFB
CH2(Red) Zero Crossing Voltage, VZC
CH3(Blue) Current Sense Voltage, VCS
CH4(Green) Output Voltage, VO
Condition: VFB>4.5V
Figure 21 – Entering Burst Mode
CH1(Yellow) Feedback Voltage, VFB
CH2(Red) Zero Crossing Voltage, VZC
CH3(Blue) Current Sense Voltage, VCS
CH4(Green) Output Voltage, VO
Condition: ZC=7, FB<1.25V, Blanking time = 26ms
12.6
Protection Mode
Figure 24 – Over Load/Open Loop Protection
CH1(Yellow) Feedback Voltage, VFB
CH2(Red) Zero Crossing Voltage, VZC
CH3(Blue) Current Sense Voltage, VCS
CH4(Green) Supply Voltage, Vcc
Condition: VFB>4.5V for 30ms
Figure 23 – Vout Over Voltage Protection
CH1(Yellow) Feedback Voltage, VFB
CH2(Red) Zero Crossing Voltage, VZC
CH3(Blue) Output Voltage, VO
CH4(Green) Supply Voltage, Vcc
Condition: VO >6.7V (VZC>3.7V)
Application Note
21
20 February 2014
10W 5V Adapter Reference Board with ICE2QS03G & IPU60R950C6
AN-PS0080
References
13
References
[1]
ICE2QS03G datasheet, Infineon Technologies AG
[2]
IPU60R950C6 datasheet, 600V CoolMOS™ C6 Power Transistor
[3]
Converter Design Using the Quasi-Resonant PWM Controller ICE2QS01, Infineon Technologies AG,
2006. [ANPS0003]
[4]
Design tips for flyback converters using the Quasi-Resonant PWM controller ICE2QS01, Infineon
Technologies, 2006. [ANPS0005]
[5]
Determine the switching frequency of Quasi-Resonant flyback converters designed with ICE2QS01,
Infineon Technologies, 2006. [ANPS0004]
[6]
ICE2QS03G design guide. [ANPS0027]
[7]
36W Evaluation Board with Quasi-Resonant PWM Controller ICE2QS03G, 2011. [AN-PS0040]
Application Note
22
20 February 2014
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