AN9836: Motherboard Power Conversion Solutions Using the HIP6020 and HIP6021 Controller ICs

Motherboard Power Conversion Solutions Using
the HIP6020 and HIP6021 Controller ICs
Application Note
Introduction
The rapidly changing desktop motherboard architecture for
core processor and Accelerated Graphics Port (AGP)
voltages demand innovative power conversion solutions.
The HIP6020 [1] and HIP6021 [2] controllers provide a
bridge over these challenging power concerns. This
document describes the HIP6020EVAL1 and
HIP6021EVAL1 reference designs, features, and usage
guidelines.
April 1999
AN9836
For high performance AGP systems, the HIP6020EVAL1
monitors and controls a standard buck converter to regulate
the 1.5V or 3.3V Universal AGP Card bus voltage
(VCC_VDDQ). While the HIP6021EVAL1 addresses the
lower performance AGP systems with a third integrated
adjustable linear controller to regulate the 1.5V or 3.3V AGP
core voltage.
FROM ATX
SUPPLY
+5V
+12V
EMT TOOL
VCC_CORE
ADJUSTABLE
SYNCHRONOUS BUCK
CONTROLLER
+
DAC
VID0
VID1
VID2
VID3
VID4
VCC_VDDQ
+
ADJUSTABLE
STANDARD BUCK
CONTROLLER
THIS BLOCK
INCLUDED IN
HIP6020 ONLY
ADJUSTABLE
LINEAR
CONTROLLER
THIS BLOCK
INCLUDED IN
HIP6021 ONLY
+3.3V
+
VCC_VTT
ADJUSTABLE
LINEAR
CONTROLLER
+
VCC_MCH
ADJUSTABLE
LINEAR
CONTROLLER
+
FIGURE 1. HIP6020/21EVAL1 BLOCK DIAGRAM
Figure 1 presents a simple block diagram of the HIP6020/21
application circuit. The +3.3V, +5V, and +12V power inputs
are provided by an ATX power supply. The HIP6020 [1] and
HIP6021 [2] both monitor and regulate four output voltages.
Both provide a synchronous-rectified buck converter
controller which regulates the microprocessor core voltage
(VCC_CORE) to a level programmed by a 5-bit digital code.
As well as, two adjustable linear controllers which drive
external MOSFETs to supply the 1.5V GTL bus voltage
(VCC_VTT) and 1.8V North/South Bridge core voltage
(VCC_MCH) and/or cache memory. The linear regulators
use the 3.3V from the ATX for their input voltage to minimize
the power dissipated.
1
J2
SLOT 1
TP
HIP6020/21EVAL1
FIGURE 2. QUICK START EVALUATION CONNECTIONS
The HIP6020/21 EVAL1 circuit board shows the layout and
traces of the power supply portion of a computer
motherboard. Included on the boards are the ATX input
power connector and a Pentium II, SLOT 1 connector.
Motherboard designers should reference the component
placement and printed circuit routing of the specific circuit
board. Both circuit boards contain jumpers and spare
component placeholders to facilitate detailed evaluation of
the HIP6020 or HIP6021.
Quick Start Evaluation
Both evaluation platforms support testing with standard
power supplies or an ATX-style power supply. Simply
connect the ATX supply to J2 connector, see Figure 2, or
connect standard laboratory supplies to the related posts
marked +12VIN, +5VIN, +3.3VIN and GND. No power-up
sequence is required when using standard laboratory power
supplies.
The outputs can be exercised using either resistive loads,
electronic loads, or the Intel Slot 1 EMT tool. Shielded scope
probe test points (TP2, TP5, TP6 and TP8) on the outputs
(VCC_VDDQ, VCC_CORE, VCC_VTT and VCC_MCH)
allow for accurate inspection of the output power quality.
Before proceeding, please consult Table 1 for the evaluation
board’s design envelope characteristics.
1-888-INTERSIL or 1-888-468-3774 | Copyright © Intersil Corporation 1999
Pentium® is a registered trademark of Intel Corporation.
Application Note 9836
TABLE 1. HIP6020/21EVAL1 OUTPUT LOAD CAPABILITIES
OUTPUT
NOMINAL
VOLTAGE
(V)
STATIC
TOLERANCE
(±,%)
DYNAMIC
TOLERANCE
(±,%)
NOMINAL
CURRENT
(A)
MAXIMUM
CURRENT
(A)
MAXIMUM
CURRENT
STEP (A)
MAXIMUM
SLEW RATE
(A/μs)
DESIGN
PLATFORM
(EVAL1)
VCC_CORE
2.0
3.0
6.5
10
17.4
9.5
20.0
Both
VCC_VDDQ
1.5/3.3
3.0
9.0
1.0
3.0
2.0
1.0
HIP6021
VCC_VDDQ
1.5/3.3
3.0
9.0
2.0
6.0
4.0
1.0
HIP6020
VCC_VTT
1.5
3.0
9.0
1.0
3.0
2.0
1.0
Both
VCC_MCH
1.8
3.0
5.0
1.0
3.0
2.0
1.0
Both
HIP6020/21EVAL1 Reference Designs
The evaluation board is designed to simultaneously meet all
the applicable criteria outlined in Table 1. The following
section highlights some of the most important features of this
system power solution.
ATX Power Supply Control Interface
JP7 allows control of the ATX power supply. Placing the
jumper in the 1-2 position, connects the PS-ON (output
enable) input of the ATX supply to ground, thus
unconditionally enabling the outputs. Placing the jumper in
the 2-3 position enables automatic control of the ATX. When
ATX supply turns on, the 5V stand-by output turns Q6A on to
enable the main ATX outputs. When FAULT/RT pin goes
high, Q6B latches on, thus turning off Q6A and disabling the
ATX outputs. Cycling power off and then back on re-enables
the ATX power supply. The sole purpose of this circuit is to
exemplify a possible interface between the control circuit’s
FAULT output and an ATX power supply.
ATX
CONNECTOR
9
R15
5.1K
J2
14
3, 5, 7, 13
15, 16, 17
PS-ON
JP7
GND
3
2
1
CR2
R16
5.1K
1N4148
Q6A
1/2
RF1K49154
Q6B
1/2
RF1K49154
FIGURE 3. ATX POWER SUPPLY CONTROL CIRCUIT
2
2.030V
2.000V
WITHOUT
DROOP
1.970V
WITH DROOP
OUTPUT CURRENT
17.4A
FIGURE 4. OUTPUT VOLTAGE DROOP AT 2.0V DAC SETTING
51K
5VSB
The synchronous switching regulator on the
HIP6020/21EVAL1 board implements output voltage droop
functions, where the output voltage sags proportionately with
the output current. Although not necessary for proper circuit
operation, this method takes advantage of the static
regulation limits to improve the dynamic regulation by
expanding the available headroom for transient edge output
excursion. In such practical applications, compared to a nondroop implementation, this translates to fewer output
capacitors or better regulation for the same type and number
of capacitors. Figure 4 details the output voltage
characteristics of a converter with 3.0% droop compared to a
non-droop implementation.
0.5A
R17
FAULT/RT
Lossless Output Voltage Droop with Load
OUTPUT VOLTAGE
When using the Intel Slot 1 EMT Tool, note that the core
regulator VID jumpers (JP0-JP4) located on the evaluation
board are in parallel with the ones located on the EMT tool.
Remember to de-populate one set of jumpers completely
and use the other set to dial-in the desired output voltage.
In contrast to droop implementation involving a resistive
element placed in the output current path, this method does
not involve the additional power loss introduced by the
resistor. By moving the voltage regulation point ahead of the
output inductor (at the PHASE node), droop becomes equal
to the average voltage drop across the output inductor’s DC
resistance as well as any distributed resistance. To insure
symmetric output voltage excursions in response to load
transients, the output voltage is offset above the nominal
level by half the calculated droop.
Application Note 9836
Over-Current Protection
The switching regulators within the HIP6020 and HIP6021
employ a lossless current sensing technique based on the
upper MOSFETs rDS(ON). During the ON-time of the upper
MOSFET, its drain-to-source voltage is compared with a
user-adjustable voltage created by an internal current
source across ROCSET (i.e., R2, R3 in the HIP6020EVAL1
schematic). When the MOSFETs drain-to-source voltage
exceeds the preset threshold, the regulator immediately
shuts down all outputs and initiates a soft-start cycle. If the
condition persists, the third shutdown latches the chip off
and pulls the FAULT/RT pin high. Cycling the bias voltage
OFF and ON resets the protection circuitry.
The linear regulator outputs employ a different method of
overcurrent detection. Given the relatively large rDS(ON) of
the pass devices, a short-circuit condition usually translates
into a dip in the output voltage. If the output voltage (as
sensed at the feedback pin) dips below approximately 75%
of the set point, this undervoltage is interpreted as an
overcurrent event and the control IC reacts accordingly,
shutting down all outputs and cycling the soft-start.
The internal regulator is protected by an additional internal
output current mirror. Output current exceeding the preset
threshold (see data sheet) generates a similar response.
Any over-current event on any output is reported by the
toggle of the PGOOD output.
Over-Voltage Protection
blows due to the magnitude of the surge current being drawn
from the 5V input supply. Proper operation of this protection
feature is contingent, however, on the 12V bias voltage
being sufficiently high to turn on the lower MOSFET. The
circuit has been tested with several ATX supplies, and they
all produced acceptable bias voltage for the operation of the
protection circuitry and the on-board UltraFET MOSFETs.
Figure 6 depicts the same start-up scenario, this time with
the ATX supply control interface enabled. As seen in the
oscilloscope capture, as soon as power-on reset (POR)
thresholds are detected, the HIP6020/21 detects the
overvoltage condition and reports it on the FAULT/RT pin. In
turn, the control circuit shuts down the ATX supply by
generating a logic high at the PS-ON input, before any
expensive damage can occur.
10
FAULT/RT
0
10
+12VIN
0
2
1
+5VIN
0
2
1
VCC_CORE
The microprocessor core regulator (synchronous buck) has
a voltage-tracking over-voltage threshold set at 115%
(typically) of the DAC setting. In the case of an over-voltage
event, the microprocessor core regulator attempts to
regulate the output voltage at the over-voltage threshold. It
also reports the condition through a high output on the
FAULT/RT pin.
In addition to the normal over-voltage operation, the
microprocessor core regulator has another very useful
protection feature presented in Figures 5 and 6. In case of a
power-up sequence with a shorted upper MOSFET, the
microprocessor can be destroyed without the protective
circuitry integrated into the HIP6020/21. An independent
functional block acts upon the lower gate driver, regulating
the core voltage to around 1.3V until the controller bias
voltage reaches power-on threshold. At this point normal
operation resumes, core voltage is regulated to 115% of the
DAC setting (2.0V in this case), and fault condition is
reported on the FAULT/RT pin.
Figure 5 exemplifies operation of the evaluation board
without the help of the ATX supply control circuit (Figure 3).
Initially the core voltage is held around 1.3V until the poweron threshold is reached (15ms till 50ms). Then the output
voltage is released to rise up to 115% of the DAC setting
(DAC = 2.0V). FAULT/RT goes high at this time signaling an
over-voltage condition. About 20ms later the 15A fuse (F1)
3
0
0
20
40
60
80
100
120 140 160
TIME (ms)
FIGURE 5. START-UP SEQUENCE WITH SHORTED Q1
(ATX CONTROL CIRCUIT BY-PASSED)
10
FAULT/RT
0
5
+12VIN
0
2
1
+5VIN
0
2
1
VCC_CORE
0
0
10
20
30
40
50
TIME (ms)
60
70
80
FIGURE 6. START-UP SEQUENCE WITH SHORTED Q1
(ATX CONTROL CIRCUIT ACTIVE)
UltraFET™ is a trademark of Intersil Corporation.
Application Note 9836
The practical implementation of the circuit is done on a twoounce four-layer printed circuit board. The two internal layers
are dedicated for ground and power planes. The layout is
compact and several additional footprints are provided for
increased evaluation flexibility. The component side of the
board contains two embedded serpentine resistors. One in
series with the drain of Q4 and Q5, approximately 220mΩ
and 200mΩ respectively. These resistors is not necessary
for the proper operation of the circuit; their role is simply to
share the power dissipation which otherwise would be
dissipated entirely by Q4 or Q5. Both serpentine resistors
can be removed by shorted them via two separate footprints
on the bottom of the EVAL boards. Contact Intersil for board
layout Gerber files.
only the core regulator efficiency, use Figure 7. The core
regulator design of the HIP6020 is identical to that of the
HIP6021.
92
Power MOSFETs
90
88
86
84
82
0
The power transistors utilized by HIP6020/21EVAL1 belong
to Intersil’ newest line of 30V UltraFET MOSFETs. Featuring
reduced rDS(ON) and low trr and Qrr, these transistors allow
for elimination of the traditional lower MOSFET anti-parallel
schottky.
Efficiency
Figure 7 displays the efficiency of the HIP6021EVAL1 core
regulator reference design versus load current. Laboratory
measurements were made with a 5V input and 100 linear
feet per minute (LFM) of airflow across the evaluation board.
The linear regulators are neglected since their efficiency is
not a figure of merit for the application circuit.
93
10
20
30
40
50
COMBINED SWITCHING CONVERTERS OUTPUT POWER [W]
FIGURE 8. HIP6021EVAL1 MEASURED CONVERTER
EFFICIENCY
Load Transient Response
HIP6020/21EVAL1 Performance
HIP6020EVAL1 response of the core voltage regulation to a
13.5A output step load transient is shown in Figure 9. An
Intel Slot 1 Test Tool provided the load transient which was
larger than the 9.5A design point. All other outputs are
subjected to the maximum transient loading conditions and
nominal output voltage settings as described in Table 1.
100
50
VCC_CORE
0
VCC_CORE = 2.0V
VOLTAGE (ms)
CONVERTER EFFICIENCY (%)
VCC_CORE = 2.0V
VCC_VDDQ = 1.5V
CONVERTER EFFICIENCY [%]
Printed Circuit Board
91
89
87
50
VCC_VDDQ
0
20
VCC_VTT
0
20
VCC_MCH
0
85
0
200
800
83
0
4
8
12
16
20
SWITCHING CONVERTER OUTPUT CURRENT (A)
FIGURE 7. HIP6021EVAL1 MEASURED CONVERTER
EFFICIENCY
Similarly, Figure 8 displays the efficiency obtained in the
HIP6020EVAL1 reference design. Since this evaluation
platform contains two switching regulators, both switching
regulator outputs were simultaneously loaded and
measured. The efficiency curve in Figure 8 represents a
composite result of the overall circuit efficiency plotted
against total converter output power. For those interested in
4
1200
1600
2000
TIME (μs)
FIGURE 9. HIP6020EVAL1 OUTPUT TRANSIENT RESPONSE
HIP6020/21EVAL1 Modifications
Input Capacitors Selection
In a DC/DC converter employing an input inductor, the input
RMS current is supplied entirely by the input capacitors. The
number of input capacitors is usually determined by their
maximum RMS current rating. The voltage rating at
maximum ambient temperature of the input capacitors
Application Note 9836
should be at least 1.25 to 1.5 times the maximum input
voltage. High frequency decoupling (highly recommended) is
implemented through the use of ceramic capacitors in
parallel with the bulk aluminum capacitor filtering. The
switching converter’s input RMS current is dependent on the
input and output voltages as well as the output current.
Figure 10 shows this approximate relationships for five
different levels of current. Based on the linearity of the
relationship, the graph results can be interpolated for
additional levels of output current. For output voltages
ranging from 2 to 3 volts, a good approximation of the input
RMS current is 1/2 the output current.
APPROXIMATE INPUT RMS CURRENT (A)
10
IOUT = 16A
8
IOUT = 14A
IOUT = 10A
4
2
0
R8
V VCC – VTT = 1.5V Þ ⎛ 1 + --------⎞
⎝
R9⎠
R10
V VCC – MCH = 1.8V Þ ⎛ 1 + -----------⎞
⎝
R11⎠
The HIP6021 gives the user the option to override the
internal resistors and adjust the output voltage based on the
chip’s internal bandgap voltage reference. By grounding the
FIX pin (pin 2), simple resistor value changes allow for
outputs as low as 1.3V or as high as the input voltage. The
steady-state DC output voltages can be set using the
following equations:
IOUT = 12A
6
The HIP6020 linear controller outputs (VCC_VTT and
VCC_MCH) are set by internal resistor dividers to 1.5V and
1.8V respectively. The output levels can be increased by
adding external resistors to the VSEN lines per the following
equations:
Note that the resistor values used should be no more than
5kΩ in total value. If this is not met, the internal resistor
values will induce some degree of offset in the output
voltages.
VIN = 5V
IOUT = 18A
out JP5 will allow the internal pullup to hold the SELECT pin
at a TTL high.
R9
V VCC – VTT = V REF Þ ⎛ 1 + -----------⎞
⎝
R10⎠
0
1
2
3
4
5
OUTPUT VOLTAGE (V)
FIGURE 10. SWITCHING CONVERTER RMS INPUT CURRENT
Using the above graph and the capacitor RMS current
rating, a minimum number of input capacitors can be easily
determined. If the time-averaged load is different than the
maximum load, the number of input capacitors may be
cautiously scaled down.
Output Voltages
The synchronous buck converter supplying the
microprocessor core voltage is controlled by the internal
DAC. Output voltage can be adjusted by selecting the
appropriate VID jumper combination. For more information
please refer to the HIP6020 or HIP6021 data sheet which
contains a very comprehensive table detailing all the VID
combinations and the resultant output voltages. If droop
implementation is desired, the no-load output voltage can be
determined from the following equation:
R11
V VCC – CLK = V REF Þ ⎛ 1 + -----------⎞ , where
⎝
R12⎠
Left open, the FIX pin is pulled high internally and the fixed
1.5V and 1.8V outputs are enabled.
Conclusion
The HIP6020/21EVAL1 board lends itself to a wide variety of
high-power DC-DC microprocessor converter designs. The
built-in flexibility allows the designer to quickly modify for
applications with various requirements, the printed circuit
board being laid out to accommodate the necessary
components for operation at currents up to 19A.
References
For Intersil documents available on the web, see
http://www.intersil.com/
[1] HIP6020 Data Sheet, Intersil Corporation, FN4683
R4 + R5
V VCC – CORE = V DAC Þ ⎛ 1 + ----------------------⎞
⎝
R7 ⎠
HIP6020EVAL1
R5 + R6
V VCC – CORE = V DAC Þ ⎛ 1 + ----------------------⎞
⎝
R8 ⎠
HIP6021EVAL1
where VDAC = DAC-set output voltage target.
The AGP bus voltage is controlled by the SELECT pin. A
TTL low inputs sets the internal resistor dividers for 1.5V
output and a TTL high sets the AGP output to 3.3V. Leaving
5
VREF = HIP6021 internal reference voltage (typically 1.267V)
[2] HIP6021 Data Sheet, Intersil Corporation, FN4684
[3] Slot 1 Test Kit, Intel # EUCDSLOTKIT1
Application Note 9836
HIP6020EVAL1 Schematic
+12VIN
F1
15A
+5VIN
L1
1μH
+
F2
SPARE
C1-7
7X1000μF
R1
750
C8
1μF
C9
1μF
GND
GND
VCC
R2
GND
OCSET2
28
9
R3
23
2.7K
Q3
HUF76107D3S
VCC_VDDQ TP2
(3.3V OR 1.5V)
8
R18
TP3
L2
68
6.2μH
+
C10-12
3x1000μF
UGATE2
PHASE2
27
2
26
VSEN2
SELECT
+3.3VIN
10
24
11
22
U1 21
HIP6020
JP5
C25 +
1000μF
3
2
JP6
VAUX
DRIVE3
TP6
(1.5V)
0
+
VSEN3
20
16
18
7
19
6
R9
SPARE
C28,29
2x1000μF
5
4
3
TP8
Q5
HUF76107D3S
DRIVE4
R10
VCC_MCH
(1.8V)
+
Q1,2
HUF76143S3S
UGATE1
TP4
LGATE1
VSEN4
0
R11
SPARE
C30,31
2x1000μF
12
VCC5
FB1
COMP1
VID0
R5
1.62K
C26
10pF
C24
0.22μF
C27
R6
R7
2.7nF
150K
499K
JP1
VID2
JP2
VID3
JP3
VID4
JP4
VID[1] VID[3]
VID[0] VID[2] VID[4]
SS
14
C32
0.1μF
13
17
13
FAULT/RT
R12
PB1
SHUTDOWN
100
R17
51K
R13
SPARE
CR2
R16
5.1K
1N4148
TP9
JP7
1
6
3 Q6A
2
1/2
RF1K49154
JP0
VID1
+5VSB
R15
5.1K
+
VSEN1
GND
TP9
C13-20
8x1000μF
R4
10.2K
PGND
TP7
15
+5VIN
PS-ON
TP5 VCC_CORE
(1.3V TO 3.5V)
L3
PHASE1
1
Q4
HUF76107D3S
R8
PWRGOOD
PGOOD
4.2μH
25
VCC_VTT
LP1
TP1
1K
1
CR1
MBRD835L
+5VIN
OCSET1
Q6B
1/2
RF1K49154
+12VIN
R14
SPARE
CONNECTIONS TO PROCESSOR SLOT1
AND ATX POWER CONNECTORS NOT
SHOWN FOR CLARITY
ALL ELECTRICAL CIRCUIT NODES
DENOTED BY THE SAME NAME ARE,
HOWEVER, GALVANICALLY CONNECTED
Application Note 9836
HIP6021EVAL1 Schematic
+12VIN
F1
15A
+5VIN
L1
1μH
PB1
F2
SPARE
+
SHUTDOWN
R2
50K
C7
1μF
C8
+3.3VIN
C1-6
6x1000μF
R1
750
C9
1μF
10nF
GND
GND
VCC
SD
GND
28
9
8
VCC_VDDQ
(3.3V OR 1.5V)
TP2
Q3
HUF76121D3S
DRIVE2
FIX
+
27
2
26
VSEN2
SELECT
10
24
11
22
U1 21
HIP6021
JP5
C24 +
1000μF
3
+5VIN
JP6
2
(1.5V)
0
+
VAUX
DRIVE3
TP5
R9
VSEN3
20
16
18
7
19
6
R10
SPARE
C27,28
2x1000μF
5
4
3
TP7
Q5
HUF76107D3S
DRIVE4
R11
VCC_MCH
(1.8V)
+
PWRGOOD
PGOOD
Q1,2
HUF76143S3S
UGATE1
TP3
TP4 VCC_CORE
(1.3V TO 3.5V)
L3
PHASE1
LGATE1
VSEN4
0
VSEN1
FB1
COMP1
12
17
GND
TP8
C23
0.22μF
C26
R7
R8
2.7nF
150K
499K
JP0
VID1
JP1
VID2
JP2
VID3
JP3
VID4
JP4
SS
14
+5VIN
VCC5
VID0
R6
1.62K
C25
10pF
TP6
15
R12
SPARE
C30,31
2x1000μF
+
C12-19
8x1000μF
R5
10.2K
PGND
1
Q4
HUF76107D3S
VCC_VTT
TP1
1K
4.2μH
25
+3.3VIN
OCSET1
1
R4
SPARE
C10,11
2x1000μF
LP1
R3
23
R17
51K
13
VID[1] VID[3]
C29
VID[0] VID[2] VID[4]
0.1μF
FAULT/RT
R13
R14
SPARE
+12VIN
SPARE
+5VSB
R15
5.1K
R16
5.1K
1N4148
TP9
PS-ON
CR1
JP7
1
7
3 Q6A
2
1/2
RF1K49154
Q6B
1/2
RF1K49154
CONNECTIONS TO PROCESSOR SLOT1
AND ATX POWER CONNECTORS NOT
SHOWN FOR CLARITY
ALL ELECTRICAL CIRCUIT NODES
DENOTED BY THE SAME NAME ARE,
HOWEVER, GALVANICALLY CONNECTED
Application Note 9836
Bill of Materials for HIP6020EVAL1
REF
PART #
DESCRIPTION
PACKAGE
QTY
VENDOR
C1-7,10-20, 25, 28-31 EEUFA1A10
Aluminum Capacitor, 10V, 1000μF
Radial 8x20
22
Panasonic
C8, 9
1206YZ105MAT1A
Ceramic Capacitor, X7S, 16V, 1.0μF
1206
2
AVX
C24
0.22μF Ceramic
Ceramic Capacitor, X7R, 16V
1206
1
AVX
C26
10pF Ceramic
Ceramic Capacitor, X7R, 25V
0805
1
Various
C27
2.7nF Ceramic
Ceramic Capacitor, X7R, 16V
0805
1
Various
C32
0.1μF Ceramic
Ceramic Capacitor, X7R, 16V
0805
1
Various
C21-23
Spares
CR1
MBRD835L
Schottky Rectifier
D-PAK
1
Motorola
CR2
1N4148
Silicon Rectifier, 100mA, 75V
DO-35
1
Motorola
F1
251015A
Miniature Fuse, 15A
Axial
1
Littelfuse
F2
spare
J1
71796-0005
145251-1
Slot 1 Edge Connector
1
Molex
AMP
J2
39-29-9203
20-pin Mini-Fit, Jr. Header Connector
1
Molex
JP0-4, 5, 7
68000-236
Jumper Header
0.1” spacing
15/36
Berg
71363-102
Jumper Shunt
0.1” spacing
7
Berg
JP6
19AWG
Jumper, Ni-Plated Copper Conductor
populated 1-2
L1
PO720
1μH Inductor, 7T of 16AWG on T50-52 Core
Wound Toroid
18x18x9
1
Pulse
L2
PO561
6.2μH Inductor, 12T of 19AWG on T44-52
Core
Wound Toroid
15x15x8
1
Pulse
4.2μH Inductor, 9T of 16AWG on T68-52A
Core
Wound Toroid
22x22x10
1
Radial 8x20
Axial
L3
LP1
L63111CT-ND
Miniature LED, Through-Board Indicator
1
Digikey
Q1, Q2
HUF76143S3S
UltraFET MOSFET, 30V, 5.5mΩ
TO-263AB
2
Intersil Corporation
Q3-5
HUF76107D3S
UltraFET MOSFET, 30V, 52mΩ
TO-252AA
3
Intersil Corporation
Q6
RF1K49154
MegaFET MOSFET, 60V, VGS(MIN) = 2V,
130mΩ
SO-8
1
Intersil Corporation
PB1
P8007S-ND
Push-Button, Miniature
1
Digikey
R1
750Ω
Resistor, 5%, 0.1W
0805
1
Various
R2
2.7kΩ
Resistor, 5%, 0.1W
0805
1
Various
R3
1kΩ
Resistor, 5%, 0.1W
0805
1
Various
R4
10.2kΩ
Resistor, 1%, 0.1W
0805
1
Various
R5
1.62kΩ
Resistor, 1%, 0.1W
0805
1
Various
R6
150kΩ
Resistor, 5%, 0.1W
0805
1
Various
R7
499kΩ
Resistor, 1%, 0.1W
0805
1
Various
R8,10
0Ω
Shorting Resistor, 0.1W
0805
2
Various
R12
100Ω
Resistor, 5%, 0.1W
0805
1
Various
R15,16
5.1kΩ
Resistor, 5%, 0.1W
0805
2
Various
R17
51kΩ
Resistor, 5%, 0.1W
0805
1
Various
R18
68Ω
Resistor, 5%, 0.1W
0805
1
Various
8
Application Note 9836
Bill of Materials for HIP6020EVAL1
REF
(Continued)
PART #
DESCRIPTION
PACKAGE
QTY
VENDOR
R9,11,13,14
Spares
TP1, 3, 4, 7, 9, 10
SPCJ-123-01
Test Point
6
Jolo
TP2, 5, 6, 8
1314353-00
Test Point, Scope Probe
4
Tektronics
U1
HIP6020CB
Dual PWM and Dual Linear Controller
1
Intersil Corporation
SJ-5003SP BLACK
BUMPON
5
3M
1514-2
Terminal Post
14
Keystone
+5V, +12V, +3.3V,
GND, VCC_CORE,
VCC_VDDQ,
VCC_VTT,
VCC_MCH
0805
SOIC-28
Bill of Materials for HIP6021EVAL1
REF
PART #
DESCRIPTION
PACKAGE
QTY
VENDOR
C1-6,10-19, 24, 27,
28, 30, 31
EEUFA1A10
Aluminum Capacitor, 10V, 1000μF
Radial 8x20
20
Panasonic
C7,9
1206YZ105MAT1A
Ceramic Capacitor, X7S, 16V, 1.0μF
1206
2
AVX
C8
10nF Ceramic
Ceramic Capacitor, X7R, 25V
0805
1
Various
C23
0.22μF Ceramic
Ceramic Capacitor, X7R, 16V
1206
1
AVX
C25
10pF Ceramic
Ceramic Capacitor, X7R, 25V
0805
1
Various
C26
2.7nF Ceramic
Ceramic Capacitor, X7R, 16V
0805
1
Various
C29
0.1μF Ceramic
Ceramic Capacitor, X7R, 16V
0805
1
Various
C20-22
spares
CR1
1N4148
Silicon Rectifier, 100mA, 75V
DO-35
1
Motorola
F1
251015A
Miniature Fuse, 15A
Axial
1
Littelfuse
F2
spare
J1
71796-0005
145251-1
Slot 1 Edge Connector
1
Molex
AMP
J2
39-29-9203
20-pin Mini-Fit, Jr. Header Connector
1
Molex
JP0-4, 5, 7
68000-236
Jumper Header
0.1” spacing
15/36
Berg
71363-102
Jumper Shunt
0.1” spacing
7
Berg
JP6
19AWG
Jumper, Ni-Plated Copper Conductor
populated 1-2
L1
PO720
1μH Inductor, 7T of 16AWG on T50-52 Core
Wound Toroid
18x18x9
1
Pulse
4.2μH Inductor, 9T of 16AWG on T68-52A
Core
Wound Toroid
22x22x10
1
Radial 8x20
Axial
L3
LP1
L63111CT-ND
LED, Through-Board Indicator
1
Digikey
Q1, Q2
HUF76143S3S
UltraFET MOSFET, 30V, 5.5mΩ
TO-263AB
2
Intersil Corporation
Q3
HUF76121D3S
UltraFET MOSFET, 30V, 21mΩ
TO-252AA
1
Intersil Corporation
Q4, 5
HUF76107D3S
UltraFET MOSFET, 30V, 52mΩ
TO-252AA
2
Intersil Corporation
Q6
RF1K49154
MegaFET MOSFET, 60V, VGS(MIN) = 2V,
130mΩ
SO-8
1
Intersil Corporation
PB1
P8007S-ND
Push-Button, Miniature
1
Digikey
9
Application Note 9836
Bill of Materials for HIP6021EVAL1
REF
(Continued)
PART #
DESCRIPTION
PACKAGE
QTY
VENDOR
R1
750Ω
Resistor, 5%, 0.1W
0805
1
Various
R2
51kΩ
Resistor, 5%, 0.1W
0805
1
Various
R3
1kΩ
Resistor, 5%, 0.1W
0805
1
Various
R5
10.2kΩ
Resistor, 1%, 0.1W
0805
1
Various
R6
1.62kΩ
Resistor, 1%, 0.1W
0805
1
Various
R7
150kΩ
Resistor, 5%, 0.1W
0805
1
Various
R8
499kΩ
Resistor, 1%, 0.1W
0805
1
Various
R9,11
0Ω
Shorting Resistor, 0.1W
0805
2
Various
R15,16
5.1kΩ
Resistor, 5%, 0.1W
0805
2
Various
R17
51kΩ
Resistor, 5%, 0.1W
0805
1
Various
R10,12-14
Spares
TP1, 3, 6, 8, 9
SPCJ-123-01
Test Point
5
Jolo
TP2, 4, 5, 7
1314353-00
Test Point, Scope Probe
4
Tektronics
U1
HIP6021CB
PWM and Triple Linear Controller
1
Intersil Corporation
SJ-5003SP BLACK
BUMPON
5
3M
1514-2
Terminal Post
14
Keystone
+5V, +12V, +3.3V,
GND, VCC_CORE,
VCC_VDDQ,
VCC_VTT,
VCC_MCH
0805
SOIC-28
All Intersil semiconductor products are manufactured, assembled and tested under ISO9000 quality systems certification.
Intersil semiconductor products are sold by description only. Intersil Corporation reserves the right to make changes in circuit design and/or specifications at any time without notice. Accordingly, the reader is cautioned to verify that data sheets are current before placing orders. Information furnished by Intersil is believed to be accurate and
reliable. However, no responsibility is assumed by Intersil or its subsidiaries for its use; nor for any infringements of patents or other rights of third parties which may result
from its use. No license is granted by implication or otherwise under any patent or patent rights of Intersil or its subsidiaries.
For information regarding Intersil Corporation and its products, see web site http://www.intersil.com
10
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