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Data Sheet
May 19, 2006
DATASHEET
EL2250, EL2450
125MHz Single Supply Dual/Quad Op Amps
Features
The EL2250/EL2450 are part of a family of the electronics
industry’s fastest single supply op amps available. Prior
single supply op amps have generally been limited to
bandwidths and slew rates to that of the EL2250/EL2450.
The 125MHz bandwidth, 275V/µs slew rate, and
0.05%/0.05° differential gain/differential phase makes this
part ideal for single or dual supply video speed applications.
With its voltage feedback architecture, this amplifier can
accept reactive feedback networks, allowing them to be
used in analog filtering applications. The inputs can sense
signals below the bottom supply rail and as high as 1.2V
below the top rail. Connecting the load resistor to ground
and operating from a single supply, the outputs swing
completely to ground without saturating. The outputs can
also drive to within 1.2V of the top rail. The EL2250/EL2450
will output ±100mA and will operate with single supply
voltages as low as 2.7V, making them ideal for portable, low
power applications.
• Specified for +3V, +5V, or ±5V applications
The EL2250/EL2450 are available in PDIP and SO
packages in industry standard pin outs. Both parts operate
over the industrial temperature range of -40°C to +85°C, and
are part of a family of single supply op amps. For single
amplifier applications, see the EL2150/EL2157. For dual and
triple amplifiers with power down and output voltage clamps,
see the EL2257/EL2357.
FN7061.3
• Large input common mode range
0V < VCM < VS -1.2V
• Output swings to ground without saturating
• -3dB bandwidth = 125MHz
• ±0.1dB bandwidth = 30MHz
• Low supply current = 5mA (per amplifier)
• Slew rate = 275V/µs
• Low offset voltage = 4mV max
• Output current = ±100mA
• High open loop gain = 80dB
• Differential gain = 0.05%
• Differential phase = 0.05°
• Pb-free plus anneal available (RoHS compliant)
Applications
• Video amplifiers
• PCMCIA applications
• A/D drivers
• Line drivers
Ordering Information
• Portable computers
PART NUMBER
PART
TAPE &
MARKING REEL PACKAGE
PKG.
DWG. #
• High speed communications
EL2250CN
EL2250CN
-
8 Ld PDIP
MDP0031
• RGB printers, FAX, scanners
EL2250CS
2250CS
-
8 Ld SO
MDP0027
• Broadcast equipment
EL2250CS-T7
2250CS
7”
8 Ld SO
MDP0027
EL2250CS-T13
2250CS
13”
8 Ld SO
MDP0027
EL2250CSZ
(Note)
2250CSZ
-
8 Ld SO
(Pb-free)
MDP0027
EL2250CSZ-T7
(Note)
2250CSZ
7”
8 Ld SO
(Pb-free)
MDP0027
EL2250CSZ-T13 2250CSZ
(Note)
13”
8 Ld SO
(Pb-free)
MDP0027
EL2450CN
EL2450CN
-
14 Ld PDIP MDP0031
EL2450CS
2450CS
-
14 Ld SO
MDP0027
EL2450CS-T7
2450CS
7”
14 Ld SO
MDP0027
EL2450CS-T13
2450CS
13”
14 Ld SO
MDP0027
• Active filtering
NOTE: Intersil Pb-free plus anneal products employ special Pb-free
material sets; molding compounds/die attach materials and 100%
matte tin plate termination finish, which are RoHS compliant and
compatible with both SnPb and Pb-free soldering operations. Intersil
Pb-free products are MSL classified at Pb-free peak reflow
temperatures that meet or exceed the Pb-free requirements of
IPC/JEDEC J STD-020.
1
CAUTION: These devices are sensitive to electrostatic discharge; follow proper IC Handling Procedures.
1-888-INTERSIL or1-888-468-3774 | Intersil (and design) is a registered trademark of Intersil Americas Inc.
Copyright © Intersil Americas Inc. 2002-2006. All Rights Reserved.
All other trademarks mentioned are the property of their respective owners.
EL2250, EL2450
Pinouts
EL2450
(14 LD SO, PDIP)
TOP VIEW
EL2250C
(8 LD SO, PDIP)
TOP VIEW
OUTA
1
INA-
2
INA+
3
GND
4
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A
+
B
2
+
OUTA
1
OUTB
INA-
2
6
INB-
INA+
3
12 IND+
5
INB+
VS+
4
11 GND
INB+
5
8
VS+
7
INB-
6
OUTB
7
14 OUTD
A
- +
D
+ -
13 IND-
10 INC+
- +
B
+ C
9
INC-
8
OUTC
FN7061.3
May 19, 2006
EL2250, EL2450
Absolute Maximum Ratings (TA = 25°C)
Power Dissipation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . See Curves
Storage Temperature Range . . . . . . . . . . . . . . . . . .-65°C to +150°C
Ambient Operating Temperature Range . . . . . . . . . .-40°C to +85°C
Operating Junction Temperature . . . . . . . . . . . . . . . . . . . . . . . 150°C
Supply Voltage between VS and GND . . . . . . . . . . . . . . . . . . +12.6V
Input Voltage (IN+, IN-) . . . . . . . . . . . . . . . . . . . GND-0.3V,VS+0.3V
Differential Input Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .±6V
Maximum Output Current. . . . . . . . . . . . . . . . . . . . . . . . . . . . . 90mA
Output Short Circuit Duration. . . . . . . . . . . . . . . . . . . . . . . . (Note 1)
CAUTION: Stresses above those listed in “Absolute Maximum Ratings” may cause permanent damage to the device. This is a stress only rating and operation of the
device at these or any other conditions above those indicated in the operational sections of this specification is not implied.
IMPORTANT NOTE: All parameters having Min/Max specifications are guaranteed. Typical values are for information purposes only. Unless otherwise noted, all tests
are at the specified temperature and are pulsed tests, therefore: TJ = TC = TA
DC Electrical Specifications VS = +5V, GND = 0V, TA = 25°C, VCM = 1.5V, VOUT = 1.5V, unless otherwise specified.
PARAMETER
DESCRIPTION
TEST CONDITIONS
VOS
Offset Voltage
TCVOS
Offset Voltage Temperature Coefficient
Measured from TMIN to TMAX
IB
Input Bias Current
VIN = 0V
IOS
Input Offset Current
VIN = 0V
TCIOS
Input Bias Current Temperature Coefficient Measured from TMIN to TMAX
PSRR
Power Supply Rejection Ratio
VS = +2.7V to +12V
CMRR
Common Mode Rejection Ratio
MIN
TYP
MAX
UNIT
12
mV
-12
10
-1200
µV/°C
-5.5
-10
µA
150
1200
nA
50
nA/°C
55
70
dB
VCM = 0V to +3.8V
45
65
dB
VCM = 0V to +3.0V
50
70
dB
CMIR
Common Mode Input Range
0
RIN
Input Resistance
Common Mode
CIN
Input Capacitance
SO Package
1
VS-1.2
V
2
M
1
pF
PDIP Package
1.5
pF
m
ROUT
Output Resistance
AV = +1
40
IS
Supply Current (per amplifier)
VS = +12V
5
PSOR
Power Supply Operating Range
2.7
6.5
mA
12.0
V
DC Electrical Specifications VS = +5V, GND = 0V, TA = 25°C, VCM = +1.5V, VOUT = +1.5V, unless otherwise specified.
PARAMETER
AVOL
VOP
DESCRIPTION
Open Loop Gain
Positive Output
Voltage Swing
TEST CONDITIONS
MIN
TYP
VS = +12V, VOUT = +2V to +9V, RL = 1k to GND
60
80
dB
VOUT = +1.5V to +3.5V, RL = 1k to GND
70
dB
VOUT = +1.5V to +3.5V, RL = 150 to GND
60
dB
10.8
V
10.0
V
4.0
V
VS = +12V, AV = +1, RL = 1k to 0V
VS = +12V, AV = +1, RL = 150 to 0V
9.6
VS = ±5V, AV = +1, RL = 1k to 0V
VON
IOUT
Negative Output
Voltage Swing
Output Current (Note 1)
MAX
UNIT
VS = ±5V, AV = +1, RL = 150 to 0V
3.4
3.8
V
VS = +3V, AV = +1, RL = 150 to 0V
1.8
1.95
V
VS = +12V, AV = +1, RL = 150 to 0V
5.5
V S = ±5V, AV = +1, RL = 1k to 0V
-4.0
VS = ±5V, AV = +1, RL = 150 to 0V
-3.7
VS = ±5V, AV = +1, RL = 10 to 0V
±75
±100
8
mV
V
-3.4
V
mA
VS = ±5V, AV = +1, RL = 50 to 0V ±60VmA
NOTE:
1. Internal short circuit protection circuitry has been built into the EL2250/EL2450; see the Applications section
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3
FN7061.3
May 19, 2006
EL2250, EL2450
AC Electrical Specifications VS = +5V, GND = 0V, TA = 25°C, VCM = +1.5V, VOUT = +1.5V, AV = +1, RF = 0, RL = 150 to GND pin,
unless otherwise specified. (Note 1)
PARAMETER
BW
BW
DESCRIPTION
-3dB Bandwidth
(VOUT = 400mVP-P)
±0.1dB Bandwidth
(VOUT = 400mVP-P)
TEST CONDITIONS
MIN
TYP
MAX
UNIT
VS = +5V, AV = +1, RF = 0
125
MHz
VS = +5V, AV = -1, RF = 500
60
MHz
VS = +5V, AV = +2, RF = 500
60
MHz
VS = +5V, AV = +10, RF = 500
6
MHz
VS = +12V, AV = +1, RF = 0
150
MHz
VS = +3V, AV = +1, RF = 0
100
MHz
VS = +12V, AV = +1, RF = 0
25
MHz
VS = +5V, AV = +1, RF = 0
30
MHz
VS = +3V, AV = +1, RF = 0
20
MHz
GBWP
Gain Bandwidth Product
VS = +12V, @ AV = +10
60
MHz
PM
Phase Margin
RL = 1k, CL = 6pF
55
°
SR
Slew Rate
VS = +10V, RL = 150, VOUT = 0V to +6V
275
V/µs
VS = +5V, RL = 150, VOUT = 0V to +3V
300
V/µs
200
tR, tF
Rise Time, Fall Time
±0.1V Step
2.8
ns
OS
Overshoot
±0.1V Step
10
%
tPD
Propagation Delay
±0.1V Step
3.2
ns
tS
0.1% Settling Time
VS = ±5V, RL = 500, AV = +1, VOUT = ±3V
40
ns
0.01% Settling Time
VS = ±5V, RL = 500, AV = +1, VOUT = ±3V
75
ns
dG
Differential Gain (Note 2)
AV = +2, RF = 1k
0.05
%
dP
Differential Phase (Note 2)
AV = +2, RF = 1k
0.05
°
eN
Input Noise Voltage
f = 10kHz
48
nV/Hz
iN
Input Noise Current
f = 10kHz
1.25
pA/Hz
NOTES:
1. All AC tests are performed on a “warmed up” part, except slew rate, which is pulse tested.
2. Standard NTSC signal = 286mVP-P, f = 3.58MHz, as VIN is swept from 0.6V to 1.314V; RL is DC coupled.
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FN7061.3
May 19, 2006
EL2250, EL2450
Typical Performance Curves
Non-Inverting Frequency
Response (Gain)
Inverting Frequency Response
(Gain)
Frequency Response for Various RL
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5
Non-Inverting Frequency
Response (Phase)
Inverting Frequency Response
(Phase)
Frequency Response for Various CL
3dB Bandwidth vs Temperature for
Non-Inverting Gains
3dB Bandwidth vs Temperature for
Inverting Gains
Non-Inverting Frequency
Response vs Common Mode
Voltage
FN7061.3
May 19, 2006
EL2250, EL2450
Typical Performance Curves (Continued)
3dB Bandwidth vs Supply Voltage
for Non-Inverting Gains
Frequency Response for Various
Supply Voltages, AV = + 1
PSSR and CMRR vs Frequency
3dB Bandwidth vs Supply Voltage
for Inverting Gains
Frequency Response for Various
Supply Voltages, AV = + 2
PSRR and CMRR vs Die
Temperature
Open Loop Gain and Phase vs
Frequency
Open Loop Voltage Gain vs Die
Temperature
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Closed Loop Output Impedance vs
Frequency
FN7061.3
May 19, 2006
EL2250, EL2450
Typical Performance Curves
(Continued)
Large Signal Step Response, VS = +3V
Large Signal Step Response, VS = +5V
Small Signal Step Response
Slew Rate vs Temperature
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Large Signal Step Response, VS = +12V
Large Signal Step Response, VS = ±5V
Settling Time vs Settling Accuracy
Voltage and Current Noise vs
Frequency
FN7061.3
May 19, 2006
EL2250, EL2450
Typical Performance Curves
(Continued)
Differential Gain for
Single Supply Operation
Differential Phase for
Single Supply Operation
Differential Gain and Phase
for Dual Supply Operation
2nd and 3rd Harmonic Distortion
vs Frequency
2nd and 3rd Harmonic Distortion
vs Frequency
2nd and 3rd Harmonic Distortion
vs Frequency
Output Voltage Swing vs
Frequency for THD < 0.1%
Output Voltage Swing vs
Frequency for Unlimited Distortion
Output Current vs Die Temperature
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8
FN7061.3
May 19, 2006
EL2250, EL2450
Typical Performance Curves
(Continued)
Supply Current vs Supply Voltage
(per amplifier)
Supply Current vs Die
Temperature (per amplifier)
Offset Voltage vs Die Temperature
(4 Samples)
Input Bias Current vs Input Voltage
Input Offset Current and Input Bias
Current vs Die Temperature
Positive Output Voltage Swing vs
Die Temperature, RL = 150 to
GND
Negative Output Voltage Swing vs
Die Temperature, RL = 150 to
GND
Channel to Channel Isolation vs
Frequency
1.8
Package Power Dissipation vs Ambient Temp.
SEMI G42-88 Single Layer Test Board
1.2
JA
1
PD
=8 IP1
1° 4
C/
W
Power Dissipation (W)
Power Dissipation (W)

1.4 1.25W
1.2
J
PD
A =1 IP8
00
°C
/W
0.8
Package Power Dissipation vs Ambient Temp.
JEDEC JESD51-3 Low Effective Thermal Conductivity
Test Board
1.042W
1.6 1.54W
1
Input Resistance vs Die
Temperature
0.6
0.4
SO
781W
0.8
SO
8
0.6
JA =
1
0.4
14

JA
=1
20
°C
/W
60
°C
/W
0.2
0.2
0
0
0
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25
50
75 85 100
Ambient Temperature (°C)
9
125
150
0
25
50
75 85 100
Ambient Temperature (°C)
125
150
FN7061.3
May 19, 2006
EL2250, EL2450
Simplified Schematic
Applications Information
Product Description
The EL2250/EL2450 are part of a family of the industries
fastest single supply operational amplifiers. Connected in
voltage follower mode, their -3dB bandwidth is 125MHz
while maintaining a 275V/µs slew rate. With an input and
output common mode range that includes ground, these
amplifiers were optimized for single supply operation, but will
also accept dual supplies. They operate on a total supply
voltage range as low as +2.7V or up to +12V. This makes
them ideal for +3V applications, especially portable
computers.
While many amplifiers claim to operate on a single supply,
and some can sense ground at their inputs, most fail to truly
drive their outputs to ground. If they do succeed in driving to
ground, the amplifier often saturates, causing distortion and
recovery delays. However, special circuitry built into the
EL2250/EL2450 allows the output to follow the input signal
to ground without recovery delays.
Power Supply Bypassing And Printed Circuit
Board Layout
As with any high-frequency device, good printed circuit
board layout is necessary for optimum performance. Ground
plane construction is highly recommended. Lead lengths
should be as short as possible. The power supply pins must
be well bypassed to reduce the risk of oscillation. The
combination of a 4.7µF tantalum capacitor in parallel with a
0.1µF ceramic capacitor has been shown to work well when
placed at each supply pin. For single supply operation,
where the GND pin is connected to the ground plane, a
single 4.7µF tantalum capacitor in parallel with a 0.1µF
ceramic capacitor across the VS+ and GND pins will suffice.
For good AC performance, parasitic capacitance should be
kept to a minimum. Ground plane construction should be
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10
used. Carbon or Metal-Film resistors are acceptable with the
Metal-Film resistors giving slightly less peaking and
bandwidth because of their additional series inductance. Use
of sockets, particularly for the SO package should be
avoided if possible. Sockets add parasitic inductance and
capacitance which will result in some additional peaking and
overshoot.
Supply Voltage Range and Single-Supply
Operation
The EL2250/EL2450 have been designed to operate with
supply voltages having a span of greater than 2.7V, and less
than 12V. In practical terms, this means that the
EL2250/EL2450 will operate on dual supplies ranging from
±1.35V to ±6V. With a single-supply, the EL2250/EL2450 will
operate from +2.7V to +12V. Performance has been
optimized for a single +5V supply.
Pins 8 and 4 are the power supply pins on the EL2250. The
positive power supply is connected to pin 8. When used in
single supply mode, pin 4 is connected to ground. When
used in dual supply mode, the negative power supply is
connected to pin 4.
Pins 4 and 11 are the power supply pins on the EL2450. The
positive power supply is connected to pin 4. When used in
single supply mode, pin 11 is connected to ground. When
used in dual supply mode, the negative power supply is
connected to pin 11.
As supply voltages continue to decrease, it becomes
necessary to provide input and output voltage ranges that
can get as close as possible to the supply voltages. The
EL2250/EL2450 have an input voltage range that includes
the negative supply and extends to within 1.2V of the
positive supply. So, for example, on a single +5V supply, the
EL2250/EL2450 have an input range which spans from 0V to
3.8V.
FN7061.3
May 19, 2006
EL2250, EL2450
The output range of the EL2250/EL2450 is also quite large.
It includes the negative rail, and extends to within 1V of the
top supply rail with a 1k load. On a +5V supply, the output
is therefore capable of swinging from 0V to +4V. On split
supplies, the output will swing ±4V. If the load resistor is tied
to the negative rail and split supplies are used, the output
range is extended to the negative rail.
Choice Of Feedback Resistor, RF
The feedback resistor forms a pole with the input
capacitance. As this pole becomes larger, phase margin is
reduced. This increases ringing in the time domain and
peaking in the frequency domain. Therefore, RF has some
maximum value which should not be exceeded for optimum
performance. If a large value of RF must be used, a small
capacitor in the few picofarad range in parallel with RF can
help to reduce this ringing and peaking at the expense of
reducing the bandwidth.
As far as the output stage of the amplifier is concerned,
RF + RG appear in parallel with RL for gains other than +1.
As this combination gets smaller, the bandwidth falls off.
Consequently, RF has a minimum value that should not be
exceeded for optimum performance.
For AV = +1, RF = 0 is optimum. For AV = -1 or +2 (noise
gain of 2), optimum response is obtained with RF between
500 and 1k. For AV = -4 or +5 (noise gain of 5), keep RF
between 2k and 10k.
Video Performance
For good video performance, an amplifier is required to
maintain the same output impedance and the same
frequency response as DC levels are changed at the output.
This can be difficult when driving a standard video load of
150, because of the change in output current with DC level.
Differential Gain and Differential Phase for the
EL2250/EL2450 are specified with the black level of the
output video signal set to +1.2V. This allows ample room for
the sync pulse even in a gain of +2 configuration. This
results in dG and dP specifications of 0.05% and 0.05° while
driving 150 at a gain of +2. Setting the black level to other
values, although acceptable, will compromise peak
performance. For example, looking at the single supply dG
and dP curves for RL = 150, if the output black level clamp
is reduced from 1.2V to 0.6V dG/dP will increase from
0.05%/0.05° to 0.08%/0.25° Note that in a gain of +2
configuration, this is the lowest black level allowed such that
the sync tip doesn’t go below 0V.
If your application requires that the output goes to ground,
then the output stage of the EL2250/EL2450, like all other
single supply op amps, requires an external pull down
resistor tied to ground. As mentioned above, the current
flowing through this resistor becomes the DC bias current for
the output stage NPN transistor. As this current approaches
zero, the NPN turns off, and dG and dP will increase. This
becomes more critical as the load resistor is increased in
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11
value. While driving a light load, such as 1k, if the input
black level is kept above 1.25V, dG and dP are a respectable
0.03% and 0.03°.
For other biasing conditions see the Differential Gain and
Differential Phase vs. Input Voltage curves.
Output Drive Capability
In spite of their moderately low 5mA of supply current, the
EL2250/EL2450 are capable of providing ±100mA of output
current into a 10 load, or ±60mA into 50. With this large
output current capability, a 50 load can be driven to ±3V
with VS = ±5V, making it an excellent choice for driving
isolation transformers in telecommunications applications.
Driving Cables and Capacitive Loads
When used as a cable driver, double termination is always
recommended for reflection-free performance. For those
applications, the back-termination series resistor will decouple the EL2250/EL2450 from the cable and allow
extensive capacitive drive. However, other applications may
have high capacitive loads without a back-termination
resistor. In these applications, a small series resistor (usually
between 5 and 50) can be placed in series with the
output to eliminate most peaking. The gain resistor (RG) can
then be chosen to make up for any gain loss which may be
created by this additional resistor at the output.
Video Sync Pulse Remover Application
All CMOS Analog to Digital Converters (A/Ds) have a
parasitic latch-up problem when subjected to negative input
voltage levels. Since the sync tip contains no useful video
information and it is a negative going pulse, we can chop it
off.
Figure 1 shows a unity gain connected amplifier A of an
EL2250. Figure 2 shows the complete input video signal
applied at the input, as well as the output signal with the
negative going sync pulse removed.
FIGURE 1.
FN7061.3
May 19, 2006
EL2250, EL2450
The maximum power dissipation allowed in a package is
determined according to [1]:
T JMAX – T AMAX
PD MAX = -------------------------------------------- JA
where:
TJMAX = Maximum Junction Temperature
TAMAX = Maximum Ambient Temperature
FIGURE 2.
Short Circuit Current Limit
The EL2250/EL2450 have internal short circuit protection
circuitry that protect it in the event of its output being shorted
to either supply rail. This limit is set to around 100mA
nominally and reduces with increasing junction temperature.
It is intended to handle temporary shorts. If an output is
shorted indefinitely, the power dissipation could easily
increase such that the part will be destroyed. Maximum
reliability is maintained if the output current never exceeds
±90mA. A heat sink may be required to keep the junction
temperature below absolute maximum when an output is
shorted indefinitely.
Power Dissipation
JA = Thermal Resistance of the Package
PDMAX = Maximum Power Dissipation in the Package.
The maximum power dissipation actually produced by an IC
is the total quiescent supply current times the total power
supply voltage, plus the power in the IC due to the load, or
[2]:
V OUT

PD MAX = N   V s  I SMAX +  V S – V OUT   ----------------
RL 

where:
N = Number of amplifiers
VS = Total Supply Voltage
ISMAX = Maximum Supply Current per amplifier
With the high output drive capability of the EL2250/EL2450,
it is possible to exceed the 150°C Absolute Maximum
junction temperature under certain load current conditions.
Therefore, it is important to calculate the maximum junction
temperature for the application to determine if power-supply
voltages, load conditions, or package type need to be
modified for the EL2250/EL2450 to remain in the safe
operating area.
VOUT = Maximum Output Voltage of the Application
RL = Load Resistance tied to Ground
If we set the two PDMAX equations, [1] & [2], equal to each
other, and solve for VS, we can get a family of curves for
various loads and output voltages according to [3]:
R L   T JMAX – T AMAX 
--------------------------------------------------------------- +  V OUT 
N   JA
V S = ------------------------------------------------------------------------------------------ IS  R L  + V OUT
Figures 3 through 6 below show total single supply voltage
VS vs. RL for various output voltage swings for the PDIP and
SO packages. The curves assume WORST CASE
conditions of TA = +85°C and IS = 6.5mA per amplifier.
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FN7061.3
May 19, 2006
EL2250, EL2450
EL2250 Single Supply Voltage vs
RLOAD for Various VOUT (PDIP
Package)
FIGURE 3.
EL2250 Single Supply Voltage vs
RLOAD for Various VOUT (SO
Package)
FIGURE 4.
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EL2450 Single Supply Voltage vs
RLOAD for Various VOUT (PDIP
Package)
FIGURE 5.
EL2450 Single Supply Voltage vs
RLOAD for Various VOUT (SO
Package)
FIGURE 6.
FN7061.3
May 19, 2006
EL2250, EL2450
EL2250/EL2450 Macromodel (one amplifier)
* Revision A, April 1996
* Pin numbers reflect a standard single op amp.
* Connections:
+input
*
|
-input
*
|
|
+Vsupply
*
|
|
|
-Vsupply
*
|
|
|
|
output
.subckt EL2250/el 3 2 7 4 6
*
* Input Stage
*
i1 7 10 250µA
i2 7 11 250µA
r1 10 11 4k
q1 12 2 10 qp
q2 13 3 11 qpa
r2 12 4 100
r3 13 4 100
*
* Second Stage & Compensation
*
gm 15 4 13 12 4.6m
r4 15 4 15Meg
c1 15 4 0.36pF
*
* Poles
*
e1 17 4 15 4 1.0
r6 17 25 400
c3 25 4 1pF
r7 25 18 500
c4 18 4 1pF
*
* Output Stage
*
i3 20 4 1.0mA
q3 7 23 20 qn
q4 7 18 19 qn
q5 7 18 21 qn
q6 4 20 22 qp
q7 7 23 18 qn
d1 19 20 da
r8 21 6 2
r9 22 6 2
r10 18 21 10k
r11 7 23 100k
d2 23 24 da
d3 24 4 da
d4 23 18 da
*
* Power Supply Current
*
ips 7 4 3.2mA
*
* Models
*
.model qn npn(is=800e-18 bf=150 tf=0.02nS)
.model qpa pnp(is=810e-18 bf=50 tf=0.02nS)
.model qp pnp(is=800e-18 bf=54 tf=0.02nS)
.model da d(tt=0nS)
.ends
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FN7061.3
May 19, 2006
EL2250, EL2450
EL2250/EL2450 Macromodel (one amplifier)
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in the quality certifications found at www.intersil.com/en/support/qualandreliability.html
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FN7061.3
May 19, 2006
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