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RECOM
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EL2360
®
June 1996, Rev A
Triple 130MHz Current Feedback Amplifier
Features
The EL2360 is a triple currentfeedback operational amplifier which
achieves a -3dB bandwidth of 130MHz
at a gain of +2. Built using the Elantec proprietary monolithic
complementary bipolar process, these amplifiers use current
mode feedback to achieve more bandwidth at a given gain
than a conventional voltage feedback amplifier.
• Triple amplifier topology
The EL2360 is designed to drive a double terminated 75Ω
coax cable to video levels. It’s fast slew rate of 1500V/µs,
combined with the triple amplifier topology, makes its ideal
for RGB video applications.
This amplifier can operate on any supply voltage from 4V
(±2V) to 33V (±16.5V), yet consume only 8mA per amplifier
at any supply voltage. The EL2360 is available in 16-pin
PDIP and SOIC packages.
For Single, Dual, or Quad applications, consider the EL2160,
EL2260, or EL2460 all in industry standard pin outs. For
Single applications with a power down feature, consider the
EL2166.
FN7065.0
• 130MHz -3dB bandwidth (AV=+2)
• 180MHz -3dB bandwidth (AV=+1)
• Wide supply range, ±2V to ±15V
• 80mA output current (peak)
• Low cost
• 1500V/µs slew rate
• Input common mode range to within 1.5V of supplies
• 35ns settling time to 0.1%
• Available in single (EL2160), dual (EL2260), and quad
(EL2460) form
Applications
• RGB amplifiers
• Video amplifiers
• Cable driver
• Test equipment amplifiers
Pinout
• Current to voltage converters
EL2360
(16-PIN SO, PDIP)
TOP VIEW
• Video broadcast equipment
Ordering Information
PART
NUMBER
1
TEMP. RANGE
PACKAGE
PKG. NO.
EL2360CN
-40°C to +85°C
16-Pin PDIP
MDP0031
EL2360CS
-40°C to +85°C
16-Pin SOIC
MDP0027
CAUTION: These devices are sensitive to electrostatic discharge; follow proper IC Handling Procedures.
1-888-INTERSIL or 321-724-7143 | Intersil (and design) is a registered trademark of Intersil Americas Inc.
Copyright © Intersil Americas Inc. 2003. All Rights Reserved. Elantec is a registered trademark of Elantec Semiconductor, Inc.
All other trademarks mentioned are the property of their respective owners.
EL2360
Absolute Maximum Ratings (TA = 25°C)
Voltage between VS+ and VS-. . . . . . . . . . . . . . . . . . . . . . . . . .+33V
Common-Mode Input Voltage . . . . . . . . . . . . . . . . . . . . . VS- to VS+
Differential Input Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .±6V
Current into +IN or -IN . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . ±10mA
Internal Power Dissipation . . . . . . . . . . . . . . . . . . . . . . . See Curves
Output Current (continuous) . . . . . . . . . . . . . . . . . . . . . . . . . ±50mA
Operating Ambient Temperature Range . . . . . . . . . .-40°C to +85°C
Operating Junction Temperature . . . . . . . . . . . . . . . . . . . . . . . 150°C
Storage Temperature Range . . . . . . . . . . . . . . . . . .-65°C to +150°C
CAUTION: Stresses above those listed in “Absolute Maximum Ratings” may cause permanent damage to the device. This is a stress only rating and operation of the
device at these or any other conditions above those indicated in the operational sections of this specification is not implied.
IMPORTANT NOTE: All parameters having Min/Max specifications are guaranteed. Typical values are for information purposes only. Unless otherwise noted, all tests
are at the specified temperature and are pulsed tests, therefore: TJ = TC = TA
DC Electrical Specifications
PARAMETER
VS = ±15V, RL=150Ω, TA=25°C unless otherwise specified.
DESCRIPTION
CONDITIONS
MIN
TYP
MAX
UNITS
2
10
mV
VOS
Input Offset Voltage
TCVOS
Average Input Offset Voltage Drift (Note 1)
+IIN
+Input Current
VS = ±5V, ±15V
0.5
3
µA
-IIN
-Input Current
VS = ±5V, ±15V
5
25
µA
CMRR
Common Mode Rejection Ratio (Note 2)
VS = ±5V, ±15V
-ICMR
-Input Current Common Mode Rejection
(Note 2)
VS = ±5V, ±15V
PSRR
Power Supply Rejection Ratio (Note 3)
-IPSR
-Input Current Power Supply Rejection
(Note 3)
ROL
Transimpedance (Note 4)
+RIN
+ Input Resistance
+CIN
+ Input Capacitance
CMIR
VO
Common Mode Input Range
Output Voltage Swing
VS = ±5V, ±15V
10
50
55
0.2
75
µV/°C
dB
5
95
0.2
µA/V
dB
5
µA/V
VS = ±15V, RL = 400Ω
500
2000
kΩ
VS = ±15V, RL = 150Ω
500
1800
kΩ
1.5
3
MΩ
PDIP package
1.5
pF
SOIC package
1
pF
VS = ±15V
±13.5
V
VS = ±5V
±3.5
V
±13.5
V
±12
V
±3.0
±3.7
V
60
100
150
mA
VS = ±15V, RL = 400Ω
±12
VS = ±15V, RL = 150Ω
VS = ±5V, RL = 150Ω
ISC
Output Short Circuit Current (Note 5)
VS = ±5V, ±15V
IS
Supply Current (per amplifier)
VS = ±15V
8.0
11.3
mA
VS = ±5V
5.7
8.8
mA
NOTES:
1. Measured from TMIN to TMAX.
2. VCM = ±10V for VS = ±15V, VCM = ±3V for VS = ±5V.
3. The supplies are moved from ±2.5V to ±15V.
4. VOUT = ±7V for VS = ±15V, VOUT = ±2V for VS = ±5V.
5. A heat sink is required to keep junction temperature below absolute maximum when an output is shorted.
2
EL2360
AC Electrical Specifications
PARAMETER
BW
SR
VS = ±15V, AV = +2, RF=RG=560Ω, RL=150Ω, TA=25°C unless otherwise specified. (Note 1)
DESCRIPTION
-3dB Bandwidth
Slew Rate (Note 2)
CONDITIONS
MIN
TYP
MAX
UNITS
VS = ±15V, AV = +2
130
MHz
VS = ±15V, AV = +1
180
MHz
VS = ±5V, AV = +2
100
MHz
VS = ±5V, AV = +1
110
MHz
1500
V/µs
1500
V/µs
RL= 400Ω
RF = 1 kΩ, RG = 110Ω, RL= 400Ω
1000
tR, tF
Rise Time, Fall Time
VOUT = ±500mV
2.7
ns
tPD
Propagation Delay
VOUT = ±500mV
3.2
ns
OS
Overshoot
VOUT = ±500mV
0
%
tS
0.1% Settling Time
VOUT = ±2.5V, AV = -1
35
ns
dG
Differential Gain (Note 3)
RL = 150Ω
0.025
%
RL = 500Ω
0.006
%
RL = 150Ω
0.1
°
RL = 500Ω
0.005
°
dP
Differential Phase (Note 3)
NOTES:
1. All AC tests are performed on a “warmed up” part, except Slew Rate, which is pulse tested.
2. Slew Rate is with VOUT from +10V to -10V and measured at +5V and -5V.
3. DC offset from -0.714V to +0.714V, AC amplitude 286mVP-P, f = 3.58MHz.
3
EL2360
Typical Performance Curves
Non-Inverting Frequency
Response (Gain)
Inverting Frequency
Response (Gain)
3dB Bandwidth vs Supply
Voltage for AV = -1
4
Non-Inverting Frequency
Response (Phase)
Inverting Frequency
Response (Phase)
Peaking vs Supply Voltage
for AV = -1
Frequency Response
for Various RL
Frequency Response for
Various RF and RG
3dB Bandwidth vs
Temperature for AV = - 1
EL2360
Typical Performance Curves
3dB Bandwidth vs Supply
Voltage for AV = +1
3dB Bandwidth vs Supply
Voltage for AV = +2
3dB Bandwidth vs Supply
Voltage for AV = +10
5
(Continued)
Peaking vs Supply Voltage
for AV = +1
Peaking vs Supply Voltage
for AV = +2
Peaking vs Supply Voltage
for AV = +10
3dB Bandwidth vs Temperature
for AV = +1
3dB Bandwidth vs Temperature
for AV = +2
3dB Bandwidth vs Temperature
for AV = +10
EL2360
Typical Performance Curves
(Continued)
Frequency Response
for Various CL
Frequency Response
for Various CIN-
Channel to Channel
Isolation vs Frequency
PSRR and CMRR
vs Frequency
2nd and 3rd Harmonic
Distortion vs Frequency
Transimpedance (ROL)
vs Frequency
Voltage and Current Noise
vs Frequency
Closed-Loop Output
Impedance vs Frequency
Transimpedance (ROL)
vs Die Temperature
6
EL2360
Typical Performance Curves
Offset Voltage
vs Die Temperature
(4 Samples)
(Continued)
Supply Current
vs Die Temperature
(Per Amplifier)
Supply Current
vs Supply Voltage
(Per Amplifier)
+Input Resistance
vs Die Temperature
Input Current
vs Die Temperature
+Input Bias Current
vs Input Voltage
Output Voltage Swing
vs Die Temperature
Short Circuit Current
vs Die Temperature
PSRR & CMRR
vs Die Temperature
7
EL2360
Typical Performance Curves
(Continued)
Differential Phase
vs DC Input Voltage,
RL = 150
Differential Gain
vs DC Input Voltage,
RL = 150
Differential Gain
vs DC Input Voltage,
RL = 500
Differential Phase
vs DC Input Voltage,
RL = 500
Slew Rate
vs Supply Voltage
8
Small Signal
Pulse Response
Large Signal
Pulse Response
Slew Rate
vs Temperature
EL2360
Typical Performance Curves
(Continued)
Settling Time vs
Settling Accuracy
16-Pin Plastic SO
Maximum Power Dissipation
vs Ambient Temperature
Differential Gain And Phase Test Circuit
9
Long Term Settling Error
16-Pin Plastic DIP
Maximum Power Dissipation
vs Ambient Temperature
EL2360
Simplified Schematic (One Amplifier)
Applications Information
Product Description
The EL2360 is a triple current feedback amplifier that offers
wide bandwidth and good video specifications at moderately
low supply currents. It is built using Elantec’s proprietary
complimentary bipolar process and is offered in both a 16pin PDIP and SOIC packages. Due to the current feedback
architecture, the EL2360 closed-loop -3dB bandwidth is
dependent on the value of the feedback resistor. First the
desired bandwidth is selected by choosing the feedback
resistor, RF, and then the gain is set by picking a gain
resistor, RG. The curves at the beginning of the Typical
Performance Curves section show the effect of varying both
RF and RG. The -3dB bandwidth is somewhat dependent on
the power supply voltage. As the supply voltage is
decreased, internal junction capacitances increase, causing
a reduction in the closed loop bandwidth. To compensate for
this, smaller values of feedback resistor can be used at
lower supply voltages.
Power Supply Bypassing and Printed Circuit
Board Layout
As with any high-frequency device, good printed circuit
board layout is necessary for optimum performance. Ground
plane construction is highly recommended. Lead lengths
should be as short as possible, preferably below 1/4”. The
power supply pins must be well bypassed to reduce the risk
of oscillation. The combination of a 1.0µF tantalum capacitor
in parallel with a 0.01µF ceramic capacitor has been shown
to work well when placed at each supply pin.
For good AC performance, parasitic capacitance should be
kept to a minimum especially at the inverting input (see the
Capacitance at the Inverting Input section). This implies
10
keeping the ground plane away from this pin. Carbon or
Metal-Film resistors are acceptable with the Metal-Film
resistors giving slightly less peaking and bandwidth because
of their additional series inductance. Use of sockets,
particularly for the SO package should be avoided if
possible. Sockets add parasitic inductance and capacitance
which will result in some additional peaking and overshoot.
Capacitance at the Inverting Input
Any manufacturer’s high-speed voltage- or current-feedback
amplifier can be affected by stray capacitance at the
inverting input. The characteristic curve of gain vs. frequency
with variations in CIN- emphasizes this effect. The curve
illustrates how the bandwidth can be extended to beyond
200MHz with some additional peaking with an additional 2pF
of capacitance at the VIN- pin. For inverting gains, this
parasitic capacitance has little effect because the inverting
input is a virtual ground, but for non-inverting gains, this
capacitance (in conjunction with the feedback and gain
resistors) creates a pole in the feedback path of the
amplifier. This pole, if low enough in frequency, has the
same destabilizing effect as a zero in the forward open-loop
response. The use of large value feedback and gain
resistors further exacerbates the problem by further lowering
the pole frequency.
Feedback Resistor Values
The EL2360 has been designed and specified at a gain of +2
with RF = 560Ω. This value of feedback resistor yields
relatively flat frequency response with little to no peaking out
to 130MHz. Since the EL2360 is a current-feedback
amplifier, it is also possible to change the value of RF to get
more bandwidth. As seen in the curve of Frequency
Response For Various RF and RG, bandwidth and peaking
EL2360
can be easily modified by varying the value of the feedback
resistor. For example, by reducing RF to 430Ω, bandwidth
can be extended to 170MHz with under 1dB of peaking.
Further reduction of RF to 360Ω increases the bandwidth to
195MHz with about 2.5dB of peaking.
Bandwidth vs Temperature
Whereas many amplifier’s supply current and consequently
-3dB bandwidth drop off at high temperature, the EL2360
was designed to have little supply current variation with
temperature. An immediate benefit from this is that the -3dB
bandwidth does not drop off drastically with temperature.
With VS = ±15V and AV = +2, the bandwidth varies only from
150MHz to 110MHz over the entire die junction temperature
range of -50°C < T < 150°C.
Supply Voltage Range and Single Supply
Operation
The EL2360 has been designed to operate with supply
voltages from ±2V to ±15V. Optimum bandwidth, slew rate,
and video characteristics are obtained at higher supply
voltages. However, at ±2V supplies, the -3dB bandwidth at
AV = +2 is a respectable 70MHz. The following figure is an
oscilloscope plot of the EL2360 at ±2V supplies, AV = +2,
RF = RG = 560Ω, driving a load of 150Ω, showing a clean
±600mV signal at the output.
error caused by a power dissipation differential (before and
after the voltage step). For AV = -1, due to the inverting
mode configuration, this tail does not appear since the input
stage does not experience the large voltage change as in
the non-inverting mode. With AV = -1, 0.01% settling time is
slightly greater than 100ns.
Power Dissipation
The EL2360 amplifier combines both high speed and large
output current capability at a moderate supply current in very
small packages. It is possible to exceed the maximum
junction temperature allowed under certain supply voltage,
temperature, and loading conditions. To ensure that the
EL2360 remains within it’s absolute maximum ratings, the
following discussion will help to avoid exceeding the
maximum junction temperature.
The maximum power dissipation allowed in a package is
determined according to [1]:
T JMAX – T AMAX
PD MAX = --------------------------------------------θ JA
where:
TJMAX = Maximum Junction Temperature
TAMAX = Maximum Ambient Temperature
θJA = Thermal Resistance of the Package
PDMAX = Maximum Power Dissipation in the Package
The maximum power dissipation actually produced by an IC
is the total quiescent supply current times the total power
supply voltage, plus the power in the IC due to the load, or
[2] :
V OUT⎞
⎛
PD MAX = N × ⎜ V S × I SMAX + ( V S – V OUT ) × ----------------⎟
RL ⎠
⎝
where:
If a single supply is desired, values from +4V to +30V can be
used as long as the input common mode range is not
exceeded. When using a single supply, be sure to either 1)
DC bias the inputs at an appropriate common mode voltage
and AC couple the signal, or 2) ensure the driving signal is
within the common mode range of the EL2360, which is
typically 1.5V from each supply rail.
Settling Characteristics
The EL2360 offers superb settling characteristics to 0.1%,
typically in the 35ns to 40ns range. There are no aberrations
created from the input stage which often cause longer
settling times in other current feedback amplifiers. The
EL2360 is not slew rate limited, therefore any size step up to
±10V gives approximately the same settling time.
As can be seen from the Long Term Settling Error curve, for
AV = +1, there is approximately a 0.035% residual which
tails away to 0.01% in about 40µs. This is a thermal settling
11
N =Number of amplifiers
VS = Total Supply Voltage
ISMAX = Maximum Supply Current per amplifier
VOUT = Maximum Output Voltage of the Application
RL = Load Resistance tied to Ground
If we set the two PDMAX equations, [1] and [2], equal to each
other, and solve for VS, we can get a family of curves for
various loads and output voltages according to [3]:
R L × ( T JMAX – T AMAX )
2
--------------------------------------------------------------- + ( V OUT )
N × θ JA
V S = ---------------------------------------------------------------------------------------------( I S × R L ) + V OUT
The figures below show total supply voltage VS vs RL for
various output voltage swings for the PDIP and SOIC
packages. The curves assume WORST CASE conditions of
TA = +85°C and IS = 11.3mA per amplifier. The curves do
EL2360
not include heat removal or forcing air, or the simple fact that
the package will be attached to a circuit board, which can
also provide some form of heat removal. Larger temperature
and voltage ranges are possible with heat removal and
forcing air past the part.
Supply Voltage vs RL
for Various VOUT (PDIP Package)
Supply Voltage vs RL
for Various VOUT (SOIC Package)
Current Limit
The EL2360 has internal current limits that protect the circuit
in the event of an output being shorted to ground. This limit
is set at 100mA nominally and reduces with the junction
temperature. At TJ = 150°C, the current limits at about
65mA. If any one output is shorted to ground, the power
dissipation could be well over 1W, and much greater if all
outputs are shorted. Heat removal is required in order for the
EL2360 to survive an indefinite short.
Driving Cables and Capacitive Loads
When used as a cable driver, double termination is always
recommended for reflection-free performance. For those
applications, the back-termination series resistor will decouple the EL2360 from the cable and allow extensive
capacitive drive. However, other applications may have high
capacitive loads without a back-termination resistor. In these
applications, a small series resistor (usually between 5Ω and
50Ω) can be placed in series with the output to eliminate
most peaking. The gain resistor (RG) can then be chosen to
make up for any gain loss which may be created by this
additional resistor at the output. In many cases it is also
12
possible to simply increase the value of the feedback
resistor (RF) to reduce the peaking.
EL2360
EL2360 Macromodel
*EL2360 Macromodel
*Revision A, June 1996
*AC characteristics used: Rf = Rg = 560 ohms
*Pin numbers reflect a standard single opamp
*Connections:
+input
*
|
-input
*
|
|
+Vsupply
*
|
|
|
-Vsupply
*
|
|
|
|
output
*
|
|
|
|
|
.subckt EL2360/EL 3 2 7 4 6
*
*Input Stage
*
e1 10 0 3 0 1.0
vis 10 9 0V
h2 9 12 vxx 1.0
r1 2 11 130
l1 11 12 25nH
iinp 3 0 0.5µA
iinm 2 0 5µA
r12 3 0 2 Meg
*
*Slew Rate Limiting
*
h1 13 0 vis 600
r2 13 14 1K
d1 14 0 dclamp
d2 0 14 dclamp
*
*High Frequency Pole
*
e2 30 0 14 0 0.00166666666
l3 30 17 0.43µH
c5 17 0 0.27pF
r5 17 0 500
*
*Transimpedance Stage
*
g1 0 18 17 0 1.0
rol 18 0 2Meg
cdp 18 0 2.285pF
*
*Output Stage
*
q1 4 18 19 qp
q2 7 18 20 qn
q3 7 19 21 qn
q4 4 20 22 qp
r7 21 6 4
r8 22 6 4
ios1 7 19 2mA
ios2 20 4 2mA
*
*Supply Current
*
ips 7 4 2.5mA
*
*Error Terms
13
EL2360
*
ivos 0 23 2mA
vxx 23 0 0V
e4 24 0 3 0 1.0
e5 25 0 7 0 1.0
e6 26 0 4 0 -1.0
r9 24 23 562
r10 25 23 1K
r11 26 23 1K
*
*Models
*
.model qn npn(is=5e-15 bf=100 tf=0.1ns)
.model qp pnp(is=5e-15 bf=100 tf=0.1ns)
.model dclamp d(is=1e-30 ibv=0.266
+ bv=2.24v n=4)
.ends
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Intersil Corporation’s quality certifications can be viewed at www.intersil.com/design/quality
Intersil products are sold by description only. Intersil Corporation reserves the right to make changes in circuit design, software and/or specifications at any time without
notice. Accordingly, the reader is cautioned to verify that data sheets are current before placing orders. Information furnished by Intersil is believed to be accurate and
reliable. However, no responsibility is assumed by Intersil or its subsidiaries for its use; nor for any infringements of patents or other rights of third parties which may result
from its use. No license is granted by implication or otherwise under any patent or patent rights of Intersil or its subsidiaries.
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14
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