ESIGNS NEW D R O F D ART ME N D E ME N T P E M C O A C L E D REP N OT R Sheet MENDE L536Data 0 RECOM E EL2360 ® June 1996, Rev A Triple 130MHz Current Feedback Amplifier Features The EL2360 is a triple currentfeedback operational amplifier which achieves a -3dB bandwidth of 130MHz at a gain of +2. Built using the Elantec proprietary monolithic complementary bipolar process, these amplifiers use current mode feedback to achieve more bandwidth at a given gain than a conventional voltage feedback amplifier. • Triple amplifier topology The EL2360 is designed to drive a double terminated 75Ω coax cable to video levels. It’s fast slew rate of 1500V/µs, combined with the triple amplifier topology, makes its ideal for RGB video applications. This amplifier can operate on any supply voltage from 4V (±2V) to 33V (±16.5V), yet consume only 8mA per amplifier at any supply voltage. The EL2360 is available in 16-pin PDIP and SOIC packages. For Single, Dual, or Quad applications, consider the EL2160, EL2260, or EL2460 all in industry standard pin outs. For Single applications with a power down feature, consider the EL2166. FN7065.0 • 130MHz -3dB bandwidth (AV=+2) • 180MHz -3dB bandwidth (AV=+1) • Wide supply range, ±2V to ±15V • 80mA output current (peak) • Low cost • 1500V/µs slew rate • Input common mode range to within 1.5V of supplies • 35ns settling time to 0.1% • Available in single (EL2160), dual (EL2260), and quad (EL2460) form Applications • RGB amplifiers • Video amplifiers • Cable driver • Test equipment amplifiers Pinout • Current to voltage converters EL2360 (16-PIN SO, PDIP) TOP VIEW • Video broadcast equipment Ordering Information PART NUMBER 1 TEMP. RANGE PACKAGE PKG. NO. EL2360CN -40°C to +85°C 16-Pin PDIP MDP0031 EL2360CS -40°C to +85°C 16-Pin SOIC MDP0027 CAUTION: These devices are sensitive to electrostatic discharge; follow proper IC Handling Procedures. 1-888-INTERSIL or 321-724-7143 | Intersil (and design) is a registered trademark of Intersil Americas Inc. Copyright © Intersil Americas Inc. 2003. All Rights Reserved. Elantec is a registered trademark of Elantec Semiconductor, Inc. All other trademarks mentioned are the property of their respective owners. EL2360 Absolute Maximum Ratings (TA = 25°C) Voltage between VS+ and VS-. . . . . . . . . . . . . . . . . . . . . . . . . .+33V Common-Mode Input Voltage . . . . . . . . . . . . . . . . . . . . . VS- to VS+ Differential Input Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .±6V Current into +IN or -IN . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . ±10mA Internal Power Dissipation . . . . . . . . . . . . . . . . . . . . . . . See Curves Output Current (continuous) . . . . . . . . . . . . . . . . . . . . . . . . . ±50mA Operating Ambient Temperature Range . . . . . . . . . .-40°C to +85°C Operating Junction Temperature . . . . . . . . . . . . . . . . . . . . . . . 150°C Storage Temperature Range . . . . . . . . . . . . . . . . . .-65°C to +150°C CAUTION: Stresses above those listed in “Absolute Maximum Ratings” may cause permanent damage to the device. This is a stress only rating and operation of the device at these or any other conditions above those indicated in the operational sections of this specification is not implied. IMPORTANT NOTE: All parameters having Min/Max specifications are guaranteed. Typical values are for information purposes only. Unless otherwise noted, all tests are at the specified temperature and are pulsed tests, therefore: TJ = TC = TA DC Electrical Specifications PARAMETER VS = ±15V, RL=150Ω, TA=25°C unless otherwise specified. DESCRIPTION CONDITIONS MIN TYP MAX UNITS 2 10 mV VOS Input Offset Voltage TCVOS Average Input Offset Voltage Drift (Note 1) +IIN +Input Current VS = ±5V, ±15V 0.5 3 µA -IIN -Input Current VS = ±5V, ±15V 5 25 µA CMRR Common Mode Rejection Ratio (Note 2) VS = ±5V, ±15V -ICMR -Input Current Common Mode Rejection (Note 2) VS = ±5V, ±15V PSRR Power Supply Rejection Ratio (Note 3) -IPSR -Input Current Power Supply Rejection (Note 3) ROL Transimpedance (Note 4) +RIN + Input Resistance +CIN + Input Capacitance CMIR VO Common Mode Input Range Output Voltage Swing VS = ±5V, ±15V 10 50 55 0.2 75 µV/°C dB 5 95 0.2 µA/V dB 5 µA/V VS = ±15V, RL = 400Ω 500 2000 kΩ VS = ±15V, RL = 150Ω 500 1800 kΩ 1.5 3 MΩ PDIP package 1.5 pF SOIC package 1 pF VS = ±15V ±13.5 V VS = ±5V ±3.5 V ±13.5 V ±12 V ±3.0 ±3.7 V 60 100 150 mA VS = ±15V, RL = 400Ω ±12 VS = ±15V, RL = 150Ω VS = ±5V, RL = 150Ω ISC Output Short Circuit Current (Note 5) VS = ±5V, ±15V IS Supply Current (per amplifier) VS = ±15V 8.0 11.3 mA VS = ±5V 5.7 8.8 mA NOTES: 1. Measured from TMIN to TMAX. 2. VCM = ±10V for VS = ±15V, VCM = ±3V for VS = ±5V. 3. The supplies are moved from ±2.5V to ±15V. 4. VOUT = ±7V for VS = ±15V, VOUT = ±2V for VS = ±5V. 5. A heat sink is required to keep junction temperature below absolute maximum when an output is shorted. 2 EL2360 AC Electrical Specifications PARAMETER BW SR VS = ±15V, AV = +2, RF=RG=560Ω, RL=150Ω, TA=25°C unless otherwise specified. (Note 1) DESCRIPTION -3dB Bandwidth Slew Rate (Note 2) CONDITIONS MIN TYP MAX UNITS VS = ±15V, AV = +2 130 MHz VS = ±15V, AV = +1 180 MHz VS = ±5V, AV = +2 100 MHz VS = ±5V, AV = +1 110 MHz 1500 V/µs 1500 V/µs RL= 400Ω RF = 1 kΩ, RG = 110Ω, RL= 400Ω 1000 tR, tF Rise Time, Fall Time VOUT = ±500mV 2.7 ns tPD Propagation Delay VOUT = ±500mV 3.2 ns OS Overshoot VOUT = ±500mV 0 % tS 0.1% Settling Time VOUT = ±2.5V, AV = -1 35 ns dG Differential Gain (Note 3) RL = 150Ω 0.025 % RL = 500Ω 0.006 % RL = 150Ω 0.1 ° RL = 500Ω 0.005 ° dP Differential Phase (Note 3) NOTES: 1. All AC tests are performed on a “warmed up” part, except Slew Rate, which is pulse tested. 2. Slew Rate is with VOUT from +10V to -10V and measured at +5V and -5V. 3. DC offset from -0.714V to +0.714V, AC amplitude 286mVP-P, f = 3.58MHz. 3 EL2360 Typical Performance Curves Non-Inverting Frequency Response (Gain) Inverting Frequency Response (Gain) 3dB Bandwidth vs Supply Voltage for AV = -1 4 Non-Inverting Frequency Response (Phase) Inverting Frequency Response (Phase) Peaking vs Supply Voltage for AV = -1 Frequency Response for Various RL Frequency Response for Various RF and RG 3dB Bandwidth vs Temperature for AV = - 1 EL2360 Typical Performance Curves 3dB Bandwidth vs Supply Voltage for AV = +1 3dB Bandwidth vs Supply Voltage for AV = +2 3dB Bandwidth vs Supply Voltage for AV = +10 5 (Continued) Peaking vs Supply Voltage for AV = +1 Peaking vs Supply Voltage for AV = +2 Peaking vs Supply Voltage for AV = +10 3dB Bandwidth vs Temperature for AV = +1 3dB Bandwidth vs Temperature for AV = +2 3dB Bandwidth vs Temperature for AV = +10 EL2360 Typical Performance Curves (Continued) Frequency Response for Various CL Frequency Response for Various CIN- Channel to Channel Isolation vs Frequency PSRR and CMRR vs Frequency 2nd and 3rd Harmonic Distortion vs Frequency Transimpedance (ROL) vs Frequency Voltage and Current Noise vs Frequency Closed-Loop Output Impedance vs Frequency Transimpedance (ROL) vs Die Temperature 6 EL2360 Typical Performance Curves Offset Voltage vs Die Temperature (4 Samples) (Continued) Supply Current vs Die Temperature (Per Amplifier) Supply Current vs Supply Voltage (Per Amplifier) +Input Resistance vs Die Temperature Input Current vs Die Temperature +Input Bias Current vs Input Voltage Output Voltage Swing vs Die Temperature Short Circuit Current vs Die Temperature PSRR & CMRR vs Die Temperature 7 EL2360 Typical Performance Curves (Continued) Differential Phase vs DC Input Voltage, RL = 150 Differential Gain vs DC Input Voltage, RL = 150 Differential Gain vs DC Input Voltage, RL = 500 Differential Phase vs DC Input Voltage, RL = 500 Slew Rate vs Supply Voltage 8 Small Signal Pulse Response Large Signal Pulse Response Slew Rate vs Temperature EL2360 Typical Performance Curves (Continued) Settling Time vs Settling Accuracy 16-Pin Plastic SO Maximum Power Dissipation vs Ambient Temperature Differential Gain And Phase Test Circuit 9 Long Term Settling Error 16-Pin Plastic DIP Maximum Power Dissipation vs Ambient Temperature EL2360 Simplified Schematic (One Amplifier) Applications Information Product Description The EL2360 is a triple current feedback amplifier that offers wide bandwidth and good video specifications at moderately low supply currents. It is built using Elantec’s proprietary complimentary bipolar process and is offered in both a 16pin PDIP and SOIC packages. Due to the current feedback architecture, the EL2360 closed-loop -3dB bandwidth is dependent on the value of the feedback resistor. First the desired bandwidth is selected by choosing the feedback resistor, RF, and then the gain is set by picking a gain resistor, RG. The curves at the beginning of the Typical Performance Curves section show the effect of varying both RF and RG. The -3dB bandwidth is somewhat dependent on the power supply voltage. As the supply voltage is decreased, internal junction capacitances increase, causing a reduction in the closed loop bandwidth. To compensate for this, smaller values of feedback resistor can be used at lower supply voltages. Power Supply Bypassing and Printed Circuit Board Layout As with any high-frequency device, good printed circuit board layout is necessary for optimum performance. Ground plane construction is highly recommended. Lead lengths should be as short as possible, preferably below 1/4”. The power supply pins must be well bypassed to reduce the risk of oscillation. The combination of a 1.0µF tantalum capacitor in parallel with a 0.01µF ceramic capacitor has been shown to work well when placed at each supply pin. For good AC performance, parasitic capacitance should be kept to a minimum especially at the inverting input (see the Capacitance at the Inverting Input section). This implies 10 keeping the ground plane away from this pin. Carbon or Metal-Film resistors are acceptable with the Metal-Film resistors giving slightly less peaking and bandwidth because of their additional series inductance. Use of sockets, particularly for the SO package should be avoided if possible. Sockets add parasitic inductance and capacitance which will result in some additional peaking and overshoot. Capacitance at the Inverting Input Any manufacturer’s high-speed voltage- or current-feedback amplifier can be affected by stray capacitance at the inverting input. The characteristic curve of gain vs. frequency with variations in CIN- emphasizes this effect. The curve illustrates how the bandwidth can be extended to beyond 200MHz with some additional peaking with an additional 2pF of capacitance at the VIN- pin. For inverting gains, this parasitic capacitance has little effect because the inverting input is a virtual ground, but for non-inverting gains, this capacitance (in conjunction with the feedback and gain resistors) creates a pole in the feedback path of the amplifier. This pole, if low enough in frequency, has the same destabilizing effect as a zero in the forward open-loop response. The use of large value feedback and gain resistors further exacerbates the problem by further lowering the pole frequency. Feedback Resistor Values The EL2360 has been designed and specified at a gain of +2 with RF = 560Ω. This value of feedback resistor yields relatively flat frequency response with little to no peaking out to 130MHz. Since the EL2360 is a current-feedback amplifier, it is also possible to change the value of RF to get more bandwidth. As seen in the curve of Frequency Response For Various RF and RG, bandwidth and peaking EL2360 can be easily modified by varying the value of the feedback resistor. For example, by reducing RF to 430Ω, bandwidth can be extended to 170MHz with under 1dB of peaking. Further reduction of RF to 360Ω increases the bandwidth to 195MHz with about 2.5dB of peaking. Bandwidth vs Temperature Whereas many amplifier’s supply current and consequently -3dB bandwidth drop off at high temperature, the EL2360 was designed to have little supply current variation with temperature. An immediate benefit from this is that the -3dB bandwidth does not drop off drastically with temperature. With VS = ±15V and AV = +2, the bandwidth varies only from 150MHz to 110MHz over the entire die junction temperature range of -50°C < T < 150°C. Supply Voltage Range and Single Supply Operation The EL2360 has been designed to operate with supply voltages from ±2V to ±15V. Optimum bandwidth, slew rate, and video characteristics are obtained at higher supply voltages. However, at ±2V supplies, the -3dB bandwidth at AV = +2 is a respectable 70MHz. The following figure is an oscilloscope plot of the EL2360 at ±2V supplies, AV = +2, RF = RG = 560Ω, driving a load of 150Ω, showing a clean ±600mV signal at the output. error caused by a power dissipation differential (before and after the voltage step). For AV = -1, due to the inverting mode configuration, this tail does not appear since the input stage does not experience the large voltage change as in the non-inverting mode. With AV = -1, 0.01% settling time is slightly greater than 100ns. Power Dissipation The EL2360 amplifier combines both high speed and large output current capability at a moderate supply current in very small packages. It is possible to exceed the maximum junction temperature allowed under certain supply voltage, temperature, and loading conditions. To ensure that the EL2360 remains within it’s absolute maximum ratings, the following discussion will help to avoid exceeding the maximum junction temperature. The maximum power dissipation allowed in a package is determined according to [1]: T JMAX – T AMAX PD MAX = --------------------------------------------θ JA where: TJMAX = Maximum Junction Temperature TAMAX = Maximum Ambient Temperature θJA = Thermal Resistance of the Package PDMAX = Maximum Power Dissipation in the Package The maximum power dissipation actually produced by an IC is the total quiescent supply current times the total power supply voltage, plus the power in the IC due to the load, or [2] : V OUT⎞ ⎛ PD MAX = N × ⎜ V S × I SMAX + ( V S – V OUT ) × ----------------⎟ RL ⎠ ⎝ where: If a single supply is desired, values from +4V to +30V can be used as long as the input common mode range is not exceeded. When using a single supply, be sure to either 1) DC bias the inputs at an appropriate common mode voltage and AC couple the signal, or 2) ensure the driving signal is within the common mode range of the EL2360, which is typically 1.5V from each supply rail. Settling Characteristics The EL2360 offers superb settling characteristics to 0.1%, typically in the 35ns to 40ns range. There are no aberrations created from the input stage which often cause longer settling times in other current feedback amplifiers. The EL2360 is not slew rate limited, therefore any size step up to ±10V gives approximately the same settling time. As can be seen from the Long Term Settling Error curve, for AV = +1, there is approximately a 0.035% residual which tails away to 0.01% in about 40µs. This is a thermal settling 11 N =Number of amplifiers VS = Total Supply Voltage ISMAX = Maximum Supply Current per amplifier VOUT = Maximum Output Voltage of the Application RL = Load Resistance tied to Ground If we set the two PDMAX equations, [1] and [2], equal to each other, and solve for VS, we can get a family of curves for various loads and output voltages according to [3]: R L × ( T JMAX – T AMAX ) 2 --------------------------------------------------------------- + ( V OUT ) N × θ JA V S = ---------------------------------------------------------------------------------------------( I S × R L ) + V OUT The figures below show total supply voltage VS vs RL for various output voltage swings for the PDIP and SOIC packages. The curves assume WORST CASE conditions of TA = +85°C and IS = 11.3mA per amplifier. The curves do EL2360 not include heat removal or forcing air, or the simple fact that the package will be attached to a circuit board, which can also provide some form of heat removal. Larger temperature and voltage ranges are possible with heat removal and forcing air past the part. Supply Voltage vs RL for Various VOUT (PDIP Package) Supply Voltage vs RL for Various VOUT (SOIC Package) Current Limit The EL2360 has internal current limits that protect the circuit in the event of an output being shorted to ground. This limit is set at 100mA nominally and reduces with the junction temperature. At TJ = 150°C, the current limits at about 65mA. If any one output is shorted to ground, the power dissipation could be well over 1W, and much greater if all outputs are shorted. Heat removal is required in order for the EL2360 to survive an indefinite short. Driving Cables and Capacitive Loads When used as a cable driver, double termination is always recommended for reflection-free performance. For those applications, the back-termination series resistor will decouple the EL2360 from the cable and allow extensive capacitive drive. However, other applications may have high capacitive loads without a back-termination resistor. In these applications, a small series resistor (usually between 5Ω and 50Ω) can be placed in series with the output to eliminate most peaking. The gain resistor (RG) can then be chosen to make up for any gain loss which may be created by this additional resistor at the output. In many cases it is also 12 possible to simply increase the value of the feedback resistor (RF) to reduce the peaking. EL2360 EL2360 Macromodel *EL2360 Macromodel *Revision A, June 1996 *AC characteristics used: Rf = Rg = 560 ohms *Pin numbers reflect a standard single opamp *Connections: +input * | -input * | | +Vsupply * | | | -Vsupply * | | | | output * | | | | | .subckt EL2360/EL 3 2 7 4 6 * *Input Stage * e1 10 0 3 0 1.0 vis 10 9 0V h2 9 12 vxx 1.0 r1 2 11 130 l1 11 12 25nH iinp 3 0 0.5µA iinm 2 0 5µA r12 3 0 2 Meg * *Slew Rate Limiting * h1 13 0 vis 600 r2 13 14 1K d1 14 0 dclamp d2 0 14 dclamp * *High Frequency Pole * e2 30 0 14 0 0.00166666666 l3 30 17 0.43µH c5 17 0 0.27pF r5 17 0 500 * *Transimpedance Stage * g1 0 18 17 0 1.0 rol 18 0 2Meg cdp 18 0 2.285pF * *Output Stage * q1 4 18 19 qp q2 7 18 20 qn q3 7 19 21 qn q4 4 20 22 qp r7 21 6 4 r8 22 6 4 ios1 7 19 2mA ios2 20 4 2mA * *Supply Current * ips 7 4 2.5mA * *Error Terms 13 EL2360 * ivos 0 23 2mA vxx 23 0 0V e4 24 0 3 0 1.0 e5 25 0 7 0 1.0 e6 26 0 4 0 -1.0 r9 24 23 562 r10 25 23 1K r11 26 23 1K * *Models * .model qn npn(is=5e-15 bf=100 tf=0.1ns) .model qp pnp(is=5e-15 bf=100 tf=0.1ns) .model dclamp d(is=1e-30 ibv=0.266 + bv=2.24v n=4) .ends All Intersil U.S. products are manufactured, assembled and tested utilizing ISO9000 quality systems. Intersil Corporation’s quality certifications can be viewed at www.intersil.com/design/quality Intersil products are sold by description only. Intersil Corporation reserves the right to make changes in circuit design, software and/or specifications at any time without notice. Accordingly, the reader is cautioned to verify that data sheets are current before placing orders. Information furnished by Intersil is believed to be accurate and reliable. However, no responsibility is assumed by Intersil or its subsidiaries for its use; nor for any infringements of patents or other rights of third parties which may result from its use. No license is granted by implication or otherwise under any patent or patent rights of Intersil or its subsidiaries. For information regarding Intersil Corporation and its products, see www.intersil.com 14