DATASHEET

NS
ESIG
WD
E
N
FOR
DED
MEN EL5364
M
O
SEE
REC
NOT
®
Data Sheet
Triple 600MHz Current Feedback Amplifier
with Enable
The EL5392A is a triple current feedback amplifier with a
very high bandwidth of 600MHz. This makes this amplifier
ideal for today’s high speed video and monitor applications.
With a supply current of just 6mA per amplifier and the ability
to run from a single supply voltage from 5V to 10V, the
EL5392A is also ideal for hand held, portable or battery
powered equipment.
The EL5392A also incorporates an enable and disable
function to reduce the supply current to 100µA typical per
amplifier. Allowing the CE pin to float or applying a low logic
level will enable the amplifier.
For applications where board space is critical, the EL5392A
is offered in the 16 Ld QSOP package, as well as an
industry-standard 16 Ld SO (0.150"). The EL5392A operates
over the industrial temperature range of -40°C to +85°C.
EL5392A
March 9, 2006
FN7194.1
Features
• 600MHz -3dB bandwidth
• 6mA supply current (per amplifier)
• Single and dual supply operation, from 5V to 10V
• Fast enable/disable
• Available in 16 Ld QSOP package
• Single (EL5192) and dual (EL5292) available
• High speed, 1GHz product available (EL5191)
• Low power, 4mA, 300MHz product available (EL5193,
EL5293, and EL5393)
• Pb-free plus anneal available (RoHS compliant)
Applications
• Video amplifiers
• Cable drivers
• RGB amplifiers
Ordering Information
PART NUMBER
• Test equipment
PART
TAPE &
MARKING REEL
PACKAGE
PKG.
DWG. #
• Instrumentation
• Current to voltage converters
EL5392ACS
EL5392ACS
-
16 Ld SOIC
(0.150")
MDP0027
EL5392ACS-T7
EL5392ACS
7”
16 Ld SOIC
(0.150")
MDP0027
EL5392ACS-T13
EL5392ACS
13”
16 Ld SOIC
(0.150")
MDP0027
EL5392ACU
5392ACU
-
16 Ld QSOP
MDP0040
INA+ 1
EL5392ACU-T13
(Note)
5392ACU
13”
16 Ld QSOP
(Pb-free)
MDP0040
CEA 2
EL5392ACUZ
(Note)
5392ACUZ
-
16 Ld QSOP
(Pb-free)
MDP0040
EL5392ACUZ-T7
(Note)
5392ACUZ
7”
16 Ld QSOP
(Pb-free)
MDP0040
EL5392ACUZ-T13 5392ACUZ
(Note)
13”
16 Ld QSOP
(Pb-free)
MDP0040
Pinout
EL5392
[16 LD SOIC (0.150") & QSOP]
TOP VIEW
16 INA+
VS- 3
CEB 4
NOTE: Intersil Pb-free plus anneal products employ special Pb-free
material sets; molding compounds/die attach materials and 100% matte
tin plate termination finish, which are RoHS compliant and compatible
with both SnPb and Pb-free soldering operations. Intersil Pb-free
products are MSL classified at Pb-free peak reflow temperatures that
meet or exceed the Pb-free requirements of IPC/JEDEC J STD-020.
1
14 VS+
+
-
INB+ 5
INC+ 8
13 OUTB
12 INB-
NC 6
CEC 7
15 OUTA
11 NC
+
-
10 OUTC
9 INC-
CAUTION: These devices are sensitive to electrostatic discharge; follow proper IC Handling Procedures.
1-888-INTERSIL or 1-888-468-3774 | Intersil (and design) is a registered trademark of Intersil Americas Inc.
Copyright © Intersil Americas Inc. 2004, 2006. All Rights Reserved. Elantec is a registered trademark of Elantec Semiconductor, Inc.
All other trademarks mentioned are the property of their respective owners.
EL5392A
Absolute Maximum Ratings (TA = 25°C)
Supply Voltage Between VS+ and VS-. . . . . . . . . . . . . . . . . . . . . 11V
Maximum Continuous Output Current . . . . . . . . . . . . . . . . . . . 50mA
Operating Junction Temperature . . . . . . . . . . . . . . . . . . . . . . . 125°C
Power Dissipation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . See Curves
Pin Voltages. . . . . . . . . . . . . . . . . . . . . . . . .VS- - 0.5V to VS+ +0.5V
Storage Temperature . . . . . . . . . . . . . . . . . . . . . . . .-65°C to +150°C
Operating Temperature . . . . . . . . . . . . . . . . . . . . . . .-40°C to +85°C
CAUTION: Stresses above those listed in “Absolute Maximum Ratings” may cause permanent damage to the device. This is a stress only rating and operation of the
device at these or any other conditions above those indicated in the operational sections of this specification is not implied.
IMPORTANT NOTE: All parameters having Min/Max specifications are guaranteed. Typical values are for information purposes only. Unless otherwise noted, all tests
are at the specified temperature and are pulsed tests, therefore: TJ = TC = TA
Electrical Specifications
PARAMETER
VS+ = +5V, VS- = -5V, RF = 750Ω for AV = 1, RF = 375Ω for AV = 2, RL = 150Ω, TA = 25°C unless otherwise
specified.
DESCRIPTION
CONDITIONS
MIN
TYP
MAX
UNIT
AC PERFORMANCE
BW
-3dB Bandwidth
AV = +1
600
MHz
AV = +2
300
MHz
25
MHz
2300
V/µs
BW1
0.1dB Bandwidth
SR
Slew Rate
VO = -2.5V to +2.5V, AV = +2
tS
0.1% Settling Time
VOUT = -2.5V to +2.5V, AV = -1
9
ns
CS
Channel Separation
f = 5MHz
60
dB
eN
Input Voltage Noise
4.1
nV/√Hz
iN-
IN- Input Current Noise
20
pA/√Hz
iN+
IN+ Input Current Noise
50
pA/√Hz
dG
Differential Gain Error (Note 1)
AV = +2
0.015
%
dP
Differential Phase Error (Note 1)
AV = +2
0.04
°
2000
DC PERFORMANCE
VOS
Offset Voltage
TCVOS
Input Offset Voltage Temperature Coefficient Measured from TMIN to TMAX
ROL
Transimpediance
-10
1
10
mV
5
µV/°C
200
400
kΩ
INPUT CHARACTERISTICS
CMIR
Common Mode Input Range
±3
±3.3
V
CMRR
Common Mode Rejection Ratio
42
50
dB
+IIN
+ Input Current
-60
3
60
µA
-IIN
- Input Current
-40
4
40
µA
RIN
Input Resistance
37
kΩ
CIN
Input Capacitance
0.5
pF
OUTPUT CHARACTERISTICS
VO
RL = 150Ω to GND
±3.4
±3.7
V
RL = 1kΩ to GND
±3.8
±4.0
V
Output Current
RL = 10Ω to GND
95
120
mA
ISON
Supply Current - Enabled
No load, VIN = 0V
5
6
7.5
mA
ISOFF
Supply Current - Disabled
No load, VIN = 0V
100
150
µA
IOUT
Output Voltage Swing
SUPPLY
2
FN7194.1
March 9, 2006
EL5392A
Electrical Specifications
PARAMETER
VS+ = +5V, VS- = -5V, RF = 750Ω for AV = 1, RF = 375Ω for AV = 2, RL = 150Ω, TA = 25°C unless otherwise
specified. (Continued)
DESCRIPTION
CONDITIONS
MIN
TYP
75
PSRR
Power Supply Rejection Ratio
DC, VS = ±4.75V to ±5.25V
55
-IPSR
- Input Current Power Supply Rejection
DC, VS = ±4.75V to ±5.25V
-2
MAX
UNIT
dB
2
µA/V
ENABLE
tEN
Enable Time
40
ns
tDIS
Disable Time
600
ns
IIHCE
CE Pin Input High Current
CE = VS+
0.8
6
µA
IILCE
CE Pin Input Low Current
CE = VS-
0
-0.1
µA
VIHCE
CE Input High Voltage for Power-down
VILCE
CE Input Low Voltage for Power-down
VS+ - 1
V
VS+ - 3
V
NOTE:
1. Standard NTSC test, AC signal amplitude = 286mVP-P, f = 3.58MHz
3
FN7194.1
March 9, 2006
EL5392A
Typical Performance Curves
Non-Inverting Frequency Response (Gain)
Non-Inverting Frequency Response (Phase)
6
90
AV=2
2
0
-2
-90
AV=1
AV=2
Phase (°)
Normalized Magnitude (dB)
AV=1
AV=5
-6
AV=5
AV=10
-180
AV=10
-10
-270
RF=750Ω
RL=150Ω
-14
1M
RF=750Ω
RL=150Ω
10M
100M
-360
1M
1G
10M
Frequency (Hz)
Inverting Frequency Response (Gain)
90
AV=-1
2
AV=-2
AV=-1
0
Phase (°)
-2
AV=-5
-6
-10
-90
AV=-2
AV=-5
-180
-270
RF=375Ω
RL=150Ω
-14
1M
RF=375Ω
RL=150Ω
10M
100M
-360
1M
1G
10M
Frequency (Hz)
100M
Frequency Response for Various RL
10
6
RL=150Ω
Normalized Magnitude (dB)
2pF added
6
1pF added
2
-2
-6
1G
Frequency (Hz)
Frequency Response for Various CIN-
Normalized Magnitude (dB)
1G
Inverting Frequency Response (Phase)
6
Normalized Magnitude (dB)
100M
Frequency (Hz)
0pF added
AV=2
RF=375Ω
RL=150Ω
RL=100Ω
2
RL=500Ω
-2
-6
-10
AV=2
RF=375Ω
-10
1M
10M
100M
Frequency (Hz)
4
1G
-14
1M
10M
100M
1G
Frequency (Hz)
FN7194.1
March 9, 2006
EL5392A
Typical Performance Curves
(Continued)
Frequency Response for Various CL
Frequency Response for Various RF
6
AV=2
RF=375Ω
RL=150Ω
10
250Ω
Normalized Magnitude (dB)
Normalized Magnitude (dB)
14
12pF added
6
8pF added
2
0pF added
-2
-6
1M
10M
100M
475Ω
-2
620Ω
-6
750Ω
-10
AV=2
RG=RF
RL=150Ω
-14
1M
1G
10M
Frequency (Hz)
100M
1G
Frequency (Hz)
Frequency Response for Various Common-Mode
Input Voltages
Group Delay vs Frequency
3.5
6
VCM=3V
2.5
Normalized Magnitude (dB)
3
Group Delay (ns)
375Ω
2
AV=2
RF=375Ω
2
1.5
1
AV=1
RF=750Ω
0.5
0
1M
100M
10M
-2
VCM=-3V
-6
-10
AV=2
RF=375Ω
RL=150Ω
-14
1M
1G
VCM=0V
2
10M
100M
1G
Frequency (Hz)
Frequency (Hz)
Transimpedance (ROL) vs Frequency
PSRR and CMRR vs Frequency
20
10M
0
Phase
100k
-180
10k
-270
Gain
1k
PSRR/CMRR (dB)
0
-90
Phase (°)
Magnitude (Ω)
1M
PSRR+
-20
PSRR-40
-60
CMRR
-360
100
1k
10k
100k
1M
10M
Frequency (Hz)
5
100M
1G
-80
10k
100k
1M
10M
100M
1G
Frequency (Hz)
FN7194.1
March 9, 2006
EL5392A
Typical Performance Curves
(Continued)
-3dB Bandwidth vs Supply Voltage for Non-Inverting
Gains
-3dB Bandwidth vs Supply Voltage for Inverting Gains
800
350
300
600
-3dB Bandwidth (MHz)
-3dB Bandwidth (MHz)
RF=750Ω
RL=150Ω
AV=1
400
AV=2
200
AV=5
AV=10
AV=-1
250
AV=-2
200
AV=-5
150
100
50
0
RF=375Ω
RL=150Ω
0
5
6
7
8
9
5
10
6
7
Total Supply Voltage (V)
Peaking vs Supply Voltage for Non-Inverting Gains
10
4
RF=750Ω
RL=150Ω
3
3
AV=1
2
1
RF=375Ω
RL=150Ω
AV=-1
Peaking (dB)
Peaking (dB)
9
Peaking vs Supply Voltage for Inverting Gains
4
AV=-2
2
1
AV=2
AV=10
AV=-5
0
0
5
6
7
8
9
5
10
6
7
Total Supply Voltage (V)
9
10
-3dB Bandwidth vs Temperature for Inverting Gains
1400
500
RF=750Ω
RL=150Ω
AV=1
400
-3dB Bandwidth (MHz)
1200
8
Total Supply Voltage (V)
-3dB Bandwidth vs Temperature for Non-Inverting
Gains
-3dB Bandwidth (MHz)
8
Total Supply Voltage (V)
1000
800
600
400
AV=5
AV=10
AV=2
300
RF=375Ω
RL=150Ω
AV=-1
AV=-2
200
AV=-5
100
200
0
-40
10
60
110
Ambient Temperature (°C)
6
160
0
-40
10
60
110
160
Ambient Temperature (°C)
FN7194.1
March 9, 2006
EL5392A
Typical Performance Curves
(Continued)
Peaking vs Temperature
Voltage and Current Noise vs Frequency
2
1k
RL=150Ω
AV=1
Voltage Noise (nV/√Hz)
Current Noise (pA/√Hz)
Peaking (dB)
1.5
1
AV=-1
0.5
AV=-2
0
i n+
100
i n10
en
AV=2
-0.5
-50
-50
0
50
1
100
100
1k
10k
100
10
10
8
Supply Current (mA)
Output Impedance (Ω)
1M
10M
Supply Current vs Supply Voltage
Closed Loop Output Impedance vs Frequency
1
0.1
0.01
6
4
2
0.001
0
100
1k
10k
1M
100k
10M
100M
1G
0
2
4
6
8
10
12
Supply Voltage (V)
Frequency (Hz)
2nd and 3rd Harmonic Distortion vs Frequency
Two-Tone 3rd Order
Input Referred Intermodulation Intercept (IIP3)
-20
30
AV=+2
VOUT=2VP-P
RL=100Ω
-40
-50
2nd Order
Distortion
-60
-70
3rd Order
Distortion
-80
-90
20
15
10
5
0
-5
-10
-100
1
10
Frequency (MHz)
7
AV=+2
RL=150Ω
25
Input Power Intercept (dBm)
-30
Harmonic Distortion (dBc)
100k
Frequency (Hz)
Ambient Temperature (°C)
100
AV=+2
RL=100Ω
-15
10
100
200
Frequency (MHz)
FN7194.1
March 9, 2006
EL5392A
Typical Performance Curves
(Continued)
Differential Gain/Phase vs DC Input
Voltage at 3.58MHz
Differential Gain/Phase vs DC Input
Voltage at 3.58MHz
0.03
0.03
AV=2
RF=RG=375Ω
RL=150Ω
0.02
dP
0.01
dG (%) or dP (°)
0.01
dG (%) or dP (°)
AV=1
RF=750Ω
RL=500Ω
0.02
0
dG
-0.01
-0.02
-0.03
dP
0
dG
-0.01
-0.02
-0.03
-0.04
-0.04
-0.05
-0.05
-1
-0.5
0
0.5
-0.06
-1
1
-0.5
DC Input Voltage
Output Voltage Swing vs Frequency
THD<1%
0.5
1
Output Voltage Swing vs Frequency
THD<0.1%
9
10
7
RL=500Ω
Output Voltage Swing (VPP)
RL=500Ω
8
Output Voltage Swing (VPP)
0
DC Input Voltage
RL=150Ω
6
5
4
3
2
8
RL=150Ω
6
4
2
1
AV=2
AV=2
0
0
1
10
100
1
Frequency (MHz)
10
Small Signal Step Response
Large Signal Step Response
VS=±5V
RL=150Ω
AV=2
RF=RG=375Ω
200mV/div
100
Frequency (MHz)
VS=±5V
RL=150Ω
AV=2
RF=RG=375Ω
1V/div
10ns/div
8
10ns/div
FN7194.1
March 9, 2006
EL5392A
Typical Performance Curves
(Continued)
Settling Time vs Settling Accuracy
Transimpedance (RoI) vs Temperature
25
500
AV=2
RF=RG=375Ω
RL=150Ω
VSTEP=5VP-P output
450
15
RoI (kΩ)
Settling Time (ns)
20
10
400
350
5
0
0.01
0.1
300
-40
1
10
Settling Accuracy (%)
PSRR and CMRR vs Temperature
110
160
110
160
ICMR and IPSR vs Temperature
90
2.5
PSRR
80
2
ICMR/IPSR (µA/V)
70
PSRR/CMRR (dB)
60
Die Temperature (°C)
60
CMRR
50
40
30
ICMR+
1.5
1
IPSR
0.5
0
ICMR-
-0.5
20
10
-40
10
60
110
-1
-40
160
10
Die Temperature (°C)
60
Die Temperature (°C)
Offset Voltage vs Temperature
Input Current vs Temperature
3
60
40
Input Current (µA)
VOS (mV)
2
1
0
20
IB0
-20
IB+
-40
-1
-60
-2
-40
10
60
Die Temperature (°C)
9
110
160
-80
-40
10
60
110
160
Temperature (°C)
FN7194.1
March 9, 2006
EL5392A
Typical Performance Curves
(Continued)
Positive Input Resistance vs Temperature
Supply Current vs Temperature
50
8
45
7
Supply Current (mA)
40
RIN+ (kΩ)
35
30
25
20
15
6
5
4
3
2
10
1
5
0
-40
10
60
110
0
-40
160
10
Temperature (°C)
60
110
160
Temperature (°C)
Positive Output Swing vs Temperature for Various
Loads
Negative Output Swing vs Temperature for Various
Loads
4.2
-3.5
4.1
-3.6
150Ω
1kΩ
-3.7
VOUT (V)
VOUT (V)
4
3.9
3.8
3.7
-3.8
-3.9
1kΩ
-4
150Ω
-4.1
3.6
3.5
-40
10
50
110
-4.2
-40
160
10
Output Current vs Temperature
4600
AV=2
RF=RG=375Ω
RL=150Ω
4400
4200
Sink
Slew Rate (V/µS)
IOUT (mA)
160
Slew Rate vs Temperature
135
130
110
60
Temperature (°C)
Temperature (°C)
125
Source
120
4000
3800
3600
3400
3200
115
-40
10
60
Die Temperature (°C)
10
110
160
3000
-40
10
60
110
160
Die Temperature (°C)
FN7194.1
March 9, 2006
EL5392A
Typical Performance Curves
(Continued)
Package Power Dissipation vs Ambient Temperature
JEDEC JESD51-3 Low Effective Thermal Conductivity Test
Board
Channel-to-Channel Isolation vs Frequency
0
1
0.9
0.8
Power Dissipation (W)
Gain (dB)
-20
-40
-60
-80
909mW
0.7
0.6
633mW
0.5
0.4
SO
16
(0
11
.1
0°
50
C
”)
/W
QS
OP
15
16
8°
C/
W
0.3
0.2
0.1
-100
100k
0
1M
10M
100M
400M
0
Frequency (Hz)
25
50
75 85
100
125
150
Ambient Temperature (°C)
Enable Response
Disable Response
500mV/div
500mV/div
5V/div
5V/div
20ns/div
11
400ns/div
FN7194.1
March 9, 2006
EL5392A
Pin Descriptions
16 Ld SOIC
(0.150")
16 Ld QSOP
Pin Name
1
1
INA+
Function
Equivalent Circuit
Non-inverting input, channel A
VS+
IN+
IN-
VSCircuit 1
2
2
CEA
Chip enable, channel A
VS+
CE
VSCircuit 2
3
3
VS-
Negative supply
4
4
CEB
Chip enable, channel B
(See circuit 2)
5
5
INB+
Non-inverting input, channel B
(See circuit 1)
6, 11
6, 11
NC
7
7
CEC
Chip enable, channel C
(See circuit 2)
8
8
INC+
Non-inverting input, channel C
(See circuit 1)
9
9
INC-
Inverting input, channel C
(See circuit 1)
10
10
OUTC
Not connected
Output, channel C
VS+
OUT
VSCircuit 3
12
12
INB-
13
13
OUTB
14
14
VS+
15
15
OUTA
16
16
INA-
Inverting input, channel B
(See circuit 1)
Output, channel B
(See circuit 3)
Positive supply
Output, channel A
(See circuit 3)
Inverting input, channel A
(See circuit 1)
Applications Information
Product Description
The EL5392A is a current-feedback operational amplifier
that offers a wide -3dB bandwidth of 600MHz and a low
supply current of 6mA per amplifier. The EL5392A works
with supply voltages ranging from a single 5V to 10V and
they are also capable of swinging to within 1V of either
supply on the output. Because of their current-feedback
topology, the EL5392A does not have the normal gainbandwidth product associated with voltage-feedback
operational amplifiers. Instead, its -3dB bandwidth to remain
12
relatively constant as closed-loop gain is increased. This
combination of high bandwidth and low power, together with
aggressive pricing make the EL5392A the ideal choice for
many low-power/high-bandwidth applications such as
portable, handheld, or battery-powered equipment.
For varying bandwidth needs, consider the EL5191 with
1GHz on a 9mA supply current or the EL5193 with 300MHz
on a 4mA supply current. Versions include single, dual, and
triple amp packages with 5 Ld SOT-23, 16 Ld QSOP, and
8 Ld or 16 Ld SOIC (0.150") outlines.
FN7194.1
March 9, 2006
EL5392A
Power Supply Bypassing and Printed Circuit
Board Layout
not recommended around the inverting input pin of the
amplifier.
As with any high frequency device, good printed circuit
board layout is necessary for optimum performance. Low
impedance ground plane construction is essential. Surface
mount components are recommended, but if leaded
components are used, lead lengths should be as short as
possible. The power supply pins must be well bypassed to
reduce the risk of oscillation. The combination of a 4.7µF
tantalum capacitor in parallel with a 0.01µF capacitor has
been shown to work well when placed at each supply pin.
Feedback Resistor Values
For good AC performance, parasitic capacitance should be
kept to a minimum, especially at the inverting input. (See the
Capacitance at the Inverting Input section) Even when
ground plane construction is used, it should be removed
from the area near the inverting input to minimize any stray
capacitance at that node. Carbon or Metal-Film resistors are
acceptable with the Metal-Film resistors giving slightly less
peaking and bandwidth because of additional series
inductance. Use of sockets, particularly for the SOIC
(0.150") package, should be avoided if possible. Sockets
add parasitic inductance and capacitance which will result in
additional peaking and overshoot.
Disable/Power-Down
The EL5392A amplifier can be disabled placing its output in
a high impedance state. When disabled, the amplifier supply
current is reduced to < 450µA. The EL5392A is disabled
when its CE pin is pulled up to within 1V of the positive
supply. Similarly, the amplifier is enabled by floating or
pulling its CE pin to at least 3V below the positive supply. For
±5V supply, this means that an EL5392A amplifier will be
enabled when CE is 2V or less, and disabled when CE is
above 4V. Although the logic levels are not standard TTL,
this choice of logic voltages allows the EL5392A to be
enabled by tying CE to ground, even in 5V single supply
applications. The CE pin can be driven from CMOS outputs.
Capacitance at the Inverting Input
Any manufacturer’s high-speed voltage- or current-feedback
amplifier can be affected by stray capacitance at the
inverting input. For inverting gains, this parasitic capacitance
has little effect because the inverting input is a virtual
ground, but for non-inverting gains, this capacitance (in
conjunction with the feedback and gain resistors) creates a
pole in the feedback path of the amplifier. This pole, if low
enough in frequency, has the same destabilizing effect as a
zero in the forward open-loop response. The use of largevalue feedback and gain resistors exacerbates the problem
by further lowering the pole frequency (increasing the
possibility of oscillation.)
The EL5392A has been optimized with a 375Ω feedback
resistor. With the high bandwidth of these amplifiers, these
resistor values might cause stability problems when
combined with parasitic capacitance, thus ground plane is
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The EL5392A has been designed and specified at a gain of
+2 with RF approximately 375Ω. This value of feedback
resistor gives 300MHz of -3dB bandwidth at AV=2 with 2dB
of peaking. With AV=-2, an RF of 375Ω gives 275MHz of
bandwidth with 1dB of peaking. Since the EL5392A is a
current-feedback amplifier, it is also possible to change the
value of RF to get more bandwidth. As seen in the curve of
Frequency Response for Various RF and RG, bandwidth and
peaking can be easily modified by varying the value of the
feedback resistor.
Because the EL5392A is a current-feedback amplifier, its
gain-bandwidth product is not a constant for different closedloop gains. This feature actually allows the EL5392A to
maintain about the same -3dB bandwidth. As gain is
increased, bandwidth decreases slightly while stability
increases. Since the loop stability is improving with higher
closed-loop gains, it becomes possible to reduce the value
of RF below the specified 375Ω and still retain stability,
resulting in only a slight loss of bandwidth with increased
closed-loop gain.
Supply Voltage Range and Single-Supply
Operation
The EL5392A has been designed to operate with supply
voltages having a span of greater than 5V and less than 10V.
In practical terms, this means that the EL5392A will operate
on dual supplies ranging from ±2.5V to ±5V. With singlesupply, the EL5392A will operate from 5V to 10V.
As supply voltages continue to decrease, it becomes
necessary to provide input and output voltage ranges that
can get as close as possible to the supply voltages. The
EL5392A has an input range which extends to within 2V of
either supply. So, for example, on ±5V supplies, the
EL5392A has an input range which spans ±3V. The output
range of the EL5392A is also quite large, extending to within
1V of the supply rail. On a ±5V supply, the output is therefore
capable of swinging from -4V to +4V. Single-supply output
range is larger because of the increased negative swing due
to the external pull-down resistor to ground.
Video Performance
For good video performance, an amplifier is required to
maintain the same output impedance and the same
frequency response as DC levels are changed at the output.
This is especially difficult when driving a standard video load
of 150Ω, because of the change in output current with DC
level. Previously, good differential gain could only be
achieved by running high idle currents through the output
transistors (to reduce variations in output impedance.)
These currents were typically comparable to the entire 6mA
supply current of each EL5392A amplifier. Special circuitry
has been incorporated in the EL5392A to reduce the
FN7194.1
March 9, 2006
EL5392A
variation of output impedance with current output. This
results in dG and dP specifications of 0.015% and 0.04°,
while driving 150Ω at a gain of 2.
Video performance has also been measured with a 500Ω
load at a gain of +1. Under these conditions, the EL5392A
has dG and dP specifications of 0.03% and 0.05°,
respectively.
modified for the EL5392A to remain in the safe operating
area. These parameters are calculated as follows:
T JMAX = T MAX + ( θ JA × n × PD MAX )
where:
TMAX = Maximum ambient temperature
Output Drive Capability
θJA = Thermal resistance of the package
In spite of its low 6mA of supply current, the EL5392A is
capable of providing a minimum of ±95mA of output current.
With a minimum of ±95mA of output drive, the EL5392A is
capable of driving 50Ω loads to both rails, making it an
excellent choice for driving isolation transformers in
telecommunications applications.
n = Number of amplifiers in the package
Driving Cables and Capacitive Loads
When used as a cable driver, double termination is always
recommended for reflection-free performance. For those
applications, the back-termination series resistor will
decouple the EL5392A from the cable and allow extensive
capacitive drive. However, other applications may have high
capacitive loads without a back-termination resistor. In these
applications, a small series resistor (usually between 5Ω and
50Ω) can be placed in series with the output to eliminate
most peaking. The gain resistor (RG) can then be chosen to
make up for any gain loss which may be created by this
additional resistor at the output. In many cases it is also
possible to simply increase the value of the feedback
resistor (RF) to reduce the peaking.
PDMAX = Maximum power dissipation of each amplifier in
the package
PDMAX for each amplifier can be calculated as follows:
V OUTMAX
PDMAX = ( 2 × V S × I SMAX ) + ( V S - V OUTMAX ) × ---------------------------R
L
where:
VS = Supply voltage
ISMAX = Maximum supply current of 1A
VOUTMAX = Maximum output voltage (required)
RL = Load resistance
Current Limiting
The EL5392A has no internal current-limiting circuitry. If the
output is shorted, it is possible to exceed the Absolute
Maximum Rating for output current or power dissipation,
potentially resulting in the destruction of the device.
Power Dissipation
With the high output drive capability of the EL5392A, it is
possible to exceed the 125°C Absolute Maximum junction
temperature under certain very high load current conditions.
Generally speaking when RL falls below about 25Ω, it is
important to calculate the maximum junction temperature
(TJMAX) for the application to determine if power supply
voltages, load conditions, or package type need to be
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FN7194.1
March 9, 2006
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