APPLICATION NOTE 90W Resonant SMPS with TEA1610 SwingChipTM AN99011 Philips Semiconductors 90W Resonant SMPS with TEA1610 SwingChipTM Application Note AN99011 Abstract This report describes a 90W Resonant Switched Mode Power Supply (ResSMPS) for a typical TV or monitor application based upon the TEA1610 SwingChipTM resonant SMPS controller. The power supply is based on the half bridge DC-to-DC resonant LLC converter with zero-voltage switching. The TEA1610 uses current driven frequency control. © Philips Electronics N.V. 1999 All rights are reserved. Reproduction in whole or in part is prohibited without the prior written consent of the copyright owner. The information presented in this document does not form part of any quotation or contract, is believed to be accurate and reliable and may be changed without notice. No liability will be accepted by the publisher for any consequence of its use. Publication thereof does not convey nor imply any license under patent- or other industrial or intellectual property rights. 2 Philips Semiconductors 90W Resonant SMPS with TEA1610 SwingChipTM Application Note AN99011 APPLICATION NOTE 90W Resonant SMPS with TEA1610 SwingChipTM AN99011 Author: R.Kennis Philips Semiconductors Systems Laboratory Eindhoven, The Netherlands Approved by: T. Mobers E. Derckx Keywords TM SwingChip TEA1610 Resonant SMPS Zero-voltage-switching Number of pages: 27 Date: 99-09-14 3 Philips Semiconductors 90W Resonant SMPS with TEA1610 SwingChipTM Application Note AN99011 Summary TM The SwingChip TEA1610 controller is a monolithic integrated circuit and is implemented on the 650V BCD power logic process. The IC provides the drive function for two discrete power MOSFETs in a half bridge configuration and is a high voltage controller for a zero-voltage switching resonant converter. To guarantee an accurate 50% duty cycle, the oscillator signal passes through a divider before being fed to the output drivers. This application note briefly describes a 90W Resonant Converter for a typical TV or monitor application based upon the TEA1610 controller. The converter is composed of two bi-directional switches and a resonant LLCcircuit. To limit the costs the two inductors are integrated in one transformer: a magnetising inductance and a leakage inductance, which is cheaper than two separate coils. With a certain coupling of about 0.6 the leakage inductance is given the required value. The outputs are mains isolated and the 80V is controlled secondary. The converter has a high performance efficiency and a very good cross regulation 4 Philips Semiconductors 90W Resonant SMPS with TEA1610 SwingChipTM Application Note AN99011 CONTENTS 1 INTRODUCTION ............................................................................................................................................. 7 2 FEATURES...................................................................................................................................................... 7 3 QUICK REFERENCE DATA ........................................................................................................................... 8 4 FUNCTIONAL BLOCK DIAGRAM.................................................................................................................. 9 5 CIRCUIT DESCRIPTION............................................................................................................................... 10 5.1 5.2 5.3 5.4 5.5 5.6 5.7 6 Mains input circuit...................................................................................................................................... 10 Half bridge switches .................................................................................................................................. 10 Transformer............................................................................................................................................... 10 Output section ........................................................................................................................................... 10 Regulation, opto coupler and controller..................................................................................................... 11 Start-up...................................................................................................................................................... 11 Protections................................................................................................................................................. 12 5.7.1Under Voltage Lock Out (UVLO) and Short Circuit Protection.......................................................... 12 5.7.2Over Voltage Protection (OVP) ......................................................................................................... 12 5.7.3Over Current Protection (OCP) ......................................................................................................... 12 MEASUREMENTS ........................................................................................................................................ 13 6.1 6.2 6.3 6.4 Static performance .................................................................................................................................... 13 Dynamic performance ............................................................................................................................... 16 Bode diagrams .......................................................................................................................................... 17 EMI results................................................................................................................................................. 18 7 CIRCUIT DIAGRAM ...................................................................................................................................... 19 8 LAYOUT CONSIDERATIONS....................................................................................................................... 21 9 PARTS LIST .................................................................................................................................................. 25 10 REFERENCES .............................................................................................................................................. 27 5 Philips Semiconductors 90W Resonant SMPS with TEA1610 SwingChipTM 1 Application Note AN99011 INTRODUCTION The TV and monitor market demands more and more high-quality, reliable, small, lightweight and efficient power supplies. In principle the higher the operating frequency the smaller and lighter the transformers, filter inductors and capacitors can be. A remark on this is that the core and winding losses of the transformer will increase at higher frequencies. and become dominant. This effect reduces the efficiency at a high frequency, which limits the minimum size of the transformer. The corner frequency of the output filter usually determines the band width of the control loop. A well chosen corner frequency allows high operating frequencies for achieving a fast dynamic response. power applications. A disadvantage of these converters is that the PWM rectangular voltage and current waveforms cause turn-on and turn-off losses that limit the operating frequency. The rectangular waveforms generate also broad band electromagnetic energy, what can produce Electromagnetic Interference (EMI). A resonant DCDC converter produces sinusoidal waveforms and reduces the switching losses, what gives the possibility to operate at higher frequencies The resonant converter can be separated into three cascaded blocks: a AC-to-DC mains rectifier, a DCto-AC inverter and an AC-to-DC output rectifier (figure 2 represents the last two blocks: the inverter and the output rectifier). At this moment the Pulse Width Modulated power converters, such as the fly back, up and down converter, are widely used in low and medium 2 FEATURES • • • • • • Full mains input range 85-276VAC Continuous Output Power 90W Output voltages: 190V, 80V, +13V, +5V, -6.2V and -13V Zero voltage switching (EMI friendly) Main output short circuit proof 7 Philips Semiconductors 90W Resonant SMPS with TEA1610 SwingChipTM 3 Application Note AN99011 QUICK REFERENCE DATA SYMBOL PARAMETER CONDITIONS MIN. TYP. MAX. UNIT Supply Vline mains voltage nominal operation 85 276 VAC fline mains frequency nominal operation 50 / 60 Hz 80.0 VDC Output voltages VOUT1 main output voltage all conditions VOUT1,fl 100Hz ripple Vline= 230VAC, IOUT1=250 mA 75 mVACpp VOUT1,fs high frequency ripple Vline= 230VAC, IOUT1=250 mA 50 mVACpp ∆VOUT1,line line regulation 100 mVDC ∆VOUT1,load load regulation 10 mVDC IOUT1 main output current 135 225 mADC VOUT2 output 2 voltage 193.0 193.9 VDC IOUT2 output 2 current 190 243 mADC VOUT3 output 3 voltage 12.4 13.0 VDC IOUT3 output 3 current 670 890 mADC VOUT4 output 4 voltage -12.4 -11.7 VDC IOUT4 output 4 current 240 890 mADC VOUT5 output 5 voltage -6.3 -6.4 VDC IOUT5 output 5 current 650 mA VOUT6 output 6 voltage 5.0 IOUT6 output 6 current 43 10 – 100% load 192.3 11.7 -12.9 -6.3 VDC 50 mA Miscellaneous tSTART start-up time η efficiency PMAX maximum output power 600 measured at maximum load, spread over VOUT1 and VOUT2 89 91 90 VOUT5 and VOUT6 are post regulated. 8 msec 92 % W Philips Semiconductors 90W Resonant SMPS with TEA1610 SwingChipTM 4 Application Note AN99011 FUNCTIONAL BLOCK DIAGRAM Figure 1 shows the functional block diagram of the application. The topology which is used is the half bridge resonant converter. A reduction of EMI and especially self-pollution is achieved by zero voltage switching (ZVS) in the MOSFETs and output diodes. Another advantage of ZVS are the lower switching losses. Figure 2 shows the basic circuit of the LLC-converter, which represents the blocks ‘Half bridge switches’, ‘Transformer’ and ‘Output section’. The DC-input voltage is converted by the switches into a block voltage with a duty cycle of 50%. The LLC circuit converts this block voltage to a sinusoidal current through its components and a sinusoidal voltage across the resonant capacitor Cr. This capacitor is acting at the same time as blocking element for DC. The transformer reflects (with winding ratio) the voltage across Lp to the secondary, where it is rectified and smoothed by the output capacitor. Mains isolation Mains input circuit Half bridge switches Transformer Output section TEA1610 7[MRK'LMT Optocoupler Regulator Controller Figure 1 Functional block diagram The auxiliary winding which supplies the controller has a good coupling with the output voltage and monitored by the controller. When this voltage becomes too high the converter will be switched off, this is called Over Voltage Protection (OVP). The primary resonant current is also guarded to protect the MOSFETs in fault conditions, when the current becomes too high, this is called Over Current Protection (OCP). One of the output voltages, the 80V-supply, is controlled by means of a secondary regulator circuit that communicates with the TEA1610 controller section by means of an opto coupler, which is used for mains isolation. 9 Philips Semiconductors 90W Resonant SMPS with TEA1610 SwingChipTM 5 Application Note AN99011 CIRCUIT DESCRIPTION 5.1 Mains input circuit 5.2 The input circuit is a conventional full bridge rectifier. A common mode filter is included for mains conducted EMI suppression. A degaussing circuit is not included. A standard PTC degaussing circuit can be added. To gain full advantage in terms of power consumption in the ‘OFF’ mode a circuit to switch-off the degaussing PTC during these modes should be added. The body diodes D1 and D2 of the half bridge MOSFETs are conducting during a part of the primary resonant current. The capacitors C1 and C2 (see Figure 2) are the voltage resonant capacitors which are reducing the TURN-OFF dissipation and so the EMI produced by each MOSFET by a proper dV/dt. Inverter C1 S1 Half bridge switches Output rectifier D1 Ct Vin DC Lr D C2 S2 D2 Lp D Vout Ls D D Co RL Figure 2 Basic circuit LLC-converter 5.3 Transformer 5.4 The inductors Lr and Lp are combined on a single mains-isolated transformer with a poor coupling factor between primary and secondary. In this case the transformer behaves as an ideal transformer having a magnetising inductance Lp with a primary (Lr_p) and a secondary leakage inductance (Lr_s) transferred to the primary (Lr = Lr_p +Lr_s’). The transformer is designed to have an output voltage of 6.67V per turn. The output voltage can be chosen in 6.67V steps minus one diode forward drop. Output section Three types of rectifiers are used. A bridge rectifier for the 190V, a centre-tapped double side rectifier for the 80V and single side rectifiers for the +13 and –13V supplies. All these voltage contains a π-output filter(C-L-C). The 5V and –6.2V supply are derived out of the +13V and –13V respectively. 10 Philips Semiconductors 90W Resonant SMPS with TEA1610 SwingChipTM 5.5 Regulation, controller opto coupler Application Note AN99011 Table 1 and figures 4 to 8 show the load regulation of Vout1 and the (cross) load regulation of the other outputs. With regard to a comparable fly back converter this is a extremely good cross regulation and The TEA1610 can be used either with primary sensing as well as secondary sensing. Primary sensing is cheaper but output regulation is less accurate, especially in this application where the coupling of the primary and secondary is made purposely poor. Secondary sensing is more expensive but has a higher performance. For that reason this 90W application uses secondary sensing. Component Z1 (see chapter 7, page 19) is a TL431 voltage regulator that feeds an error signal through OC1 (CNX82A opto coupler) back to the control input IRS of the TEA1610. The TEA1610 uses this information to control an internal frequency modulator (FM). The FM is connected to the (high and low) output gate drivers to control the MOSFETs. The supply is designed to operate at a 50% duty cycle per MOSFET. When less output power is required or the input voltage is increased the frequency will be made higher by the control loop to maintain a constant output voltage. To guarantee an accurate 50% duty cycle, the oscillator signal inside the TEA1610 passes through a divider before it is fed to the output gate drivers. 5.6 Start-up The TEA1610 is supplied by the applied voltage on the Vdd pin. At a Vdd voltage of 4V the low side MOSFET is conducting and the high side MOSFET is does not conduct. This start-up output state guarantees the initial charging of the bootstrap capacitor which is used for the floating supply of the high side driver. During start-up, the voltage across the frequency capacitor C17 is zero to have a defined start-up. The output voltage of the error amplifier is kept on a constant voltage of 2.7V, which forces a current through R4 that results in a maximum starting frequency (fmax). The start-up state will be maintained until the Vdd voltage reaches the start level of 13.5V, the oscillator is activated and the converter starts operating The total start-up time is low (less than approx. 600ms.) and no overshoots are presented on Vout1 (80V) during start-up. The initial primary start-up current is kept lower than the OCP level. This is done via the soft start option of the TEA1610 via soft start capacitor C31. Soft start can also be done secondary with an additional circuit R11, R18, C22 and D16. A disadvantage of this circuit is that during the first switching stage the primary current can still be higher than the OCP level. With the TEA1610 this circuit is not necessary and via the soft start capacitor this disadvantage will be avoided. Figure 6 shows the load step response (-49dB) of the supply. Output voltage Vout1 shows an overshoot of 260 mV during high (100%) to low (10%) load step. During a low (10%) to high (100%) load step an undershoot of 288 mV occurs. Figure 7 shows 100Hz line suppression (-62dB) at main output voltage Vout1. Only 63.6 mV peak-peak ripple is present at the output under worst case (low line voltage, high output load) conditions. Figure 8 shows the 77 kHz switching frequency ripple (-65dB) present at the output The switching frequency ripple is about 43 mV under worst case conditions. 11 Philips Semiconductors 90W Resonant SMPS with TEA1610 SwingChipTM 5.7 Protections 5.7.1 Under Voltage Lock Out (UVLO) and Short Circuit Protection When the voltage level Vaux becomes too low the controller stops its operation (UVLO). This feature enables the safe restart mode during which the controller is alternately active and not active. When the main output (Vout1) gets short circuited, the controller supply voltage Vaux will drop because the transformer take-over winding 1-2 fails to charge capacitors C17 and C20. Vaux drops below UVLO and the controller enters safe restart mode. This situation persists until the short circuit is removed. 5.7.2 Over Voltage Protection (OVP) When the voltage level Vaux becomes too high the controller also stops its operation (OVP). Because Vaux is a reflection of the output voltage, this feature limits the output voltage level. 5.7.3 Over Current Protection (OCP) When the (primary) resonant current becomes too large the controller stops its operation This protect the MOSFETs for failure due to large currents. The current is measured by R35, that converts it to a voltage, which can activate the ShutDown (SD) via D14. During start-up the first period of the resonant current contains an amplitude that exceeds the OCP_level. To avoid that the controller stops its operation the SD is kept low during start-up for a short while (about 600ms), with an additional circuit, see chapter7, page 20. 12 Application Note AN99011 Philips Semiconductors 90W Resonant SMPS with TEA1610 SwingChipTM 6 Application Note AN99011 MEASUREMENTS 6.1 Static performance Output Load IOUT1=30mA IOUT1=75mA IOUT1=150mA I OUT1=250mA 80.0 V 80.0 V 80.0 V 80.0 V 193.0 V 192.7 V 192.5 V 192.3 V 12.9 V 12.5 V 12.2 V 11.7 V - 12.9 V - 12.4 V - 12.1 V - 11.7 V - 6.38 V - 6.38 V - 6.32 V 5.03 V 5.03 V 193.2 V 193.0 V 192.7 V 192.5 V 12.9 V 12.6 V 12.3 V 11.8 V - 12.9 V - 12.4 V - 12.2 V - 11.7 V - 6.38 V - 6.38 V - 6.32 V 5.03 V 5.03 V 193.6 V 193.2 V 193.0 V 192.8 V 12.9 V 12.6 V 12.4 V 12.0 V - 12.9 V - 12.5 V - 12.3 V - 11.8 V - 6.38 V - 6.38 V - 6.32 V 5.03 V 5.03 V 193.9 V 193.5 V 193.2 V 193.0 V 13.0 V 12.7 V 12.5 V 12.1 V - 12.9 V - 12.5V - 12.3 V - 11.9 V - 6.38 V - 6.38 V - 6.32 V 5.03 V 5.03 V VOUT1 80V VOUT2 190V VOUT3 13V VOUT4 -13V VOUT5 -6.2V VOUT6 5V 30mA 75mA 150mA 250mA 0 mA 250 mA 500 mA 1.00 A 0 mA 250 mA 500 mA 1.00 A 0 mA 325mA 650mA 0 mA 50 mA Table 1 Load and cross load regulation (@Vline=230VRMS), all measured values are in VDC, with –6.3V and 5.0V post regulated. Vline (VRMS) POUT (W) PIN(W) Efficiency (%) 90 0 7.1 - 42.4 54.0 79 85.6 102.6 83 0 8.8 - 42.4 54.7 78 85.6 103.4 83 0 9.8 - 42.4 56.2 75 85.6 103.4 83 230 276 Table 2 Efficiency performance (@ load spread over all outputs), with –6.3V and 5.0V post regulated. 13 Philips Semiconductors 90W Resonant SMPS with TEA1610 SwingChipTM Application Note AN99011 Vline (VRMS) POUT (W) PIN(W) Efficiency (%) 90 0 6.8 - 44.3 53.7 82 89.3 102.3 87 0 6.7 - 44.3 52.6 84 89.3 101.3 88 0 6.8 - 44.3 53.2 83 89.3 100.4 89 230 276 Table 3 Efficiency performance (@ load spread over all outputs). minus the losses in start-up resistor and with the improved transformer, which contains a separate winding for the –6.3V. Measurements of table 2, and 3 are done with load spread over all outputs !!!!!!!! 14 Philips Semiconductors 90W Resonant SMPS with TEA1610 SwingChipTM Application Note AN99011 100 90 80 70 60 η (%) 50 n 85Vac(%) 40 n 276Vac(%) 30 20 10 0 0 20 40 60 80 100 POUT (W) Figure 3 Efficiency as function of the output power, measurement done with load spread over VOUT1 and VOUT2 NOTE: The load in the graph above is spread over two outputs. Because of that the diode losses are less and the measured efficiency is better than that of table 2 and 3, where the load is spread over all outputs. Temperature measurements @ Tambient=21°C: TCORE = 46°C → ∆T = 25°C (near air gap) TWIRE = 45°C → ∆T = 24°C THEAT SINK = 43°C → ∆T = 22°C (near MOSFETs) TBODY MOSFET = 42°C → ∆T = 21°C TTIE POINT MOSFET = 46°C → ∆T = 25°C TTIE POINT 190V DIODE = 46°C → ∆T = 25°C TTIE POINT 80V DIODE = 41°C → ∆T = 20°C 15 Philips Semiconductors 90W Resonant SMPS with TEA1610 SwingChipTM 6.2 Application Note AN99011 Dynamic performance 600 100 600ms Figure 4 Start-up behauviour(@Vline=230VAC, IOUT=250mA) Figure 5 Start-up behauviour(@Vline=230VAC, IOUT=250mA) PV 63.6mV 20.0 Figure 6 Load step response(@Vline=230VAC, IOUT=25 250mA) Figure 7 VOUT1 100Hz ripple (@VLINE=90VAC, IOUT1=250mA) Figure 6 → 288mV load step response = -49dB Figure 7 → 63.6mV 100Hz ripple = -62dB Figure 8 → 43mV 77kHz ripple = -65dB 43mV 50.0 Figure 8 VOUT1 77kHz ripple (@VLINE=90VAC, IOUT1=250mA) 16 Philips Semiconductors 90W Resonant SMPS with TEA1610 SwingChipTM 6.3 Bode diagrams Figure 9 Bode plot control loop with Vin = 85V AC at full load Figure 10 Bode plot control loop with Vin = 276VAC at full load 17 Application Note AN99011 Philips Semiconductors 90W Resonant SMPS with TEA1610 SwingChipTM 6.4 Application Note AN99011 EMI results Figure 11 CISPR13/22 measurement ROUT2=659Ω, IOUT1=293mA, IOUT2=293mA (150kHz-30MHz) 18 (@Vline=230VAC, ROUT1=273Ω, Philips Semiconductors CIRCUIT DIAGRAM 7 A B C D E F 85-270V P1 value R34 is changed to 24k 1 C3 1 3 L1 CU20d3_4 4 470nF 2 ** C2 Cres R1 3.9 AC07 2 ** C1 2.2nF ** C4 2.2nF 2 D2 BYW54 D4 BYW54 D1 BYW54 D6 C5 220uF 400V 130k R33 3 R2 47k PR03 ** C15 R34 16k 100nF R28 Vaux BYW54 Vaux R27 4.7M VR25 ** C28 2.2nF ** C8 220nF C17 1nF ** C32 100pF GND_AN 4.7M VR25 3 R3 12k R8 130k 9 SGND 10 GL 11 VDD 12 IFS 13 CF 14 IRS 15 SD 16 Vref IC1 FVDD GH SH GND I- 4 8 7 6 5 4 3 1 2 GND_AN 1N4148 D14 I+ VCO PGND TEA1601 TEA1610 -13V 4 ** C9 220nF Z3 BZX79C 6V8 R30 330 TR1 TR2 R4 39k PR02 R39 3.9 C31 68nF BD140 TR6 R31 6.8k PHP8N50E PHP8N50E F1 2 Additional circuit for correct start-up with OCP: Ra=33k Rb=68k TRa=BC548B Ca=10µF_16V (see page 20) 2 1 1 2A FUSE components not visible in circuit diagram: Za=BZX15V between pin11 and pin 9 of TEA1610 1 C10 470pF C13 D15 1N4148 Vaux 470pF C27 4.7uF 25V 5 Vres C30 270pF ** C14 22nF D12 7 6 T1 ETD34 11 8 9 14 13 10 12 11 1 6 6 Monday, March 1, 1999 180V 7 L2 10uH C7 C21 GND_AN 22uF 100V GND_AN R11 15k ** C22 220nF R18 1k GND_AN 5V Project: GND_AN GND_AN 5V GND_AN -6.2V 13V 8 8 1 2 3 4 5 6 7 8 9 P2 180V GND_AN 80V GND_AN 13V 5V GND_AN -6.2V -13V -13V Size: A3 Drwg: 130 - 1 / 1 80W Resonant SMPS PR39461 Sheet Name: Philips Semiconductors B.V. Eindhoven The Netherlands GND_AN C12 GND_AN C6 80V GND_AN 22uF 250V L3 10uH C16 47uF 250V L4 10uH C40 1nF D16 1N4148 C26 1uF 50V Engineer: Roger Kennis Drawn by: I.Lodema Changed by: 7 12:35:44 pm ilodema 22uF 100V C11 13V R17 3.3k R10 120k L5 -13V 10uH 22uF 200V IC2 OUT Time Changed: GND_AN GND_AN R38 1k ** C24 47nF 100uF 160V R7 330 GND_AN C18 100uF 63V R14 2.7k GND_AN GND LM78L05AC ** C23 2.2nF C19 63V BYV27-100 100uF D13 D11 BYV27-100 D8 D3 4 x BYV27-400V D5 D7 D9 BYV27-200 R36 0 n.m. R37 0 D17 BYV27-100 n.m. GND_AN GND_AN ** IN C25 100nF GND_AN PHILIPS 10 R23 Z1 TL431C D10 BYV27-200 GND_AN SEMICONDUCTORS PS-SLE CONSUMER2 13V 2 1 11 5 4 2 R13 1k Date Changed: PHILIPS 100nF ** C29 CNX82A OC1 47uF 63V C20 BAV21 R35 68 R12 -6.2V 62k 5 A B C D E F 19 Application Note AN99011 90W Resonant SMPS with TEA1610 SwingChipTM Philips Semiconductors 90W Resonant SMPS with TEA1610 SwingChipTM Additional circuit for correct start-up with OCP: Vaux Ca 10uF/16V TEA1610 Ra 33k 15 SD TRa BC548B Rb 68k 20 Application Note AN99011 Philips Semiconductors 90W Resonant SMPS with TEA1610 SwingChipTM 8 Application Note AN99011 LAYOUT CONSIDERATIONS See next page for the implementation. General guidelines: q q q q Minimise area of loops that carry high dI/dt current transients (transformer in- and output loops) Minimise area of traces and components with high dV/dt voltage excitation; reduce trace lengths and component size Keep functional circuit blocks close together Keep transformer, resonance capacitor C14, TEA1610 and input capacitor C5 as close as possible to each other such that the main current loop area is as small as possible Layout flow: 1. Start layout with high current (large signal) primary circuit: q Minimise high current AC-loop area (transformer, TEA1610, input capacitor C5) q Minimise bridge traces (TEA1610 pin6, source TR1 and drain TR2) surface area q Minimise dV/dt limiter loop areas (C10 and C13 close as possible to MOSFETs) 2. Continue with the output AC loops: q Minimise AC loop areas (start with high current output) 3. Continue with the controller section: q Compact set-up q Keep Signal Ground (SGND) and Power Ground (PGND) separated on PCB, but short connection of pin4 to pin9 4. Continue with regulator section: q Compact set-up 5. GND of input capacitor C5 with a short track via safety capacitor C28 to output capacitor C6 and C11 6. Avoid HF interference between mains filter section (C2, L1, C3) and connector P1 coming from circuits that carry high dI/dt’s (magnetic interference) 21 Philips Semiconductors 90W Resonant SMPS with TEA1610 SwingChipTM 22 Application Note AN99011 Philips Semiconductors 90W Resonant SMPS with TEA1610 SwingChipTM 23 Application Note AN99011 Philips Semiconductors 90W Resonant SMPS with TEA1610 SwingChipTM 24 Application Note AN99011 Philips Semiconductors 90W Resonant SMPS with TEA1610 SwingChipTM 9 Application Note AN99011 PARTS LIST REFERENCE Capacitors C1 C4 C28 C2 C3 C5 C6 C7 C8 C9 C10 C13 C11 C12 C14 C15 C25 C29 C16 C21 C17 C18 C19 C20 C22 C23 C24 C26 C27 C30 C31 C32 Diodes D1 D2 D4 D6 D3 D5 D7 D8 VALUE 2.2nF Cres 470nF 220uF 47uF 22uF 220nF 220nF 470pF 100uF 22uF 22nF 100nF 22uF 100pF 100uF 47uF 220nF 22nF 47nF 1uF 4.7uF 270pF 68nF 1nF BYW54 BYV27400 D9 D10 BYV27200 D11 D13 BYV27100 D12 BAV21 D14 D15 D16 1N4148 D17 BYV27100 Fuse F1 2A Ics IC1 TEA1610 IC2 LM78L05 AC SERIES MKP 336 MKT-P 330 MKP 336 PSM-SI 057 RLH 151 RLH 151 MKT 368 MKT 370 C655 RLH 151 RLH 151 KP/MMKP 376 MKT 370 RVI136 NP0 RVI136 RSM 037 MKT 465 MKT 370 MKT 370 RLP5 134 RLP5 134 C655 X7R MKT 370 TOL RATING 20% 250V 20% 250V 20% 275V 20% 400V 20% 250V 20% 250V 10% 400V 10% 63V 10% 500V 20% 160V 20% 200V 5% 1000V 10% 63V 20% 100V 5% 50V 20% 63V 20% 63V 10% 100V 10% 100V 10% 100V 20% 50V 20% 25V 10% 500V 10% 50V 10% 400V GEOMETRY 12NC_NO C_B6_L12.5_P10mm C_B10_L26_P22mm5 C_B10_L26_P22mm5 CASE_3050 CASE_R19 CASE_R19a C368_I C370_C CER2_2A CASE_R19 CASE_R16 C_B8.5_L26_P22mm5 C370_B CASE_R14 C0805 CASE_R15 CASE_R13_m C_B4.5_L8_P5mm C370_A C370_A CASE_R51_CA CASE_R52_CA CER2_1 C0805 C370_A 2222-336-60222 2222-330-40334 2222-336-20474 2222-057-36221 2222-151-63479 2222-151-93229 2222-368-55224 2222-370-21224 2222-655-03471 2222-151-61101 2222-151-62229 2222-376-72223 2222-370-21104 2222-136-69229 2222-861-12101 2222-136-68101 2222-037-58479 2222-465-06224 2222-370-21223 2222-370-21473 2222-134-51108 2222-134-56478 2222-655-03271 2222-590-16638 2222-370-51102 Rectifier Rectifier 600V 400V SOD57 SOD57 9333-636-10153 9340-366-90133 Rectifier 200V SOD57 9335-526-80112 Rectifier 100V SOD57 9335-435-00133 100V SOD27 SOD27 SOD57 9331-892-10153 9330-839-90153 9335-435-00133 SLOW GLAS_HOLDER 2412-086-28239 IC_Universal Stab_Pos SOT38_s TO92 Gen_Purpose Gen_Purpose Rectifier 25 Philips Semiconductors 90W Resonant SMPS with TEA1610 SwingChipTM Inductors L2 L3 L4 L5 10uH TSL0709 Opto coupler OC1 CNX82A CNX Connectors P1 MKS373 MKS3730 0_2p_22 0V P2 MKS373 MKS3730 0_9p Resistors R1 3.3 AC07 R2 47k PR03 R3 12k RC01 R4 39k RC01 R7 470 SFR25H R8 130k RC01 R10 120k SFR25H R11 15k SFR25H R12 62k SFR25H R13 R18 1k SFR25H R14 2.7k SFR25H R17 3.3k SFR25H R23 10 SFR25H R27 R28 4.7M VR25 R30 330 SFR25H R31 6.8k SFR25H R33 120k SFR25H R34 24k SFR25H R35 68 SFR25H R36 n.m. SFR25H R37 0 SFR25H R38 1k 3296Y R39 3.9 PR02 Transistors TR1 TR2 PHP8N5 fets 0E TR6 BD140 Pow_Low_Freq Transformer T1 ETD34 Switch_Mode Zener diodes Z1 X Misc Z3 BZX79C BZX79C 10% Application Note AN99011 TSL0707_2e SOT231 9338-846-80127 MKS3730_2p_220V MKS3730_9p 5% 7W 5% 3W 5% 0.25W 5% 0.25W 5% 0.5W 5% 0.25W 5% 0.5W 5% 0.5W 5% 0.5W 5% 0.5W 5% 0.5W 5% 0.5W 5% 0.5W 5% 0.25W 5% 0.5W 5% 0.5W 5% 0.5W 5% 0.5W 5% 0.5W 5% 0.5W 5% 0.5W 10% 0.5W 5% 2W 6V8 26 AC07 PR03 R1206 R1206 SFR25H R1206 SFR25H SFR25H SFR25H SFR25H SFR25H SFR25H SFR25H VR25 SFR25H SFR25H SFR25H SFR25H SFR25H SFR25H SFR25H BO3296Y PR02 2322-329-07338 2322-195-13473 2322-711-61123 2322-711-61393 2322-186-16471 2322-711-61134 2322-186-16124 2322-186-16153 2322-186-16623 2322-186-16102 2322-186-16272 2322-186-16332 2322-186-16109 2322-241-13475 2322-186-16331 2322-186-16682 2322-186-16124 2322-186-16243 2322-186-16689 2322-181-90019 2322-181-90019 2122-362-00723 2322-194-13398 TO220 9340-438-80127 TO126 9330-912-30127 ETD34 8228-001-34471 TO226AA SOD27 9331-177-50153 Philips Semiconductors 90W Resonant SMPS with TEA1610 SwingChipTM Application Note AN99011 10 REFERENCES 1 M.K. Kazimierczuk & D. Czarkowski, Resonant Power Converters, 1995 Wiley Intersience, ISBN 0-471-04706-6 27