MIC2207 DATA SHEET (11/05/2015) DOWNLOAD

MIC2207
3mm x 3mm 2MHz 3A PWM Buck
Regulator
General Description
Features
The Micrel MIC2207 is a high-efficiency PWM buck (stepdown) regulators that provides up to 3A of output current.
The MIC2207 operates at 2MHz and has proprietary
internal compensation that allows a closed loop bandwidth
of over 200KHz.
The low on-resistance internal p-channel MOSFET of the
MIC2207 allows efficiencies over 94%, reduces external
components count and eliminates the need for an
expensive current sense resistor.
The MIC2207 operates from 2.7V to 5.5V input and the
output can be adjusted down to 1V. The devices can
operate with a maximum duty cycle of 100% for use in lowdropout conditions.
The MIC2207 is available in the exposed pad 12-pin
3mm x 3mm MLF® package with a junction operating
range from –40°C to +125°C.
Data sheets and support documentation can be found on
Micrel’s web site at: www.micrel.com.
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•
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2.7 to 5.5V supply voltage
2MHz PWM mode
Output current to 3A
>94% efficiency
100% maximum duty cycle
Adjustable output voltage option down to 1V
Ultra-fast transient response
Ultra-small external components
Stable with a 1µH inductor and a 4.7µF output capacitor
Fully integrated 3A MOSFET switch
Micropower shutdown
Thermal shutdown and current limit protection
Pb-free 12-pin 3mm x 3mm MLF® package
–40°C to +125°C junction temperature range
Applications
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5V or 3.3V Point of Load Conversion
Telecom/Networking Equipment
Set Top Boxes
Storage Equipment
Video Cards
DDR Power Supply
Typical Application
96
3.3V
4.5V
EFFICIENCY (%)
94
MIC2207
MIC2207
Efficiency
OUT
IN
92
90
88
5V
IN
5.5V
IN
86
84
82
3A 2MHz Buck Regulator
80
0
0.5
1
1.5
2
2.5
OUTPUT CURRENT (A)
3
MLF and MicroLeadFrame are registered trademarks of Amkor Technology, Inc.
Micrel Inc. • 2180 Fortune Drive • San Jose, CA 95131 • USA • tel +1 (408) 944-0800 • fax + 1 (408) 474-1000 • http://www.micrel.com
April 2010
M9999-041910
Micrel, Inc.
MIC2207
Ordering Information
Part Number
Output Voltage(1)
Junction Temp. Range
Package
Lead Finish
MIC2207YML
Adj.
–40° to +125°C
12-Pin 3mm x 3mm MLF®
Pb-free
Note:
1. Other Voltage options available. Contact Micrel for details.
Pin Configuration
SW 1
12 SW
VIN 2
11 VIN
PGND 3
10 PGND
SGND 4
9 PGOOD
8 EN
BIAS 5
FB 6
7 NC
EP
12-Pin 3mm x 3mm MLF® (ML)
Pin Description
Pin Number
Pin Name
Pin Function
1,12
SW
Switch (Output): Internal power P-Channel MOSFET output switch
2,11
VIN
Supply Voltage (Input): Supply voltage for the source of the internal P-channel
MOSFET and driver.
3,10
PGND
Power Ground. Provides the ground return path for the high-side drive current.
4
SGND
Signal (Analog) Ground. Provides return path for control circuitry and internal
reference.
5
BIAS
6
FB
Feedback. Input to the error amplifier, connect to the external resistor divider
network to set the output voltage.
7
NC
No Connect. Not internally connected to die. This pin can be tied to any other pin
if desired.
8
EN
Enable (Input). Logic level low will shutdown the device, reducing the current
draw to less than 5µA.
9
PGOOD
EP
GND
Requires bypass capacitor to GND.
April 2010
Internal circuit bias supply. Must be bypassed with a 0.1µF ceramic capacitor to
SGND.
Power Good. Open drain output that is pulled to ground when the output voltage
is within ±7.5% of the set regulation voltage
Connect to ground.
2
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Micrel, Inc.
MIC2207
Absolute Maximum Ratings(1)
Operating Ratings(2)
Supply Voltage (VIN) .......................................................+6V
Output Switch Voltage (VSW) ..........................................+6V
Output Switch Current (ISW)............................................11A
Logic Input Voltage (VEN) .................................. –0.3V to VIN
Storage Temperature (Ts) .........................–60°C to +150°C
ESD Rating(3) .................................................................. 2kV
Supply Voltage (VIN)..................................... +2.7V to +5.5V
Logic Input Voltage (VEN) ....................................... 0V to VIN
Junction Temperature (TJ) ........................ –40°C to +125°C
Junction Thermal Resistance
3x3 MLF-12L (θJA) .............................................60°C/W
Electrical Characteristics(4)
VIN = VEN = 3.6V; L = 1µH; COUT = 4.7µF; TA = 25°C, unless noted. Bold values indicate –40°C ≤ TJ ≤ +125°C.
Parameter
Condition
Min
Supply Voltage Range
Under-Voltage Lockout
Threshold
Typ
2.7
(turn-on)
2.45
UVLO Hysteresis
2.55
Max
Units
5.5
V
2.65
V
100
Quiescent Current
VFB = 0.9 * VNOM (not switching)
570
Shutdown Current
VEN = 0V
[Adjustable] Feedback
Voltage
± 1% ILOAD = 100mA
± 2% (over temperature) ILOAD = 100mA
0.99
0.98
FB pin input current
mV
900
µA
2
10
µA
1
1.01
1.02
V
1
nA
Current Limit in PWM Mode
VFB = 0.9 * VNOM
5
A
Output Voltage
Line Regulation
VOUT > 2V; VIN = VOUT + 500mV to 5.5V; ILOAD = 100mA
VOUT < 2V; VIN = 2.7V to 5.5V; ILOAD = 100mA
0.07
%
Output Voltage
Load Regulation
20mA < ILOAD < 3A
0.2
Maximum Duty Cycle
VFB ≤ 0.4V
PWM Switch ON-Resistance
ISW = 50mA; VFB = 0.7VFB_NOM (High Side Switch)
3.5
0.5
%
%
100
95
200
mΩ
300
Oscillator Frequency
1.8
2
2.2
MHz
Enable Threshold
0.5
0.85
1.3
V
Enable Hysteresis
50
Enable Input Current
0.1
2
µA
Power Good Range
±7
±10
%
145
250
Ω
Power Good Resistance
IPGOOD = 500µA
mV
Over-Temperature Shutdown
160
°C
Over-Temperature Hysteresis
20
°C
Notes:
1. Exceeding the absolute maximum rating may damage the device.
2. The device is not guaranteed to function outside its operating rating.
3. Devices are ESD sensitive. Handling precautions recommended. Human body model, 1.5k in series with 100pF.
4. Specification for packaged product only.
5. Dropout voltage is defined as the input-to-output differential at which the output voltage drops 2% below its nominal value that is initially measured at
a 1V differential. For outputs below 2.7V, the dropout voltage is the input-to-output voltage differential with a minimum input voltage of 2.7V.
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MIC2207
Typical Characteristics
5VIN
5.5V
IN
88
86
84
82
95
93
0.5
1
1.5
2
2.5
OUTPUT CURRENT (A)
1.8V
EFFICIENCY (%)
3
MIC2207
Efficiency
OUT
87
3.3V
83
IN
3.6VIN
81
79
77
75
0
85
83
0.5
1
1.5
2
2.5
OUTPUT CURRENT (A)
1.5V
3
MIC2207
Efficiency
OUT
IN
IN
71
69
0.5
1
1.5
2
2.5
OUTPUT CURRENT (A)
1V
81
EFFICIENCY (%)
EFFICIENCY (%)
5VIN 5.5V
73
85
83
MIC2207
Efficiency
OUT
71
April 2010
0.5
1
1.5
2
2.5
OUTPUT CURRENT (A)
80
1.8V
MIC2207
Efficiency
OUT
3.3V
IN
3.6VIN
5VIN 5.5V
IN
74
0.5
1
1.5
2
2.5
OUTPUT CURRENT (A)
1.2V
0.5
1
1.5
2
2.5
OUTPUT CURRENT (A)
3
5V
IN
5.5V
IN
84
MIC2207
Efficiency
OUT
80
80
3.3V
IN
3.6V
74
IN
0.5
1
1.5
2
2.5
OUTPUT CURRENT (A)
1V
MIC2207
Efficiency
OUT
IN
5V
IN
5.5VIN
65
0.5
1
1.5
2
2.5
OUTPUT CURRENT (A)
4
3
3V
3.3V
IN
3.6VIN
0.5
1
1.5
2
2.5
OUTPUT CURRENT (A)
1.2V
3
MIC2207
Efficiency
OUT
4.5V
IN
77
75
73
5VIN 5.5V
IN
71
69
1.010
4.5V
75
OUT
79
67
65
0
3
MIC2207
Efficiency
75
85
83
IN
76
1.5V
3
IN
70
0
3
3V
82
0.5
1
1.5
2
2.5
OUTPUT CURRENT (A)
85
81
84
60
0
86
90
76
70
IN
88
95
4.5VIN
78
78
4.5V
90
80
0
3
80
69
67
65
0
82
MIC2207
Efficiency
OUT
82
84
85
77
73
84
72
70
0
3
3VIN
79
75
IN
86
75
67
65
0
3.6V
86
90
88
4.5V
EFFICIENCY (%)
EFFICIENCY (%)
77
IN
88
72
70
0
81
79
3.3V
86
89
85
90
90
88
3VIN
91
92
82
80
0
EFFICIENCY (%)
80
0
94
2.5V
92
EFFICIENCY (%)
90
94
3VIN
96
92
MIC2207
Efficiency
OUT
EFFICIENCY (%)
IN
EFFICIENCY (%)
EFFICIENCY (%)
100
98
4.5V
94
2.5V
EFFICIENCY (%)
MIC2207
Efficiency
OUT
OUTPUT VOLTAGE (V)
96
3.3V
0.5
1
1.5
2
2.5
OUTPUT CURRENT (A)
3
Load Regulation
1.005
1.000
0.995
0.990
0
VIN = 3.3V
0.5
1
1.5
2
2.5
OUTPUT CURRENT (A)
3
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Micrel, Inc.
MIC2207
120
80
100
40
60
EN
IN
120
80
100
60
40
0
80
75
70
2.7
1
2
3
4
5
SUPPLY VOLTAGE (V)
3.2 3.7 4.2 4.7 5.2
SUPPLY VOLTAGE (V)
Enable Threshold
vs. Temperature
1.2
1.0
0.8
0.6
0.4
0.2
0
2.7
20
-20
-40
120
100
=V
90
85
3.2
3.7
4.2
4.7
SUPPLY VOLTAGE (V)
5
1.0
0.8
0.6
0.4
0.2
0
3.3VIN
120
60
40
V
95
100
ENABLE THRESHOLD (V)
80
20
FREQUENCY (MHz)
100
105
100
1.2
100
0
80
200
110
Enable Threshold
vs. Supply Voltage
120
-20
60
300
DSON
TEMPERATURE (°C)
0
400
0
0
140
20 3.3V
IN
0
20
500
vs. Temperature
160
-40
600
1
2
3
4
5
SUPPLY VOLTAGE (V)
R
April 2010
700
DSON
80
IN
800
120
115
60
=V
R
-20
EN
vs. Supply Voltage
-40
V
Quiescent Current
vs. Supply Voltage
ENABLE THRESHOLD (V)
0.2
TEMPERATURE (°C)
40
0.4
TEMPERATURE (°C)
20
0.6
1.700
1.600 V = 3.3V
IN
1.500
0
0.8
Frequency
vs. Temperature
2.500
2.400
2.300
2.200
2.100
2.000
1.900
1.800
P-CHANNEL RDSON (mOhm)
1
0
0
P-CHANNEL RDSON (mOhm)
900
QUIESCENT CURRENT (µA)
FEEDBACK VOLTAGE (V)
Feedback Voltage
vs. Supply Voltage
-20
0.994
0.992 V = 3.3V
IN
0.990
SUPPLY VOLTAGE (V)
1.2
Feedback Voltage
vs. Temperature
40
1.010
1.008
1.006
1.004
1.002
1.000
0.998
0.996
-40
FEEDBACK VOLTAGE (V)
Typical Characteristics (cont.)
TEMPERATURE (°C)
M9999-041910
Micrel, Inc.
MIC2207
INDUCTOR CURRENT
(200mA/div.)
VIN = 3.3V
VOUT = 1V
L = 1µH
COUT = 4.7µF
IOUT = 1A
TIME (200ns/div.)
TIME (200ns/div.)
Load Transient Response
Output Ripple
OUTPUT VOLTAGE
(10mV/div.)
AC COUPLED
OUTPUT CURRENT
(2A/div.)
Discontinuous Current
VIN = 3.3V
VOUT = 1V
L = 1µH
COUT = 4.7µF
IOUT = 30mA
0A
SWITCH VOLTAGE
(2V/div.)
0A
Continuious Current
SWITCH VOLTAGE
(2V/div.)
INDUCTOR CURRENT
(500mA/div.)
Functional Characteristics
VIN = 3.3V
VOUT = 1.8V
SWITCH VOLTAGE
(2V/div.)
OUTPUT VOLTAGE
(20mV/div.)
0A
IOUT = 3.0A
TIME (400µs/div.)
TIME (400ns/div.)
INPUT CURRENT
ENABLE VOLTAGE
(1A/div.)
(2V/div.)
FEEDBACK VOLTAGE INDUCTOR CURRENT
(2A/div.)
(1V/div.)
Start-Up Waveforms
April 2010
TIME (40µs/div.)
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MIC2207
Functional Diagram
VIN
VIN
P-Channel
Current Limit
BIAS
HSD
SW
SW
PWM
Control
EN
Enable and
Control Logic
Bias,
UVLO,
Thermal
Shutdown
Soft
Start
EA
FB
1.0V
PGOOD
1.0V
SGND
PGND
MIC2207 Block Diagram
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MIC2207
Pin Descriptions
SW
The switch (SW) pin connects directly to the inductor
and provides the switching current necessary to operate
in PWM mode. Due to the high speed switching on this
pin, the switch node should be routed away from
sensitive nodes. This pin also connects to the cathode of
the free-wheeling diode.
VIN
Two pins for VIN provide power to the source of the
internal P-channel MOSFET along with the current
limiting sensing. The VIN operating voltage range is from
2.7V to 5.5V. Due to the high switching speeds, a 10µF
capacitor is recommended close to VIN and the power
ground (PGND) for each pin for bypassing. Please refer
to layout recommendations.
PGOOD
Power good is an open drain pull down that indicates
when the output voltage has reached regulation. For a
power good low, the output voltage is within ±10% of the
set regulation voltage. For output voltages greater or
less than 10%, the PGOOD pin is high. This should be
connected to the input supply through a pull up resistor.
A delay can be added by placing a capacitor from
PGOOD to ground.
BIAS
The bias (BIAS) provides power to the internal reference
and control sections of the MIC2207. A 10Ω resistor
from VIN to BIAS and a 0.1µF from BIAS to SGND is
required for clean operation.
EN
The enable pin provides a logic level control of the
output. In the off state, supply current of the device is
greatly reduced (typically <1µA). Do not drive the enable
pin above the supply voltage.
PGND
Power ground (PGND) is the ground path for the
MOSFET drive current. The current loop for the power
ground should be as small as possible and separate
from the Signal ground (SGND) loop. Refer to the layout
considerations fro more details.
FB
The feedback pin (FB) provides the control path to
control the output. For adjustable versions, a resistor
divider connecting the feedback to the output is used to
adjust the desired output voltage. The output voltage is
calculated as follows:
SGND
Signal ground (SGND) is the ground path for the biasing
and control circuitry. The current loop for the signal
ground should be separate from the power ground
(PGND) loop. Refer to the layout considerations for more
details.
⎛ R1 ⎞
VOUT = VREF × ⎜
+ 1⎟
⎝ R2
⎠
where VREF is equal to 1.0V.
A feedforward capacitor is recommended for most
designs using the adjustable output voltage option. To
reduce current draw, a 10K feedback resistor is
recommended from the output to the FB pin (R1). Also, a
feedforward capacitor should be connected between the
output and feedback (across R1). The large resistor
value and the parasitic capacitance of the FB pin can
cause a high frequency pole that can reduce the overall
system phase margin. By placing a feedforward
capacitor, these effects can be significantly reduced.
Feedforward capacitance (CFF) can be calculated as
follows:
C FF =
April 2010
1
2π × R1 × 200kHz
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Micrel, Inc.
MIC2207
During the on-time, the high side switch is turned on,
current flows from the input supply through the inductor
and to the output. The inductor current is
Application Information
The MIC2207 is a 3A PWM non-synchronous buck
regulator. By switching an input voltage supply, and
filtering the switched voltage through an Inductor and
capacitor, a regulated DC voltage is obtained. Figure 1
shows a simplified example of a non-synchronous buck
converter.
Figure 1.
For a non-synchronous buck converter, there are two
modes of operation; continuous and discontinuous.
Continuous or discontinuous refer to the inductor
current. If current is continuously flowing through the
inductor throughout the switching cycle, it is in
continuous operation. If the inductor current drops to
zero during the off time, it is in discontinuous operation.
Critically continuous is the point where any decrease in
output current will cause it to enter discontinuous
operation. The critically continuous load current can be
calculated as follows;
Figure 3. On-Time
charged at the rate;
(VIN − VOUT )
L
To determine the total on-time, or time at which the
inductor charges, the duty cycle needs to be calculated.
The duty cycle can be calculated as;
D=
2⎤
⎡
V
⎢VOUT − OUT ⎥
VIN ⎥⎦
⎢⎣
VOUT =
2MHz × 2 × L
Continuous or discontinuous operation determines how
we calculate peak inductor current.
VOUT
VIN
and the On time is;
D
2MHz
Therefore, peak to peak ripple current is;
TON =
(V IN − VOUT ) × VOUT
Continuous Operation
Figure 2 illustrates the switch voltage and inductor
current during continuous operation.
VIN
2MHz × L
Since the average peak to peak current is equal to the
load current. The actual peak (or highest current the
inductor will see in a steady state condition) is equal to
the output current plus ½ the peak to peak current.
Ipk −pk =
(VIN − VOUT ) × VOUT
Ipk = IOUT +
Figure 4 demonstrates the off-time. During the offtime, the high-side internal P-channel MOSFET turns off.
Since the current in the inductor has to discharge, the
current flows through the free-wheeling Schottky diode
to the output. In this case, the inductor discharge rate is
(where VD is the diode forward voltage);
Figure 2. Continuous Operation
The output voltage is regulated by pulse width
modulating (PWM) the switch voltage to the average
required output voltage. The switching can be broken up
into two cycles; On and Off.
April 2010
VIN
2 × 2MHz × L
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Micrel, Inc.
−
(VOUT
MIC2207
+ VD )
pulses as necessary, reducing gate drive losses,
drastically improving light load efficiency.
L
The total off time can be calculated as;
TOFF =
Efficiency Considerations
Calculating the efficiency is as simple as measuring
power out and dividing it by the power in;
1− D
2MHz
P
Efficiency = OUT × 100
PIN
Where input power (PIN) is;
PIN = VIN × IIN
and output power (POUT) is calculated as;
POUT = VOUT × IOUT
The Efficiency of the MIC2207 is determined by several
factors.
• Rdson (Internal P-channel Resistance)
• Diode conduction losses
• Inductor Conduction losses
• Switching losses
Rdson losses are caused by the current flowing through
the high side P-channel MOSFET. The amount of power
loss can be approximated by;
Figure 4. Off-Time
PSW = R DSON × IOUT 2 × D
Where D is the duty cycle.
Since the MIC2207 uses an internal P-channel
MOSFET, Rdson losses are inversely proportional to
supply voltage. Higher supply voltage yields a higher
gate to source voltage, reducing the Rdson, reducing the
MOSFET conduction losses. A graph showing typical
Rdson vs input supply voltage can be found in the typical
characteristics section of this datasheet.
Diode conduction losses occur due to the forward
voltage drop (VF) and the output current. Diode power
losses can be approximated as follows;
Discontinuous Operation
Discontinuous operation is when the inductor current
discharges to zero during the off cycle. Figure 5.
demonstrates the switch voltage and inductor currents
during discontinuous operation.
PD = VF × IOUT × (1 − D)
For this reason, the schottky diode is the rectifier of
choice. Using the lowest forward voltage drop will help
reduce diode conduction losses, and improve efficiency.
Duty cycle, or the ratio of output voltage to input voltage,
determines whether the dominant factor in conduction
losses will be the internal MOSFET or the schottky
diode. Higher duty cycles place the power losses on the
high side switch, and lower duty cycles place the power
losses on the schottky diode.
Inductor conduction losses (PL) can be calculated by
multiplying the DC resistance (DCR) times the square of
the output current;
Figure 5. Discontinuous Operation
When the inductor current (IL) has completely
discharged, the voltage on the switch node rings at the
frequency determined by the parasitic capacitance and
the inductor value. In figure 5, it is drawn as a DC
voltage, but to see actual operation (with ringing) refer to
the functional characteristics.
Discontinuous mode of operation has the advantage
over full PWM in that at light loads, the MIC2207 will skip
April 2010
PL = DCR × IOUT 2
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MIC2207
Also, be aware that there are additional core losses
associated with switching current in an inductor. Since
most inductor manufacturers do not give data on the
type of material used, approximating core losses
becomes very difficult, so verify inductor temperature
rise.
Switching losses occur twice each cycle, when the
switch turns on and when the switch turns off. This is
caused by a non-ideal world where switching transitions
are not instantaneous, and neither are currents. Figure 6
demonstrates (Or exaggerates…) how switching losses
due to the transitions dissipate power in the switch.
Output Capacitor
The MIC2207 is designed for a 4.7µF output capacitor.
X5R or X7R dielectrics are recommended for the output
capacitor. Y5V dielectrics lose most of their capacitance
over temperature and are therefore not recommended.
In addition to a 4.7µF, a small 0.1µF is recommended
close to the load for high frequency filtering. Smaller
case size capacitors are recommended due to their
lower equivalent series ESR and ESL.
The MIC2207 utilizes type III voltage mode internal
compensation and utilizes an internal zero to
compensate for the double pole roll off of the LC filter.
For this reason, larger output capacitors can create
instabilities. In cases where a 4.7µF output capacitor is
not sufficient, the MIC2208 offers the ability to externally
control the compensation, allowing for a wide range of
output capacitor types and values.
Inductor Selection
The MIC2207 is designed for use with a 1µH inductor.
Proper selection should ensure the inductor can handle
the maximum average and peak currents required by the
load. Maximum current ratings of the inductor are
generally given in two methods; permissible DC current
and saturation current. Permissible DC current can be
rated either for a 40°C temperature rise or a 10% to 20%
loss in inductance. Ensure the inductor selected can
handle the maximum operating current. When saturation
current is specified, make sure that there is enough
margin that the peak current will not saturate the
inductor.
Figure 6. Switching Transition Losses
Normally, when the switch is on, the voltage across the
switch is low (virtually zero) and the current through the
switch is high. This equates to low power dissipation.
When the switch is off, voltage across the switch is high
and the current is zero, again with power dissipation
being low. During the transitions, the voltage across the
switch (VS-D) and the current through the switch (IS-D) are
at midpoint of their excursions and cause the transition
to be the highest instantaneous power point. During
continuous mode, these losses are the highest. Also,
with higher load currents, these losses are higher. For
discontinuous operation, the transition losses only occur
during the “off” transition since the “on” transitions there
is no current flow through the inductor.
Diode Selection
Since the MIC2207 is non-synchronous, a free-wheeling
diode is required for proper operation. A schottky diode
is recommended due to the low forward voltage drop
and their fast reverse recovery time. The diode should
be rated to be able to handle the average output current.
Also, the reverse voltage rating of the diode should
exceed the maximum input voltage. The lower the
forward voltage drop of the diode the better the
efficiency. Please refer to the layout recommendations to
minimize switching noise.
Component Selection
Input Capacitor
A 10µF ceramic is recommended on each VIN pin for
bypassing. X5R or X7R dielectrics are recommended for
the input capacitor. Y5V dielectrics lose most of their
capacitance over temperature and are therefore not
recommended. Also, tantalum and electrolytic capacitors
alone are not recommended because of their reduced
RMS current handling, reliability, and ESR increases.
An additional 0.1µF is recommended close to the VIN
and PGND pins for high frequency filtering. Smaller case
size capacitors are recommended due to their lower
ESR and ESL. Please refer to layout recommendations
for proper layout of the input capacitor.
April 2010
Feedback Resistors
The feedback resistor set the output voltage by dividing
down the output and sending it to the feedback pin. The
feedback voltage is 1.0V. Calculating the set output
voltage is as follows;
⎛ R1 ⎞
VOUT = VFB ⎜
+ 1⎟
⎝ R2
⎠
Where R1 is the resistor from VOUT to FB and R2 is the
resistor from FB to GND. The recommended feedback
resistor values for common output voltages are available
11
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Micrel, Inc.
MIC2207
monitoring A and R for an A/R measurement. While this
is the most common method for measuring the gain and
phase of a power supply, it does have significant
limitations. First, to measure low frequency gain and
phase, the transformer needs to be high in inductance.
This makes frequencies <100Hz require an extremely
large and expensive transformer. Conversely, it must be
able to inject high frequencies. Transformers with these
wide frequency ranges generally need to be custom
made and are extremely expensive (usually to the tune
of several hundred dollars!). By using an op-amp, cost
and frequency limitations caused by an injection
transformer are completely eliminated. Figure 8
demonstrates using an op-amp in a summing amplifier
configuration for signal injection.
in the bill of materials on page 19. Although the range of
resistance for the FB resistors is very wide, R1 is
recommended to be 10K. This minimizes the effect the
parasitic capacitance of the FB node.
Feedforward Capacitor (CFF)
A capacitor across the resistor from the output to the
feedback pin (R1) is recommended for most designs.
This capacitor can give a boost to phase margin and
increase the bandwidth for transient response. Also,
large values of feedforward capacitance can slow down
the turn-on characteristics, reducing inrush current. For
maximum phase boost, CFF can be calculated as follows;
C FF =
1
2π × 200kHz × R1
Network
Analyzer
“R” Input
Bias filter
A small 10Ω resistor is recommended from the input
supply to the bias pin along with a small 0.1µF ceramic
capacitor from bias to ground. This will bypass the high
frequency noise generated by the violent switching of
high currents from reaching the internal reference and
control circuitry. Tantalum and electrolytic capacitors are
not recommended for the bias, these types of capacitors
lose their ability to filter at high frequencies.
+8V
MIC922BC5
Feedback
R3
1k
R4
1k
50
R1
1k
Network
Analyzer
“A” Input
Output
Network Analyzer
Source
Loop Stability and Bode Analysis
Bode analysis is an excellent way to measure small
signal stability and loop response in power supply
designs. Bode analysis monitors gain and phase of a
control loop. This is done by breaking the feedback loop
and injecting a signal into the feedback node and
comparing the injected signal to the output signal of the
control loop. This will require a network analyzer to
sweep the frequency and compare the injected signal to
the output signal. The most common method of injection
is the use of a transformer. Figure 7 demonstrates how a
transformer is used to inject a signal into the feedback
network.
Figure 8. Op Amp Injection
R1 and R2 reduce the DC voltage from the output to the
non-inverting input by half. The network analyzer is
generally a 50Ω source. R1 and R2 also divide the AC
signal sourced by the network analyzer by half. These
two signals are “summed” together at half of their
original input. The output is then amplified by 2 by R3
and R4 (the 50Ω is to balance the network analyzer’s
source impedance) and sent to the feedback signal. This
essentially breaks the loop and injects the AC signal on
top of the DC output voltage and sends it to the
feedback. By monitoring the feedback “R” and output
“A”, gain and phase are measured. This method has no
minimum frequency. Ensure that the bandwidth of the
op-amp being used is much greater than the expected
bandwidth of the power supply’s control loop. An op-amp
with >100MHz bandwidth is more than sufficient for most
power supplies (which includes both linear and
switching) and are more common and significantly
cheaper than the injection transformers previously
mentioned. The one disadvantage to using the op-amp
injection method, is the supply voltages need to be
below the maximum operating voltage of the op-amp.
Also, the maximum output voltage for driving 50Ω inputs
using the MIC922 is 3V. For measuring higher output
voltages, a 1MΩ input impedance is required for the A
and R channels. Remember to always measure the
Figure 7. Transformer Injection
A 50Ω resistor allows impedance matching from the
network analyzer source. This method allows the DC
loop to maintain regulation and allow the network
analyzer to insert an AC signal on top of the DC voltage.
The network analyzer will then sweep the source while
April 2010
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M9999-041910
Micrel, Inc.
MIC2207
output voltage with an oscilloscope to ensure the
measurement is working properly. You should see a
single sweeping sinusoidal waveform without distortion
on the output. If there is distortion of the sinusoid, reduce
the amplitude of the source signal. You could be
overdriving the feedback causing a large signal
response.
The following Bode analysis show the small signal loop
stability of the MIC2207. The MIC2207 utilizes a type III
compensation. This is a dominant low frequency pole,
followed by 2 zero’s and finally the double pole of the
inductor capacitor filter, creating a final 20dB/decade roll
off. Bode analysis gives us a few important data points;
speed of response (Gain Bandwidth or GBW) and loop
stability. Loop speed or GBW determines the response
time to a load transient. Faster response times yield
smaller voltage deviations to load steps.
Instability in a control loop occurs when there is gain and
positive feedback. Phase margin is the measure of how
stable the given system is. It is measured by determining
how far the phase is from crossing zero when the gain is
equal to 1 (0dB).
OUT
50
60
105
10 L=1µH
0 COUT = 4.7µF GAIN
-10 R1 = 10k
R2 = 12.4k
-20 C = 82pF
FF
-30
100
1k
10k
100k
FREQUENCY (Hz)
35
0
-70
-105
1M
50
GAIN (dB)
40
OUT
PHASE
140
105
GAIN
GAIN (dB)
175
70
35
0
0
-1
-2
-3
-4
-5
-6
L=1µH
COUT = 4.7µF
35
0
-35
-70
-105
1M
25
GAIN
R1 = 10k
R2 = 12.4k
CFF = 82pF
-7
-8
-9
-10
100
210
20
-10 R1 = 10k
R2 = 12.4k
-20 C = 82pF
FF
-30
100
1k
10k
100k
FREQUENCY (Hz)
April 2010
=3A
30
10 L=1µH
0 COUT = 4.7µF
10 L=1µH
0 COUT = 4.7µF
-10 R1 = 10k
GAIN
R2 = 12.4k
-20 C = 82pF
FF
-30
100
1k
10k
100k
FREQUENCY (Hz)
Gain and Phase
vs. Frequency
20
15
PHASE
10
5
1k
10k
100k
FREQUENCY (Hz)
0
1M
The graph above shows the effects on the gain and
phase of the system caused by feedback resistors and a
feedforward capacitor. The maximum amount of phase
boost achievable with a feedforward capacitor is
graphed below.
PHASE (°)
OUT
70
PHASE (°)
GAIN (dB)
-35
• Phase Margin=47 Degrees
• GBW=156KHz
Gain will also increase with input voltage. The following
graph shows the increase in GBW for an increase in
supply voltage.
60 IN
105
20
Feed Forward Capacitor
The feedback resistors are a gain reduction block in the
overall system response of the regulator. By placing a
capacitor from the output to the feedback pin, high
frequency signal can bypass the resistor divider, causing
a gain increase up to unity gain.
Typically for 3.3Vin and 1.8Vout at 3A;
Bode Plot
V =5V, V
=1.8V, I
140
30
• Phase Margin=90.5 Degrees
• GBW= 64.4KHz
140
70
PHASE
3.3Vin, 1.8Vout Iout=50mA;
175
20
175
40
210
30
210
50
=3A
PHASE
40
GAIN (dB)
OUT
Bode Plot
VIN=3.3V,V OUT=1.8V,IOUT=50mA
PHASE BOOST (°)
60 IN
• Phase Margin=43.1 Degrees
• GBW= 218KHz
Being that the MIC2207 is non-synchronous; the
regulator only has the ability to source current. This
means that the regulator has to rely on the load to be
able to sink current. This causes a non-linear response
at light loads. The following plot shows the effects of the
pole created by the nonlinearity of the output drive
during light load (discontinuous) conditions.
PHASE (°)
Bode Plot
V =3.3V, V
=1.8V, I
5Vin, 1.8Vout at 3A load;
-35
-70
-105
1M
13
M9999-041910
Micrel, Inc.
MIC2207
set-up to measure output impedance from 10Hz to 1MHz
using the MIC5190 high speed controller.
By setting up a network analyzer to sweep the feedback
current, while monitoring the output of the voltage
regulator and the voltage across the load resistance,
output impedance is easily obtainable. To keep the
current from being too high, a DC offset needs to be
applied to the network analyzer’s source signal. This can
be done with an external supply and 50Ω resistor. Make
sure that the currents are verified with an oscilloscope
first, to ensure the integrity of the signal measurement. It
is always a good idea to monitor the A and R
measurements with a scope while you are sweeping it.
To convert the network analyzer data from dBm to
something more useful (such as peak to peak voltage
and current in our case);
Max. Amount of Phase Boost
Obtainable using CFF vs. Output
Voltage
50
PAHSE BOOST (°)
45
40
35
30
25
20
15
10
5
0
1
V
REF
= 1V
2
3
4
OUTPUT VOLTAGE (V)
5
By looking at the graph, phase margin can be affected to
a greater degree with higher output voltages.
The next bode plot shows the phase margin of a 1.8V
output at 3A without a feedforward capacitor.
Bode Plot
VIN=3.3V, V OUT=1.8V, IOUT=3A
60
210
50
PHASE
105
20
70
10 L=1µH
0 COUT = 4.7µF
GAIN
-10 R1 = 10k
R2 = 12.4k
-20 C = 0pF
FF
-30
100
1k
10k
100k
FREQUENCY (Hz)
35
0
ΔI =
-35
-70
dBm
10
× 1mW × 50Ω × 2
0.707 × R LOAD
Output Impedance
vs. Frequency
OUTPUT IMPEDANCE (Ohms)
1
Output impedance, simply stated, is the amount of
output voltage deviation vs. the load current deviation.
The lower the output impedance, the better.
VOUT=1.8V
L=1µH
COUT=4.7µF + 0.1µ
0.1
3.3VIN
0.01
0.001
10
ΔVOUT
ΔIOUT
5VIN
100 1k 10k 100k 1M
FREQUENCY (Hz)
From this graph, you can see the effects of bandwidth
and output capacitance. For frequencies <200KHz, the
output impedance is dominated by the gain and
inductance. For frequencies >200KHz, the output
impedance is dominated by the capacitance. A good
approximation for transient response can be calculated
from determining the frequency of the load step in amps
per second;
Output impedance for a buck regulator is the parallel
impedance of the output capacitor and the MOSFET and
inductor divided by the gain;
R DSON + DCR + X L
X COUT
GAIN
To measure output impedance vs. frequency, the load
current must be swept across the frequencies measured,
while the output voltage is monitored. Fig 9 shows a test
April 2010
10
The following graph shows output impedance vs
frequency at 2A load current sweeping the AC current
from 10Hz to 10MHz, at 1A peak to peak amplitude.
-105
1M
Output Impedance and Transient
response
Z TOTAL =
× 1mW × 50Ω × 2
0.707
and peak to peak current;
As you can see the typical phase margin, using the
same resistor values as before without a feedforward
capacitor results in 33.6 degrees of phase margin. Our
prior measurement with a feedforward capacitor yielded
a phase margin of 47 degrees. The feedforward
capacitor has given us a phase boost of 13.4 degrees
(47 degrees – 33.6 Degrees = 13.4 Degrees).
Z OUT =
dBm
10
140
30
PHASE (°)
GAIN (dB)
40
ΔV =
175
10
f =
14
A/sec
2π
M9999-041910
Micrel, Inc.
MIC2207
Ripple measurements
To properly measure ripple on either input or output of a
switching regulator, a proper ring in tip measurement is
required. Standard oscilloscope probes
come with a grounding clip, or a long wire
with an alligator clip. Unfortunately, for
high frequency measurements, this
ground clip can pick-up high frequency
noise and erroneously inject it into the
measured output ripple.
The
standard
evaluation
board
accommodates a home made version by
providing probe points for both the input
and output supplies and their respective
grounds. This requires the removing of
the oscilloscope probe sheath and ground
clip from a standard oscilloscope probe
and wrapping a non-shielded bus wire
around the oscilloscope probe. If there
does not happen to be any non shielded
bus wire immediately available, the leads
from axial resistors will work. By maintaining the
shortest possible ground lengths on the oscilloscope
probe, true ripple measurements can be obtained.
Figure 9. Output Impedance Measurement
Then, determine the output impedance by looking at the
output impedance vs frequency graph. Next, calculate
the voltage deviation times the load step;
ΔVOUT = ΔIOUT × Z OUT
The output impedance graph shows the relationship
between supply voltage and output impedance. This is
caused by the lower Rdson of the high side MOSFET
and the increase in gain with increased supply voltages.
This explains why higher supply voltages have better
transient response.
↓Z TOTAL =
April 2010
↓ R DSON + DCR + X L
X COUT
↑ GAIN
15
M9999-041910
Micrel, Inc.
MIC2207
Recommended Layout / 3A Evaluation Board
Recommended Top Layout
Recommended Bottom Layout
April 2010
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M9999-041910
Micrel, Inc.
MIC2207
MIC2207 Scheme and B.O.M for 3A Output
MIC2207 Schematic
Item
Part Number
Description
C1a,C1b
C2012JB0J106K
10µF Ceramic Capacitor X5R 0805 6.3V
TDK
GRM219R60J106KE19
10µF Ceramic Capacitor X5R 0805 6.3V
Murata
08056D106MAT
10µF Ceramic Capacitor X5R 0805 6.3V
AVX
0402ZD104MAT
0.1µF Ceramic Capacitor X5R 0402 10V
AVX
C2
Manufacturer
Qty
2
1
C2012JB0J475K
4.7µF Ceramic Capacitor X5R 0603 6.3V
TDK
GRM188R60J475KE19
4.7µF Ceramic Capacitor X5R 0603 6.3V
Murata
06036D475MAT
4.7µF Ceramic Capacitor X5R 0603 6.3V
AVX
1
C4
VJ0402A820KXAA
82pF Ceramic Capacitor 0402
Vishay VT
1
D1
SSA33L
3A Schottky 30V SMA
Vishay Semi
1
L1
RLF7030-1R0N6R4
1µH Inductor 8.8mΩ 7.1mm(L) x 6.8mm (W)x 3.2mm(H)
TDK
1
744 778 9001
1µH Inductor 12mΩ 7.3mm(L)x7.3mm(W)x3.2mm(H)
Wurth Electronik
1
C3
IHLP2525AH-01 1
1µH Inductor 17.5mΩ(L)6.47mmx(W)6.86mmx(H) 1.8mm
Vishay Dale
1
R1,R4
CRCW04021002F
10KΩ1% 0402 resistor
Vishay Dale
1
R2
CRCW04026651F
CRCW04021242F
CRCW04022002F
CRCW04024022F
6.65kΩ 1% 0402 For 2.5VOUT
12.4kΩ 1% 0402 For 1.8 VOUT
20kΩ 1% 0402 For 1.5 VOUT
40.2kΩ 1% 0402 For 1.2 VOUT
Open
For 1.0 VOUT
Vishay Dale
Vishay Dale
Vishay Dale
Vishay Dale
Vishay Dale
1
Vishay Dale
1
Micrel
1
R3
CRCW040210R0F
10Ω1% 0402 resistor
U1
MIC2207YML
2MHz 3A Buck Regulator
Notes:
1. Sumida: www.sumida.com.
2. Murata: www.murata.com.
3. Vishay: www.vishay.com.
4. Micrel, Inc.: www.micrel.com.
April 2010
17
M9999-041910
Micrel, Inc.
MIC2207
Package Information
12-Pin MLF® (ML)
MICREL, INC. 2180 FORTUNE DRIVE SAN JOSE, CA 95131 USA
TEL +1 (408) 944-0800 FAX +1 (408) 474-1000 WEB http://www.micrel.com
The information furnished by Micrel in this data sheet is believed to be accurate and reliable. However, no responsibility is assumed by Micrel for its
use. Micrel reserves the right to change circuitry and specifications at any time without notification to the customer.
Micrel Products are not designed or authorized for use as components in life support appliances, devices or systems where malfunction of a product
can reasonably be expected to result in personal injury. Life support devices or systems are devices or systems that (a) are intended for surgical implant
into the body or (b) support or sustain life, and whose failure to perform can be reasonably expected to result in a significant injury to the user. A
Purchaser’s use or sale of Micrel Products for use in life support appliances, devices or systems is a Purchaser’s own risk and Purchaser agrees to fully
indemnify Micrel for any damages resulting from such use or sale.
© 2005 Micrel, Incorporated.
April 2010
18
M9999-041910