10A LDO 5-Pin Adjustable Linear Regulator

CS52510−1
10 A LDO 5−Pin Adjustable
Linear Regulator
This new very low dropout regulator is designed to power the next
generation of advanced microprocessor. To achieve very low dropout,
the internal pass transistor is powered separately from the control
circuitry. Furthermore, with the control and power inputs tied together,
this device can be used in single supply configuration and still offer a
better dropout voltage than conventional PNP−NPN based LDO
regulators. In this mode the dropout is determined by the minimum
control voltage.
It is supplied in a five−terminal TO−220 package, which allows for
the implementation of a remote−sense pin permitting very accurate
regulation of output voltage directly at the load, where it counts, rather
than at the regulator. This remote sensing feature virtually eliminates
output voltage variations due to load changes and resistive voltage
drops. Typical load regulation measured at the sense pin is 1.0 mV for
an output voltage of 2.5 V with a load step of 10 mA to 10 A.
The very fast transient loop response easily meets the needs of the
latest microprocessors. In addition, a small capacitor on the Adjust pin
will further improve the transient capabilities.
Internal protection circuitry provides for “bust−proof” operation,
similar to three−terminal regulators. This circuitry, which includes
overcurrent, short circuit, supply sequencing and overtemperature
protection, will self protect the regulator under all fault conditions.
The CS52510−1 is ideal for generating a secondary 2.0−2.5 V low
voltage supply on a motherboard where both 5.0 V and 3.3 V are
already available.
Features
1.25 V to 5.0 V VOUT at 10 A
VPOWER Dropout < 0.65 V @ 10 A
VCONTROL Dropout < 1.25 V @ 10 A
1.5% Trimmed Reference
Fast Transient Response
Remote Voltage Sensing
Thermal Shutdown
Current Limit
Short Circuit Protection
Backwards Compatible with 3−Pin Regulators
•
•
•
•
•
•
•
•
•
•
© Semiconductor Components Industries, LLC, 2006
September, 2006 − Rev. 6
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Tab = VOUT
Pin 1. VSENSE
2. Adjust
3. VOUT
4. VCONTROL
5. VPOWER
1
5
TO−220
FIVE LEAD
T SUFFIX
CASE 314D
MARKING DIAGRAM
CS52510−1
AWLYWW
1
A
WL, L
YY, Y
WW, W
= Assembly Location
= Wafer Lot
= Year
= Work Week
ORDERING INFORMATION
Device
CS52510−1GT5
1
Package
Shipping
TO−220
FIVE LEAD
50 Units/Rail
Publication Order Number:
CS52510−1/D
CS52510−1
5.0 V
VCONTROL
VOUT
CS52510−1
2.5 V @ 10 A
3.3 V
VPOWER
VSENSE
124
1.0%
Adjust
10 μF
10 V
100 μF
5.0 V
0.1 μF
5.0 V
124
1.0%
300 μF
5.0 V
Load
Figure 1. Application Diagram
MAXIMUM RATINGS*
Rating
Value
Unit
VPOWER Input Voltage
6.0
V
VCONTROL Input Voltage
13
V
0 to 150
°C
−65 to +150
°C
2.0
kV
260 peak
°C
Operating Junction Temperature Range, TJ
Storage Temperature Range
ESD Damage Threshold
Lead Temperature Soldering:
Wave Solder: (through hole styles only) (Note 1)
1. 10 second maximum.
*The maximum package power dissipation must be observed.
ELECTRICAL CHARACTERISTICS (0°C ≤ TA ≤ 70°C; 0°C ≤ TJ ≤ 150°C; VSENSE = VOUT and VADJ = 0 V; unless
otherwise specified.)
Characteristic
Test Conditions
Min
Typ
Max
Unit
Reference Voltage
VCONTROL = 2.75 V to 12 V, VPOWER = 2.5 V to 5.5 V,
10 mA ≤ IOUT ≤ 10 A
1.234
(−1.5%)
1.253
1.272
(+1.5%)
V
Line Regulation
VCONTROL = 2.5 V to 12 V, VPOWER = 1.75 V to 5.5 V,
IOUT = 10 mA
−
0.02
0.2
%
Load Regulation (Note 2)
VCONTROL = 2.75 V, VPOWER = 2.5 V,
IOUT = 10 mA to 10 A, with Remote Sense
−
0.04
0.2
%
Minimum Load Current (Note 3)
VCONTROL = 5.0 V, VPOWER = 3.3 V, ΔVOUT = +1.0%
−
5.0
10
mA
Control Pin Current (Note 4)
VCONTROL = 2.75 V, VPOWER = 2.5 V, IOUT = 100 mA
VCONTROL = 2.75 V, VPOWER = 2.5 V, IOUT = 4.0 A
VCONTROL = 2.75 V, VPOWER = 1.75 V, IOUT = 4.0 A
VCONTROL = 2.75 V, VPOWER = 2.5 V, IOUT = 10 A
−
−
−
−
6.0
30
33
80
10
60
70
180
mA
mA
mA
mA
Adjust Pin Current
VCONTROL = 2.75 V, VPOWER = 2.5 V, IOUT = 10 mA
−
60
120
μA
Current Limit
VCONTROL = 2.75 V, VPOWER = 2.5 V, ΔVOUT = −1.5%
10.1
11
−
A
Short Circuit Current
VCONTROL = 2.75 V, VPOWER = 2.5 V, VOUT = 0 V
8.0
9.5
−
A
CS52510−1
2. This parameter is guaranteed by design and is not 100% production tested.
3. The minimum load current is the minimum current required to maintain regulation. Normally the current in the resistor divider used to set
the output voltage is selected to meet the minimum load current requirement.
4. The control pin current is the drive current required for the output transistor. This current will track output current with roughly a 1:100 ratio.
The minimum value is equal to the quiescent current of the device.
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2
CS52510−1
ELECTRICAL CHARACTERISTICS (continued) (0°C ≤ TA ≤ 70°C; 0°C ≤ TJ ≤ 150°C; VSENSE = VOUT and VADJ = 0 V; unless
otherwise specified.)
Characteristic
Test Conditions
Min
Typ
Max
Unit
CS52510−1
Ripple Rejection (Note 5)
VCONTROL = VPOWER = 3.25 V Avg,
VRIPPLE = 1.0 VP−P @ 120 Hz, IOUT = 4.0 A,
CADJ = 0.1 μF
60
80
−
dB
Thermal Regulation
30 ms Pulse, TA = 25°C
−
0.002
−
%/W
VCONTROL Dropout Voltage
(Minimum VCONTROL − VOUT)
(Note 6)
VPOWER = 2.5 V, IOUT = 100 mA
VPOWER = 2.5 V, IOUT = 1.0 A
VPOWER = 2.5 V, IOUT = 2.75 A
VPOWER = 2.5 V, IOUT = 4.0 mA
VPOWER = 2.5 V, IOUT = 10 A
−
−
−
−
−
1.00
1.00
1.00
1.00
1.25
1.15
1.15
1.15
1.15
1.40
V
V
V
V
V
VPOWER Dropout Voltage
(Minimum VPOWER − VOUT)
(Note 6)
VCONTROL = 2.75 V, IOUT = 100 mA
VCONTROL = 2.75 V, IOUT = 1.0 A
VCONTROL = 2.75 V, IOUT = 2.75 A
VCONTROL = 2.75 V, IOUT = 4.0 mA
VCONTROL = 2.75 V, IOUT = 10 A
−
−
−
−
−
0.10
0.15
0.20
0.26
0.65
0.15
0.20
0.30
0.40
0.80
V
V
V
V
V
RMS Output Noise
Freq = 10 Hz to 10 kHz, TA = 25°C
−
0.003
−
%VOUT
Temperature Stability
−
−
0.5
−
%
Thermal Shutdown (Note 7)
−
150
180
210
°C
Thermal Shutdown Hysteresis
−
−
25
−
°C
VCONTROL Supply Only Output
Current
VCONTROL = 13 V, VPOWER Not Connected,
VADJ = VOUT = VSENSE = 0 V
−
−
50
mA
VPOWER Supply Only Output
Current
VPOWER = 6.0 V, VCONTROL Not Connected,
VADJ = VOUT = VSENSE = 0 V
−
0.1
1.0
mA
5. This parameter is guaranteed by design and is not 100% production tested.
6. Dropout is defined as either minimum control voltage (VCONTROL) or minimum power voltage (VPOWER) to output voltage differential required to maintain 1.5% regulation at a particular load.
7. This parameter is guaranteed by design, but not parametrically tested in production. However, a 100% thermal shutdown functional test
is performed on each part.
PACKAGE PIN DESCRIPTION
PACKAGE PIN #
TO−220
PIN SYMBOL
1
VSENSE
This Kelvin sense pin allows for remote sensing of the output voltage at the
load for improved regulation. It is internally connected to the positive input of
the voltage sensing error amplifier.
2
Adjust
This pin is connected to the low side of the internally trimmed 1.5% bandgap
reference voltage and carries a bias current of about 50 μA. A resistor divider
from Adjust to VOUT and from Adjust to ground sets the output voltage. Also,
transient response can be improved by adding a small bypass capacitor from
this pin to ground.
3
VOUT
This pin is connected to the emitter of the power pass transistor and provides a
regulated voltage capable of sourcing 10 A of current.
4
VCONTROL
5
VPOWER
FUNCTION
This is the supply voltage for the regulator control circuitry. For the device to
regulate, this voltage should be between 1.0 V and 1.4 V (depending on the
output current) greater than the output voltage. The control pin current will be
about 1.0% of the power pin output current.
This is the power input voltage. This pin is physically connected to the collector
of the power pass transistor. For the device to regulate, this voltage should be
between 1.0 V and 0.8 V greater than the output voltage depending on the output current. The output load current of 10 A is supplied through this pin.
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3
CS52510−1
VPOWER
VCONTROL
BIAS
and
TSD
EA
−
+
VREF
IA
+
−
VOUT
VSENSE
Adjust
Figure 2. Block Diagram
TYPICAL PERFORMANCE CHARACTERISTICS
90
75
VPOWER = 2.5 V
IL = 10 mA
Adjust Pin Current (μA)
Ripple Rejection (dB)
80
70
60
50
VIN − VOUT = 2.0 V
IOUT = 4.0 A
VRIPPLE = 1.0 VP−P
COUT = 22 μF
CADJ = 0.1 μF
40
30
20
10 1
10
102
103
104
105
74
73
72
71
70
1.0
106
2.0
3.0
4.0
Frequency (Hz)
8.0
9.0
10
11
75
VCONTROL = 5.0 V
ΔVOUT = +1.0%
Adjust Pin Current (μA)
Minimum Load Current (μA)
7.0
Figure 4. Adjust Pin Current vs VCONTROL − VOUT
916.4
916.2
6.0
VCONTROL − VOUT (V)
Figure 3. Ripple Rejection vs Frequency
916.3
5.0
916.1
916.0
915.9
915.8
915.7
915.6
74
VCONTROL = 2.75 V
IL = 10 mA
73
72
71
915.5
915.4
0.5
1.5
2.5
3.5
4.5
70
0.5
VPOWER − VOUT (V)
1.5
2.5
3.5
VPOWER − VOUT (V)
Figure 5. Minimum Load Current vs VPOWER − VOUT
Figure 6. Adjust Pin Current vs VPOWER − VOUT
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4
4.5
CS52510−1
1200
14.0
Minimum Load Current (μA)
VCONTROL = 2.75 V
Output Current (A)
12.0
10.0
8.0
6.0
4.0
2.0
0
VPOWER = 3.3 V
ΔVOUT = +1.0%
1150
1100
1050
1000
950
900
850
0.5 1.0 1.5 2.0 2.5 3.0 3.5
0
4.0 4.5
800
1.0
5.0 5.5
2.0
3.0
VPOWER − VOUT (V)
5.0
6.0
7.0
8.0
9.0
10
11
VCONTROL − VOUT (V)
Figure 7. Short Circuit Current vs VPOWER − VOUT
Figure 8. Minimum Load Current vs VCONTROL − VOUT
77
0.10
VPOWER = 2.5 V
VCONTROL = 2.75 V
76
VPOWER = 2.5 V
VCONTROL = 2.75 V
0.09
Output Voltage Deviation (%)
Adjust Pin Current (μA)
4.0
75
74
73
0.08
0.07
0.06
0.05
0.04
0.03
0.02
0.01
72
1.0
0
2.0
3.0
4.0
5.0
6.0
7.0
8.0
9.0
0
10
0
1.0
2.0
3.0
Output Current (A)
6.0
7.0
8.0
9.0
10
Figure 10. Load Regulation vs Output Current
1.0
1.25
0.8
VCONTROL Dropout Voltage (V)
VPOWER = 2.5 V
VCONTROL = 2.75 V
0.9
VPOWER Dropout Voltage (V)
5.0
Output Current (A)
Figure 9. Adjust Pin Current vs Output Current
0.7
0.6
0.5
0.4
0.3
0.2
0.1
0
4.0
0
1.0
2.0
3.0
4.0
5.0
6.0
7.0
8.0
9.0
VPOWER = 2.5 V
1.00
0.75
0.50
0.25
0
10
0
Output Current (A)
1.0
2.0
3.0
4.0
5.0
6.0
7.0
8.0
9.0
Output Current (A)
Figure 11. VPOWER Dropout Voltage vs IOUT
Figure 12. VCONTROL Dropout Voltage vs IOUT
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5
10
CS52510−1
0.100
0.35
Output Voltage Deviation (%)
Output Voltage Deviation (%)
0.075
0.050
0.025
0
−0.025
−0.050
−0.075
IO = 10 mA
VCONTROL = 2.75 V
VPOWER = 2.5 V
−0.100
−0.125
−0.150
0
0.30
0.25
TCase = 25°C
0.20
0.15
TCase = 125°C
0.10
TCase = 0°C
0.05
0
10 20 30 40 50 60 70 80 90 100 110 120 130
0
2.0
TJ (°C)
Figure 13. Reference Voltage vs Temperature
6.0
10
Output Voltage
Deviation (mV)
100
81
79
77
75
50
0
COUT = 330 μF
CPOWER = 110 μF
CCONTROL = 10 μF
CADJ = 25 μF
VCONTROL = 5.0 V
VPOWER = 3.3 V
VOUT = 2.5 V
−50
−100
73
Current (A)
71
69
67
65
8.0
Figure 14. Load Regulation vs Output Current
83
Adjust Pin Current (μA)
4.0
Output Current (A)
0
20
40
60
80
100
120
140
160
7.0
0
0
0
1
Temperature (°C)
2
3
4
5
Time (μs)
Figure 15. Adjust Pin Current vs Temperature
Figure 16. Current Step Transient Response
APPLICATIONS NOTES
THEORY OF OPERATION
The CS52510−1 linear regulator provides adjustable
voltages from 1.25 V to 5.0 V at currents up to 10 A. The
regulator is protected against short circuits, and includes a
thermal shutdown circuit with hysteresis. The output, which
is current limited, consists of a PNP−NPN transistor pair and
requires an output capacitor for stability. A detailed
procedure for selecting this capacitor is included in the
Stability Considerations section.
output voltage will not turn on until both supplies are
operating. If the control voltage comes up first, the output
current will be typically limited to about 3.0 mA until the
power input voltage comes up. If the power input voltage
comes up first the output will not turn on at all until the
control voltage comes up. The output can never come up
unregulated.
The CS52510−1 can also be used as a single supply device
with the control and power inputs tied together. In this mode,
the dropout will be determined by the minimum control
voltage.
VPOWER Function
The CS52510−1 utilizes a two supply approach to
maximize efficiency. The collector of the power device is
brought out to the VPOWER pin to minimize internal power
dissipation under high current loads.VCONTROL provides
power for the control circuitry and the drive for the output
NPN transistor. VCONTROL should be at least 1.0 V greater
than the output voltage. Special care has been taken to
ensure that there are no supply sequencing problems. The
Output Voltage Sensing
The CS52510−1 five terminal linear regulator includes a
dedicated VSENSE function. This allows for true Kelvin
sensing of the output voltage. This feature can virtually
eliminate errors in the output voltage due to load regulation.
Regulation will be optimized at the point where the sense pin
is tied to the output.
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6
CS52510−1
DESIGN GUIDELINES
before the VPOWER supply. This allows the IC to begin
charging output capacitor as soon as the VPOWER to VOUT
differential is large enough that the pass transistor conducts.
As VPOWER increases, the pass transistor will remain in
dropout, and current is passed to the load until VOUT is in
regulation. Further increase in the supply voltage brings the
pass transistor out of dropout. In this manner, any output
voltage less than 13 V may be regulated, provided the
VPOWER to VOUT differential is less than 6.0 V. In the case
where VCONTROL and VPOWER are shorted, there is no
theoretical limit to the regulated voltage as long as the
VPOWER to VOUT differential of 6.0 V is not exceeded.
There is a possibility of damaging the IC when VPOWER
− VIN is greater than 6.0 V if a short circuit occurs. Short
circuit conditions will result in the immediate operation of
the pass transistor outside of its safe operating area.
Overvoltage stresses will then cause destruction of the pass
transistor before overcurrent or thermal shutdown circuitry
can become active. Additional circuitry may be required to
clamp the VPOWER to VOUT differential to less than 6.0 V
if fail safe operation is required. One possible clamp circuit
is illustrated in Figure 18; however, the design of clamp
circuitry must be done on an application by application
basis. Care must be taken to ensure the clamp actually
protects the design. Components used in the clamp design
must be able to withstand the short circuit condition
indefinitely while protecting the IC.
Adjustable Operation
This LDO adjustable regulator has an output voltage
range of 1.25 V to 5.0 V. An external resistor divider sets the
output voltage as shown in Figure 17. The regulator’s
voltage sensing error amplifier maintains a fixed 1.253 V
reference between the output pin and the adjust pin.
VCONTROL
VOUT
CS52510−1
VPOWER
VSENSE
Adjust
R1
R2
Figure 17. An External Resistor Divider Sets the
Value of VOUT. The 1.253 V Reference Voltage
Drops Across R1.
A resistor divider network R1 and R2 causes a fixed
current to flow to ground. This current creates a voltage
across R2 that adds to the 1.253 V across R1 and sets the
overall output voltage. The adjust pin current (typically
50 μA) also flows through R2 and adds a small error that
should be taken into account if precise adjustment of VOUT
is necessary. The output voltage is set according to the
formula:
VOUT + 1.253 V
R1 ) R2 ) R2
R1
External Supply
IADJ
VCONTROL
The term IADJ × R2 represents the error added by the
adjust pin current.
R1 is chosen so that the minimum load current is a least
10 mA. R1 and R2 should be of the same composition for
best tracking over temperature. The divider resistors should
be placed as close to the load as possible.
While not required, a bypass capacitor connected between
the adjust pin and ground will improve transient response
and ripple rejection. A 0.1 μF tantalum capacitor is
recommended for “first cut” design. Value and type may be
varied to optimize performance vs. price.
VSENSE
VPOWER
VOUT
VADJ
Figure 18. Example Clamp Circuitry for
VPOWER − VOUT > 6.0 V
Stability Considerations
Other Adjustable Operation Considerations
The output compensation capacitor helps determine three
main characteristics of a linear regulator: start−up delay,
load transient response, and loop stability.
The capacitor value and type is based on cost, availability,
size and temperature constraints. A tantalum or aluminum
electrolytic capacitor is best, since a film or ceramic
capacitor with almost zero ESR can cause instability. The
aluminum electrolytic capacitor is the least expensive
The CS52510−1 linear regulator has an absolute
maximum specification of 6.0 V for the voltage difference
between VIN and VOUT. However, the IC may be used to
regulate voltages in excess of 6.0 V. The two main
considerations in such a design are the sequencing of power
supplies and short circuit capability.
Power supply sequencing should be such that the
VCONTROL supply is brought up coincidentally with or
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7
CS52510−1
solution. However, when the circuit operates at low
temperatures, both the value and ESR of the capacitor will
vary considerably. The capacitor manufacturers data sheet
provides this information.
A 300 μF tantalum capacitor will work for most
applications, but with high current regulators such as the
CS52510−1 the transient response and stability improve
with higher values of capacitor. The majority of applications
for this regulator involve large changes in load current so the
output capacitor must supply the instantaneous load current.
The ESR of the output capacitor causes an immediate drop
in output voltage given by:
DV + DI
I+C
ESR
Current Limit
The internal current limit circuit limits the output current
under excessive load conditions.
Short Circuit Protection
The device includes short circuit protection circuitry that
clamps the output current at approximately two amperes less
than its current limit value. This provides for a current
foldback function, which reduces power dissipation under a
direct shorted load.
Protection Diodes
When large external capacitors are used with a linear
regulator it is sometimes necessary to add protection diodes.
If the input voltage of the regulator gets shorted, the output
capacitor will discharge into the output of the regulator. The
discharge current depends on the value of the capacitor, the
output voltage, and the rate at which VCONTROL drops. In
the CS52510−1 regulator, the discharge path is through a
large junction and protection diodes are not usually needed.
If the regulator is used with large values of output
capacitance and the input voltage is instantaneously shorted
to ground, damage can occur. In this case, a diode connected
as shown in Figure 19 is recommended. Use of this diode has
the added benefit of bleeding VOUT to ground if VCONTROL
is shorted. This prevents an unregulated output from causing
system damage.
Thermal Shutdown
The thermal shutdown circuitry is guaranteed by design to
become activate above a die junction temperature of
approximately 150°C and to shut down the regulator output.
This circuitry has 25°C of typical hysteresis, thereby
allowing the regulator to recover from a thermal fault
automatically.
Calculating Power Dissipation and
Heat Sink Requirements
High power regulators such as the CS52510−1 family
usually operate at high junction temperatures. Therefore, it
is important to calculate the power dissipation and junction
temperatures accurately to ensure that an adequate heat sink
is used. Since the package tab is connected to VOUT on the
CS52510−1, electrical isolation may be required for some
applications. Also, as with all high power packages, thermal
compound is necessary to ensure proper heat flow. For
added safety, this high current LDO includes an internal
thermal shutdown circuit.
The thermal characteristics of an IC depend on the
following four factors: junction temperature, ambient
temperature, die power dissipation, and the thermal
resistance from the die junction to ambient air. The
maximum junction temperature can be determined by:
VOUT
CS52510−1
VPOWER
V
where:
I is the current flow out of the load capacitance when
VCONTROL is shorted,
C is the value of load capacitance
V is the output voltage, and
T is the time duration required for VCONTROL to transition
from high to being shorted.
If the calculated current is greater than or equal to the
typical short circuit current value provided in the
specifications, serious thought should be given to the use of
a protection diode.
For microprocessor applications it is customary to use an
output capacitor network consisting of several tantalum and
ceramic capacitors in parallel. This reduces the overall ESR
and reduces the instantaneous output voltage drop under
transient load conditions. The output capacitor network
should be as close to the load as possible for the best results.
VCONTROL
T
VSENSE
Adjust
TJ(max) + TA(max) ) PD(max)
RQJA
The maximum ambient temperature and the power
dissipation are determined by the design while the
maximum junction temperature and the thermal resistance
depend on the manufacturer and the package type. The
maximum power dissipation for a regulator is:
Figure 19. Diode Protection Against VCONTROL
Short Circuit Conditions
A rule of thumb useful in determining if a protection diode
is required is to solve for current
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8
CS52510−1
PD(max) + (VIN(max) * VOUT(min))IOUT(max)
) VIN(max) IIN(max)
RQJA + RQJC ) RQCS ) RQSA
The value for RΘJC is 1.4°C/watt for the CS52510−1 in a
TO−220 package. For a high current regulator such as the
CS52510−1 the majority of heat is generated in the power
transistor section. The value for RΘSA depends on the heat
sink type, while the RΘCS depends on factors such as
package type, heat sink interface (is an insulator and thermal
grease used?), and the contact area between the heat sink and
the package. Once these calculations are complete, the
maximum permissible value of RΘJA can be calculated and
the proper heat sink selected. For further discussion on heat
sink selection, see our application note “Thermal
Management,” document number AND8036/D, available
through the Literature Distribution Center or via our website
at http://www.onsemi.com.
A heat sink effectively increases the surface area of the
package to improve the flow of heat away from the IC and
into the surrounding air. Each material in the heat flow path
between the IC and the outside environment has a thermal
resistance which is measured in degrees per watt. Like series
electrical resistances, these thermal resistances are summed
to determine the total thermal resistance between the die
junction and the surrounding air, RΘJA. This total thermal
resistance is comprised of three components. These resistive
terms are measured from junction to case (RΘJC), case to
heat sink RΘCS), and heat sink to ambient air (RΘSA). The
equation is:
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CS52510−1
PACKAGE DIMENSIONS
TO−220
FIVE LEAD
T SUFFIX
CASE 314D−04
ISSUE E
−T−
−Q−
B
E
A
U
NOTES:
1. DIMENSIONING AND TOLERANCING PER ANSI
Y14.5M, 1982.
2. CONTROLLING DIMENSION: INCH.
3. DIMENSION D DOES NOT INCLUDE
INTERCONNECT BAR (DAMBAR) PROTRUSION.
DIMENSION D INCLUDING PROTRUSION SHALL
NOT EXCEED 10.92 (0.043) MAXIMUM.
C
L
DIM
A
B
C
D
E
G
H
J
K
L
Q
U
1234 5
K
D
SEATING
PLANE
J
H
G
5 PL
0.356 (0.014)
M
T Q
M
INCHES
MIN
MAX
0.572
0.613
0.390
0.415
0.170
0.180
0.025
0.038
0.048
0.055
0.067 BSC
0.087
0.112
0.015
0.025
0.990
1.045
0.320
0.365
0.140
0.153
0.105
0.117
MILLIMETERS
MIN
MAX
14.529 15.570
9.906 10.541
4.318
4.572
0.635
0.965
1.219
1.397
1.702 BSC
2.210
2.845
0.381
0.635
25.146 26.543
8.128
9.271
3.556
3.886
2.667
2.972
PACKAGE THERMAL DATA
Parameter
TO−220 Five Lead
Unit
RΘJC
Typical
1.4
°C/W
RΘJA
Typical
50
°C/W
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CS52510−1/D
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