Power Supply Battery Charger Regulation Control Circuit

MC33341
Power Supply Battery
Charger Regulation
Control Circuit
The MC33341 is a monolithic regulation control circuit that is
specifically designed to close the voltage and current feedback loops in
power supply and battery charger applications. This device features the
unique ability to perform source high−side, load high−side, source
low−side and load low−side current sensing, each with either an
internally fixed or externally adjustable threshold. The various current
sensing modes are accomplished by a means of selectively using the
internal differential amplifier, inverting amplifier, or a direct input path.
Positive voltage sensing is performed by an internal voltage amplifier.
The voltage amplifier threshold is internally fixed and can be externally
adjusted in all low−side current sensing applications. An active high
drive output is provided to directly interface with economical
optoisolators for isolated output power systems. This device is available
in 8−lead dual−in−line and surface mount packages.
http://onsemi.com
MARKING
DIAGRAMS
8
SOIC−8
D SUFFIX
CASE 751
1
1
8
PDIP−8
P SUFFIX
CASE 626
Features
•
•
•
•
•
•
•
•
•
•
Differential Amplifier for High−Side Source and Load Current Sensing
Inverting Amplifier for Source Return Low−Side Current Sensing
Non−Inverting Input Path for Load Low−Side Current Sensing
Fixed or Adjustable Current Threshold in All Current Sensing Modes
Positive Voltage Sensing in All Current Sensing Modes
Fixed Voltage Threshold in All Current Sensing Modes
Adjustable Voltage Threshold in All Low−Side Current Sensing Modes
Output Driver Directly Interfaces with Economical Optoisolators
Operating Voltage Range of 2.3 V to 16 V
Pb−Free Packages are Available
Drive Output
VCC
8
7
Current Sense Input B/ Voltage Sense
Input
Voltage Threshold Adjust
5
6
1
Voltage and Current
Transconductance
Amp/Driver
A
= Assembly Location
L, WL = Wafer Lot
Y, YY
= Year
W, WW = Work Week
G or G = Pb−Free Package
(Note: Microdot may be in either location)
PIN CONNECTIONS
Current Sense
Input A 1
8 Drive Output
7 VCC
Current Sense Input B/
Compensation 3
6 Voltage Threshold Adjust
GND 4
V
MC33341P
AWL
YYWWG
1
Current Threshold
Adjust 2
Differential
Amp
1.0
33341
ALYW
G
5 Voltage Sense Input
1.2 V
(Top View)
#1.0
0.2 V
I
Inverting/
Noninverting Amp
Reference
ORDERING INFORMATION
See detailed ordering and shipping information in the package
dimensions section on page 17 of this data sheet.
1
Current Sense Input A
4
GND
2
3
Current
Compensation
Threshold Adjust
This device contains 114 active transistors.
Figure 1. Representative Block Diagram
© Semiconductor Components Industries, LLC, 2006
August, 2006 − Rev. 4
1
Publication Order Number:
MC33341/D
MC33341
MAXIMUM RATINGS
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ÁÁÁÁÁ
ÁÁÁÁÁÁÁÁ
ÁÁÁ
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Symbol
Value
Unit
Power Supply Voltage (Pin 7)
Rating
VCC
16
V
Voltage Range
Current Sense Input A (Pin 1)
Current Threshold Adjust (Pin 2)
Compensation (Pin 3)
Voltage Sense Input (Pin 5)
Current Sense Input B / Voltage Threshold Adjust (Pin 6)
Drive Output (Pin 8)
VIR
−1.0 to VCC
V
ISource
50
mA
Drive Output Source Current (Pin 8)
Thermal Resistance, Junction−to−Air
P Suffix, DIP Plastic Package, Case 626
D Suffix, SO−8 Plastic Package, Case 751
°C/W
RqJA
100
178
Operating Junction Temperature (Note 1)
TJ
−25 to +150
°C
Storage Temperature
Tstg
−55 to +150
°C
NOTE: ESD data available upon request.
Stresses exceeding Maximum Ratings may damage the device. Maximum Ratings are stress ratings only. Functional operation above the
Recommended Operating Conditions is not implied. Extended exposure to stresses above the Recommended Operating Conditions may affect
device reliability.
1. Tested ambient temperature range for the MC33341: Tlow = −25°C, Thigh = +85°C.
ELECTRICAL CHARACTERISTICS (VCC = 6.0 V, TA = 25°C, for min/max values TA is the operating junction temperature range that
applies (Note 1), unless otherwise noted.)
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
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ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Characteristic
Symbol
Min
Typ
Max
Unit
CURRENT SENSING (Pins 1, 2, 6)
High−Side Source and Load Sensing Pin 1 to Pin 6 (Pin 1 >1.6 V)
Internally Fixed Threshold Voltage (Pin 2 = VCC)
TA = 25°C
TA = Tlow to Thigh
Externally Adjusted Threshold Voltage (Pin 2 = 0 V)
Externally Adjusted Threshold Voltage (Pin 2 = 200 mV)
Vth(I HS)
Low−Side Load Sensing Pin 1 to Pin 4 (Pin 1 = 0 V to 0.8 V)
Internally Fixed Threshold Voltage (Pin 2 = VCC)
TA = 25°C
TA = Tlow to Thigh
Externally Adjusted Threshold Voltage (Pin 2 = 0 V)
Externally Adjusted Threshold Voltage (Pin 2 = 200 mV)
Vth(I LS+)
Low−Side Source Return Sensing Pin 1 to 4 (Pin 1 = 0 V to −0.2 V)
Internally Fixed Threshold Voltage (Pin 2 = VCC)
TA = 25°C
TA = Tlow to Thigh
Externally Adjusted Threshold Voltage (Pin 2 = 0 V)
Externally Adjusted Threshold Voltage (Pin 2 = 200 mV)
Vth(I LS−)
mV
187
183
−
−
197
−
10
180
207
211
−
−
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mV
194
192
−
−
200
−
10
180
206
208
−
−
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ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
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mV
−195
−193
−
−
−201
−
−10
−180
−207
−209
−
−
IIB(A HS)
−
40
−
mA
IIB(A LS+)
−
10
−
nA
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Current Sense Input A (Pin 1)
Input Bias Current, High−Side Source and Load Sensing
(Pin 2 = 0 V to VPin 6 V)
Input Bias Current, Low−Side Load Sensing
(Pin 2 = 0 V to 0.8 V)
Input Resistance, Low−Side Source Return Sensing
(Pin 2 = −0.6 V to 0 V)
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Rin(A LS−)
−
10
−
kW
−
−
20
100
−
−
mA
nA
Current Sense Input B/Voltage Threshold Adjust (Pin 6)
Input Bias Current
High−Side Source and Load Current Sensing (Pin 6 > 2.0 V)
Voltage Threshold Adjust (Pin 6 < 1.2 V)
IIB(B)
Current Sense Threshold Adjust (Pin 2)
Input Bias Current
IIB(I th)
−
10
−
nA
gm(I)
−
6.0
−
mhos
Transconductance, Current Sensing Inputs to Drive Output
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2
MC33341
ELECTRICAL CHARACTERISTICS (VCC = 6.0 V, TA = 25°C, for min/max values TA is the operating junction temperature range that
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applies (Note 1), unless otherwise noted.)
Characteristic
Symbol
Min
Typ
Max
Unit
Vth(I HS)
Vth(I LS)
−
−
≥1.7
≤1.3
−
−
1.186
1.174
−
−
1.210
−
40
1.175
1.234
1.246
−
−
V
V
mV
V
DIFFERENTIAL AMPLIFIER DISABLE LOGIC (Pins 1, 6)
Logic Threshold Voltage Pin 1 (Pin 6 = 0 V)
Enabled, High−Side Source and Load Current Sensing
Disabled, Low−Side Load and Source Return Current Sensing
V
VOLTAGE SENSING (Pins 5, 6)
Positive Sensing Pin 5 to Pin 4
Internally Fixed Threshold Voltage
TA = 25°C
TA = Tlow to Thigh
Externally Adjusted Threshold Voltage (Pin 6 = 0 V)
Externally Adjusted Threshold Voltage (Pin 6 = 1.2 V)
Vth(V)
Voltage Sense, Input Bias Current (Pin 5)
IIB(V)
−
10
−
nA
Transconductance, Voltage Sensing Inputs to Drive Output
gm(V)
−
7.0
−
mhos
VOH
−
VCC − 0.8
−
V
ISource
15
20
−
mA
Operating Voltage Range
VCC
2.5 to 15
2.3 to 15
−
V
Power Supply Current (VCC = 6.0 V)
ICC
−
300
600
mA
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DRIVE OUTPUT (Pin 8)
High State Source Voltage (ISource = 10 mA)
High State Source Current (Pin 8 = 0 V)
TOTAL DEVICE (Pin 7)
PIN FUNCTION DESCRIPTION
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ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Pin
Name
Description
1
Current Sense Input A
This multi−mode current sensing input can be used for either source high−side, load high−side,
source−return low−side, or load low−side sensing. It is common to a Differential Amplifier, Inverting
Amplifier, and a Noninverting input path. Each of these sensing paths indirectly connect to the current
sense input of the Transconductance Amplifier. This input is connected to the high potential side of a
current sense resistor when used in source high−side, load high−side, or load low−side current
sensing modes. In source return low−side current sensing mode, this pin connects to the low potential
side of a current sense resistor.
2
Current Threshold Adjust
The current sense threshold can be externally adjusted over a range of 0 V to 200 mV with respect to
Pin 4, or internally fixed at 200 mV by connecting Pin 2 to VCC.
3
Compensation
This pin is connected to a high impedance node within the transconductance amplifier and is made
available for loop compensation. It can also be used as an input to directly control the Drive Output. An
active low at this pin will force the Drive Output into a high state.
4
Ground
This pin is the regulation control IC ground. The control threshold voltages are with respect to this pin.
5
Voltage Sense Input
This is the voltage sensing input of the Transconductance Amplifier. It is normally connected to the
power supply/battery charger output through a resistor divider. The input threshold is controlled by
Pin 6.
6
Current Sense Input B /
Voltage Threshold Adjust
This is a dual function input that is used for either high−side current sensing, or as a voltage threshold
adjustment for Pin 5. This input is connected to the low potential side of a current sense resistor when
used in source high−side or load high−side current sensing modes. In all low−side current sensing
modes, Pin 6 is available as a voltage threshold adjustment for Pin 5. The threshold can be externally
adjusted over a range of 0 V to 1.2 V with respect to Pin 4, or internally fixed at 1.2 V by connecting
Pin 6 to VCC.
7
VCC
This is the positive supply voltage for the regulation control IC. The typical operating voltage range is
2.3 V to 15 V with respect to Pin 4.
8
Drive Output
This is a source−only output that normally connects to a linear or switching regulator control circuit.
This output is capable of 15 mA, allowing it to directly drive an optoisolator in primary side control
applications where galvanic isolation is required.
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1.0
4.0
−8.0
−25
0
25
50
75
100
12
VPin 5
0.8
8.0
0.6
6.0
0.4
4.0
0.2
VPin 6−VPin 5
0.2
0.4
0.6
0.8
2.0
1.0
1.2
0
1.6
1.4
50
75
100
125
0
0
VCC
−40
2.0
VPin 1−VPin 6
−80
VCC = 6.0 V
VO = 1.0 V
IO = 1.0 mA
Pin 1 = VCC
TA = 25°C
VPin 6
−120
−160
−200
4.0
6.0
8.0
10
Differential Amplifier is active for
source high−side and load high−side
current sensing. Both vertical axis are
expressed in millivolts down to VCC.
−240
−280
0
40
80
120
12
160
200
240
14
280
VPin 2, CURRENT THRESHOLD ADJUST (V)
Figure 4. Closed−Loop Voltage Sensing Input
versus Voltage Threshold Adjust
Figure 5. Closed−Loop Current Sense Input B
versus Current Threshold Adjust
120
12
10
8.0
6.0
VPin 5
80
4.0
VPin 2−VPin 1
40
2.0
GND
40
80
120
160
200
240
0
280
V Pin 1, CURRENT SENSE INPUT A (mV)
14
Noninverting input path is active
for load low−side current sensing.
VCC = 6.0 V
VO = 1.0 V
IO = 1.0 mA
TA = 25°C
0
25
VPin 6, VOLTAGE THRESHOLD ADJUST (V)
280
0
V Pin 6 , CURRENT SENSE INPUT B (mV)
14
10
160
0
TA, AMBIENT TEMPERATURE (°C)
1.0
200
−25
Figure 3. Current Sensing
Threshold Change versus Temperature
16
240
1
1 − Source High−Side and Load High−Side
2 − Source Return Low−Side
3 − Load Low−Side
TA, AMBIENT TEMPERATURE (°C)
VCC = 6.0 V
VO = 1.0 V
IO = 1.0 mA
TA = 25°C
1.2
2
−2.0
Figure 2. Voltage Sensing
Threshold Change versus Temperature
1.6
1.4
3
−3.0
−50
125
V Pin 6 −V Pin 5 , INPUT DIFFERENCE VOLTAGE (mV)
−12
−50
−1.0
0
14
VCC = 6.0 V
VO = 1.0 V
IO = 1.0 mA
TA = 25°C
GND
−40
VPin 5
−80
10
−120
8.0
−160
6.0
−200
VPin 2−|VPin 1|
−240
−260
0
40
80
120
4.0
Inverting Amplifier is
2.0
active for source return
low−side current sensing.
0
160
200
240
280
VPin 2, CURRENT THRESHOLD ADJUST (mV)
VPin 2, CURRENT THRESHOLD ADJUST (mV)
Figure 6. Closed−Loop Current Sensing Input A
versus Current Threshold Adjust
Figure 7. Closed−Loop Current Sensing Input A
versus Current Threshold Adjust
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12
V Pin 1 −V Pin 6 , INPUT DIFFERENCE VOLTAGE (mV)
−4.0
0
V Pin 2 −|V Pin 1 |, INPUT DIFFERENCE VOLTAGE (mV)
0
0
0
V Pin 1, CURRENT SENSE INPUT A (mV)
VCC = 6.0 V
Δ V th(I HS), CURRENT SENSING
THRESHOLD CHANGE (mV)
VCC = 6.0 V
V Pin 2 −V Pin 1, INPUT DIFFERENCE VOLTAGE (mV)
V Pin 5 , VOLTAGE SENSING INPUT (V)
Δ Vth(v) , VOLTAGE SENSING THRESHOLD CHANGE (mV)
MC33341
50
Phase
100
40
120
Gain
30
140
20
10
VCC = 6.0 V
VO = 1.0 V
RL = 1.0 k
Pin 3 = 1.0 nF
TA = 25°C
160
φ, EXCESS PHASE (°)
80
180
0
1.0 k
10 k
100 k
1.0 M
80
120
30
Gain
140
20
10
VCC = 6.0 V
VO = 1.0 V
RL = 1.0 k
Pin 3 = 1.8 nF
TA = 25°C
0
1.0 k
160
180
10 k
100 k
1.0 M
Figure 8. Bode Plot
Voltage Sensing Inputs to Drive Output
Figure 9. Bode Plot
Current Sensing Inputs to Drive Output
VCC = 6.0 V
VO = 1.0 V
TA = 25°C
4.0
2.0
0.2
0.3
0.5
1.0
2.0
3.0
5.0
10
IO, DRIVE OUTPUT LOAD CURRENT (mA)
8.0
I CC, SUPPLY CURRENT, DRIVE OUTPUT LOW STATE (mA)
VCC = 6.0 V
TA = 25°C
−0.4
−0.8
−1.2
−1.6
4.0
8.0
12
16
VCC = 6.0 V
VO = 1.0 V
TA = 25°C
6.0
4.0
2.0
0
0.1
0.2
0.3
0.5
1.0
2.0
3.0
5.0
10
IO, DRIVE OUTPUT LOAD CURRENT (mA)
Figure 11. Transconductance
Current Sensing Inputs to Drive Output
0
VCC
100
40
Figure 10. Transconductance
Voltage Sensing Inputs to Drive Output
V OH , OUTPUT SOURCE SATURATION VOLTAGE (V)
Phase
High−Side Sensing
f, FREQUENCY (Hz)
6.0
−2.0
0
Phase
Low−Side Sensing
50
f, FREQUENCY (Hz)
8.0
0
0.1
60
20
IL, OUTPUT LOAD CURRENT (mA)
1.0
Drive Output High State
0.8
IO = 0 mA
TA = 25°C
0.6
0.4
Drive Output Low State
0.2
0
0
Figure 12. Drive Output High State
Source Saturation versus Load Current
4.0
8.0
12
VCC, SUPPLY VOLTAGE (V)
Figure 13. Supply Current
versus Supply Voltage
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φ, EXCESS PHASE (°)
A VOL(I), CURRENT SENSING OPEN−LOOP
VOLTAGE GAIN (dB)
60
g m(I), CURRENT SENSING TRANSCONDUCTANCE (mhos)
g m(v) , VOLTAGE SENSING TRANSCONDUCTANCE (mhos)
A VOL(V) , VOLTAGE SENSING OPEN−LOOP
VOLTAGE GAIN (dB)
MC33341
MC33341
INTRODUCTION
Power supplies and battery chargers require precise
control of output voltage and current in order to prevent
catastrophic damage to the system load. Many present day
power sources contain a wide assortment of building blocks
and glue devices to perform the required sensing for proper
regulation. Typical feedback loop circuits may consist of a
voltage and current amplifier, level shifting circuitry,
summing circuitry and a reference. The MC33341 contains
all of these basic functions in a manner that is easily
adaptable to many of the various power source−load
configurations.
current sensing modes, Pin 6 is available, and can be used to
lower the regulation threshold of Pin 5. This threshold can
be externally adjusted over a range of 0 V to 1.2 V with
respect to the IC ground at Pin 4.
Current Sensing
Current sensing is accomplished by monitoring the
voltage that appears across sense resistor RS, level shifting
it with respect to Pin 4 if required, and applying it to the
noninverting Isen input of the transconductance amplifier. In
order to allow for maximum circuit flexibility, there are
three methods of current sensing, each with different
internal paths.
In source high−side (Figures 14 and 15) and load
high−side (Figures 18 and 19) current sensing, the
Differential Amplifier is active with a gain of 1.0. Pin 1
connects to the high potential side of current sense resistor
RS while Pin 6 connects to the low side. Logic circuitry is
provided to disable the Differential Amplifier output
whenever low−side current sensing is required. This circuit
clamps the Differential Amplifier output high which
disconnects it from the Isen input of the Transconductance
Amplifier. This happens if Pin 1 is less than 1.2 V or if Pin 1
is less than Pin 6.
With source return low−side current sensing (Figures 16
and 17), the Inverting Amplifier is active with a gain of −1.0.
Pin 1 connects to the low potential side of current sense
resistor RS while Pin 4 connects to the high side. Note that
a negative voltage appears across RS with respect to Pin 4.
In load low−side current sensing (Figures 20 and 21) a
Noninverting input path is active with a gain of 1.0. Pin 1
connects to the high potential side of current sense resistor
RS while Pin 4 connects to the low side. The Noninverting
input path lies from Pin 1, through the Inverting Amplifier
input and feedback resistors R, to the cathode of the output
diode. With load low−side current sensing, Pin 1 will be
more positive than Pin 4, forcing the Inverting Amplifier
output low. This causes the diode to be reverse biased, thus
preventing the output stage of the amplifier from loading the
input signal that is flowing through the feedback resistors.
The regulation threshold in all of the current sensing
modes is internally fixed at 200 mV with Pin 2 connected to
VCC. Pin 2 can be used to externally adjust the threshold
over a range of 0 to 200 mV with respect to the IC ground
at Pin 4.
OPERATING DESCRIPTION
The MC33341 is an analog regulation control circuit that
is specifically designed to simultaneously close the voltage
and current feedback loops in power supply and battery
charger applications. This device can control the feedback
loop in either constant−voltage or constant−current mode
with automatic crossover. A concise description of the
integrated circuit blocks is given below. Refer to the block
diagram in Figure 14.
Transconductance Amplifier
A quad input transconductance amplifier is used to control
the feedback loop. This amplifier has separate voltage and
current channels, each with a sense and a threshold input.
Within a given channel, if the sense input level exceeds that
of the threshold input, the amplifier output is driven high.
The channel with the largest difference between the sense
and threshold inputs will set the output source current of the
amplifier and thus dominate control of the feedback loop.
The amplifier output appears at Pin 8 and is a source−only
type that is capable of 15 mA.
A high impedance node within the transconductance
amplifier is made available at Pin 3 for loop compensation.
This pin can sink and source up to 10 mA of current. System
stability is achieved by connecting a capacitor from Pin 3 to
ground. The Compensation Pin signal is out of phase with
respect to the Drive Output. By actively clamping Pin 3 low,
the Drive Output is forced into a high state. This, in effect,
will shutdown the power supply or battery charger, by
forcing the output voltage and current regulation threshold
down towards zero.
Voltage Sensing
Reference
The voltage that appears across the load is monitored by
the noninverting Vsen input of the transconductance
amplifier. This voltage is resistively scaled down and
connected to Pin 5. The threshold at which voltage
regulation occurs is set by the level present at the inverting
Vth input of the transconductance amplifier. This level is
controlled by Pin 6. In source high−side and load high−side
current sensing modes, Pin 6 must be connected to the low
potential side of current sense resistor RS. Under these
conditions, the voltage regulation threshold is internally
fixed at 1.2 V. In source return low−side and load low−side
An internal band gap reference is used to set the 1.2 V
voltage threshold and 200 mV current threshold. The
reference is initially trimmed to a ±1.0% tolerance at
TA = 25°C and is guaranteed to be within ±2.0% over an
ambient operating temperature range of −25° to 85°C.
Applications
Each of the application circuits illustrate the flexibility of
this device. The circuits shown in Figures 14 through 21
contain an optoisolator connected from the Drive Output at
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MC33341
drop across RS could exceed 1.6 V. Depending upon the
current sensing configuration used, this will result in
forward biasing of either the internal VCC clamp diode,
Pin 6, or the device substrate, Pin 1. Under these conditions,
input series resistor R3 is required. The peak input current
should be limited to 20 mA. Excessively large values for R3
will degrade the current sensing accuracy. Figure 22 shows
a method of bounding the voltage drop across RS without
sacrificing current sensing accuracy.
Pin 8 to ground. This configuration is shown for ease of
understanding and would normally be used to provide an
isolated control signal to a primary side switching regulator
controller. In non−isolated, primary or secondary side
applications, a load resistor can be placed from Pin 8 to
ground. This resistor will convert the Drive Output current
to a voltage for direct control of a regulator.
In applications where excessively high peak currents are
possible from the source or load, the load induced voltage
RS
Source
Load
R2
R3
8
7
6
VCC
Differential Amp
Disable Logic 0.4 V
Opto
Isolator
Vsen
Vth
Differential Amp
R
R1
1.2 V
VCC
R
VCC
VCC
VCC
1.2 V
5
V
Transconductance
Amp
Isen
R
Ith
I
VCC
R
Reference
VCC
R
VCC
R
Battery or
Resistive
Load
0.2 V 0.4 V 1.2 V
VCC
0.2 V
Inverting Amp
1
2
3
4
Comp
Source
Return
Load
The above figure shows the MC33341 configured for source high−side current sensing allowing a common ground path between Load − and
Source Return −. The Differential Amplifier inputs, Pins 1 and 6, are used to sense the load induced voltage drop that appears across resistor
RS. The internal voltage and current regulation thresholds are selected by the respective external connections of Pins 2 and 6. Resistor R3
is required in applications where a high peak level of reverse current is possible if the source inputs are shorted. The resistor value should
be chosen to limit the input current of the internal VCC clamp diode to less than 20 mA. Excessively large values for R3 will degrade the
current sensing accuracy.
V reg + V
ǒ
Ǔ
R2 ) 1
th(V) R1
ǒ
Ǔ
+ 1.2 R2 ) 1
R1
V
I reg +
th(IHS)
R
S
+ 0.2
R
S
Figure 14. Source High−Side Current Sensing with
Internally Fixed Voltage and Current Thresholds
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R3 +
ǒIpkRSǓ–0.6
0.02
MC33341
RS
Source
Load
R2
R3
8
7
6
VCC
Differential Amp
Disable Logic 0.4 V
Opto
Isolator
Vsen
Vth
Differential Amp
R
R1
1.2 V
VCC
R
VCC
VCC
VCC
1.2 V
5
V
Transconductance
Amp
Isen
R
Ith
I
VCC
R
Reference
VCC
R
VCC
R
Battery or
Resistive
Load
0.2 V 0.4 V 1.2 V
VCC
0.2 V
Inverting Amp
1
2
3
Current
Control
4
Comp
Source
Return
Load
The above figure shows the MC33341 configured for source high−side current sensing with an externally adjustable current threshold.
Operation of this circuit is similar to that of Figure 14. The current regulation threshold can be adjusted over a range of 0 V to 200 mV with
respect to Pin 4.
V reg + V
ǒ
Ǔ
R2 ) 1
th(V) R1
ǒ
V
I reg +
th(Pin2)
R
S
R3 +
ǒIpkRSǓ–0.6
0.02
Ǔ
+ 1.2 R2 ) 1
R1
Figure 15. Source High−Side Current Sensing with
Externally Adjustable Current and Internally Fixed Voltage Thresholds
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MC33341
Source
Load
R2
8
7
6
VCC
Differential Amp
Disable Logic 0.4 V
Opto
Isolator
Vsen
Vth
Differential Amp
R
R1
1.2 V
VCC
R
VCC
VCC
VCC
1.2 V
5
V
Transconductance
Amp
Isen
R
Ith
I
VCC
R
Reference
VCC
R
VCC
R
Battery or
Resistive
Load
0.2 V 0.4 V 1.2 V
VCC
0.2 V
Inverting Amp
1
2
3
4
Comp
R3
RS
Source
Return
Load
The above figure shows the MC33341 configured for source return low−side current sensing allowing a common power path between
Source + and Load +. This configuration is especially suited for negative output applications where a common ground path, Source + to
Load +, is desired. The Inverting Amplifier inputs, Pins 1 and 4, are used to sense the load induced voltage drop that appears across resistor
RS. The internal voltage and current regulation thresholds are selected by the respective external connections of Pins 2 and 6. Resistor R3
is required in applications where high peak levels of inrush current are possible. The resistor value should be chosen to limit the negative
substrate current to less than 20 mA. Excessively large values for R3 will degrade the current sensing accuracy.
V reg + V
ǒ
Ǔ
R2 ) 1
th(V) R1
ǒ
Ǔ
+ 1.2 R2 ) 1
R1
V
I reg +
th(ILS–)
R
S
R3 +
ǒIpkRSǓ–0.6
+ –0.2
R
S
Figure 16. Source Return Low−Side Current Sensing with
Internally Fixed Current and Voltage Thresholds
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0.02
MC33341
Source
Load
R2
Voltage
Control
8
7
6
VCC
Differential Amp
Disable Logic 0.4 V
Opto
Isolator
Vsen
Vth
Differential Amp
R
R1
1.2 V
VCC
R
VCC
VCC
VCC
1.2 V
5
V
Transconductance
Amp
Isen
R
Ith
I
VCC
R
Reference
VCC
R
VCC
R
Battery or
Resistive
Load
0.2 V 0.4 V 1.2 V
VCC
0.2 V
Inverting Amp
1
2
3
4
Current
Control
Comp
R3
RS
Source
Return
Load
The above figure shows the MC33341 configured for source return low−side current sensing with externally adjustable voltage and current
thresholds. Operation of this circuit is similar to that of Figure 16. The respective voltage and current regulation threshold can be adjusted
over a range of 0 to 1.6 V and 0 V to 200 mV with respect to Pin 4.
V reg + V
ǒ
Ǔ
R2 ) 1
th(Pin6) R1
V
I reg + –
th(Pin2)
R
S
R3 +
Figure 17. Source Return Low−Side Current Sensing with
Externally Adjustable Current and Voltage Thresholds
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ǒIpkRSǓ–0.6
0.02
MC33341
Source
Load
8
7
6
1.2 V
Vsen
Vth
Differential Amp
R
R1
1.2 V
VCC
R
VCC
VCC
Differential Amp
Disable Logic 0.4 V
Opto
Isolator
5
VCC
VCC
RS
R2
R3
V
Transconductance
Amp
Isen
R
Ith
I
VCC
R
Reference
VCC
R
VCC
R
Battery or
Resistive
Load
0.2 V 0.4 V 1.2 V
VCC
0.2 V
Inverting Amp
1
2
3
4
Comp
Source
Return
Load
The above figure shows the MC33341 configured for load high−side current sensing allowing common paths for both power and ground,
between the source and load. The Differential Amplifier inputs, Pins 1 and 6, are used to sense the load induced voltage drop that appears
across resistor RS. The internal voltage and current regulation thresholds are selected by the respective external connections of Pins 2 and
6. Resistor R3 is required in applications where high peak levels of load current are possible from the battery or load bypass capacitor. The
resistor value should be chosen to limit the input current of the internal VCC clamp diode to less than 20 mA. Excessively large values for
R3 ill degrade the current sensing accuracy.
V reg + V
ǒ
Ǔ
R2 ) 1
th(V) R1
ǒ
Ǔ
+ 1.2 R2 ) 1
R1
V
I reg +
th(IHS)
R
S
+ 0.2
R
S
Figure 18. Load High−Side Current Sensing with
Internally Fixed Current and Voltage Thresholds
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R3 +
ǒIpkRSǓ–0.6
0.02
MC33341
Source
Load
R2
RS
R3
8
7
6
VCC
Differential Amp
Disable Logic 0.4 V
Opto
Isolator
Differential Amp
R
R1
1.2 V
VCC
R
VCC
VCC
VCC
1.2 V
5
Vsen
Vth
V
Transconductance
Amp
Isen
R
Ith
I
VCC
R
Reference
VCC
R
VCC
R
Battery or
Resistive
Load
0.2 V 0.4 V 1.2 V
VCC
0.2 V
Inverting Amp
1
2
3
Current
Control
4
Comp
Source
Return
Load
The above figure shows the MC33341 configured for load high−side current sensing with an externally adjustable current threshold. Operation of this circuit is similar to that of Figure 18. The current regulation threshold can be adjusted over a range of 0 V to 200 mV with respect
to Pin 4.
V reg + V
ǒ
Ǔ
R2 ) 1
th(V) R1
ǒ
V
I reg +
th(Pin2)
R
S
R3 +
ǒIpkRSǓ–0.6
0.02
Ǔ
+ 1.2 R2 ) 1
R1
Figure 19. Load High−Side Current Sensing with
Externally Adjustable Current and Internally Fixed Voltage Thresholds
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MC33341
Source
Load
R2
8
7
6
VCC
Differential Amp
Disable Logic 0.4 V
Opto
Isolator
Vsen
Vth
Differential Amp
R
R1
1.2 V
VCC
R
VCC
VCC
VCC
1.2 V
5
V
Transconductance
Amp
Isen
R
Ith
I
VCC
R
Reference
VCC
R
VCC
R
Battery or
Resistive
Load
0.2 V 0.4 V 1.2 V
VCC
0.2 V
Inverting Amp
1
2
3
4
R3
RS
Comp
Source
Return
Load
The above figure shows the MC33341 configured for load low−side current sensing allowing common paths for both power and ground,
between the source and load. The Noninverting input paths, Pins 1 and 4, are used to sense the load induced voltage drop that appears
across resistor RS. The internal voltage and current regulation thresholds are selected by the respective external connections of Pins 2 and
6. Resistor R3 is required in applications where high peak levels of load current are possible from the battery or load bypass capacitor. The
resistor value should be chosen to limit the negative substratecurrent to less than 20 mA. Excessively large values for R3 will degrade the
current sensing accuracy.
V reg + V
ǒ
Ǔ
R2 ) 1
th(V) R1
ǒ
Ǔ
+ 1.2 R2 ) 1
R1
V
I reg +
th(ILS))
R
S
+ 0.2
R
S
Figure 20. Load Low−Side Current Sensing with
Internally Fixed Current and Voltage Thresholds
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R3 +
ǒIpkRSǓ–0.6
0.02
MC33341
Source
Load
R2
Voltage
Current
8
7
6
VCC
Differential Amp
Disable Logic 0.4 V
Opto
Isolator
Vsen
Vth
Differential Amp
R
R1
1.2 V
VCC
R
VCC
VCC
VCC
1.2 V
5
V
Transconductance
Amp
Isen
R
Ith
I
VCC
R
Reference
VCC
R
VCC
R
Battery or
Resistive
Load
0.2 V 0.4 V 1.2 V
VCC
0.2 V
Inverting Amp
1
2
3
4
R3
Current
Control
RS
Comp
Source
Return
Load
The above figure shows the MC33341 configured for load low−side current sensing with an externally adjustable voltage and current
threshold. Operation of this circuit is similar to that of Figure 20. The respective voltage and current regulation threshold can be adjusted
over a range of 0 to 1.2 V and 0 V to 200 mV, with respect to Pin 4.
V reg + V
ǒ
Ǔ
R2 ) 1
th(Pin6) R1
V
I reg +
th(Pin2)
R
S
R3 +
Figure 21. Load Low−Side Current Sensing with
Externally Adjustable Current and Voltage Thresholds
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ǒIpkRSǓ–0.6
0.02
MC33341
Source
Load
RS
8
Input
Short
7
6
5
Output
Short
MC33341
1
2
3
4
Source
Return
Load
NOTE: An excessive load induced voltage across RS can occur if either the source input or load output is shorted. This voltage can
easily be bounded with the addition of the diodes shown without degrading the current sensing accuracy. This bounding technique
can be used in any of the MC33341 applications where high peak currents are anticipated.
Figure 22. Current Sense Resistor Bounding
Source
8
7
6
Load
Output 2
Load
Output 1
Load
Output Common
5
MC33341
1
2
3
4
Source
Opto
Isolator
8
7
6
5
MC33341
1
2
3
4
Source
Return
NOTE: Multiple outputs can be controlled by summing the error signal into a common optoisolator. The converter output with the largest
voltage or current error will dominate control of the feedback loop.
Figure 23. Multiple Output Current and Voltage Regulation
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MC33341
0.2
Input
12 V to 16 V
MTP2955
Output
10 V/1.0 A
82.5 k
8
7
6
VCC
Differential Amp
Disable Logic 0.4 V
Vsen
Vth
Differential Amp
R
R
11.1 k
1.2 V
VCC
10
VCC
VCC
VCC
1.2 V
5
V
Transconductance
Amp
10
Isen
R
I
Ith
VCC
R
Reference
VCC
R
VCC
R
0.2 V 0.4 V 1.2 V
Variable
Resistive
Load
VCC
0.2 V
Inverting Amp
1
2
3
4
0.01
3.0 k
Output
Ground
Input
Ground
Figure 24. 10 V/1.0 A Constant−Voltage Constant−Current Regulator
V O, OUTPUT VOLTAGE (V)
10
8.0
6.0
4.0
2.0
0
0
0.2
04
0.6
0.8
1.0
IO, OUTPUT LOAD CURRENT (A)
Figure 24 shows the MC33341 configured as a source high−side constant−voltage constant−current regulator. The regulator is designed for
an output voltage of 10 V at 1.0 A. Figure 25 shows the regulator’s output characteristics as the load is varied. Source return low−side, load
high−side, and load low−side configurations will each exhibit a nearly identical load regulation characteristic. A heatsink is required for the
MTP2955 series pass element.
Figure 25. Output Load Regulation
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16
MC33341
200 mH
MTP2955
Input
12 V
0.25
1N5821
Output
5.87 V/800 mA
100
68 k
3.0 k
8
7
6
VCC
Differential Amp
Disable Logic 0.4 V
1.2 V
VCC
100
Differential Amp
R
R
VCC
VCC
VCC
1.2 V
5
Vsen
Vth
Transconductance
Amp
V
Isen
R
Ith
I
VCC
R
Reference
VCC
R
VCC
R
0.2 V 0.4 V 1.2 V
VCC
0.2 V
Inverting Amp
1
2
3
4
12 k
Input
Ground
Output
Ground
Figure 26 shows that the MC33341 can be configured as a high−side constant−current constant−voltage switch mode charger. This circuit
operates as a step down converter. With a nominal input voltage and output load current as stated above, the switching frequency is
approximately 28 kHz with and an associated conversion efficiency of 86 percent. The switching frequency will vary with changes in input
voltage and load current.
Figure 26. Constant−Current Constant−Voltage Switch Mode Charger
ORDERING INFORMATION
Device
Operating Temperature Range
MC33341D
MC33341DG
MC33341DR2
MC33341DR2G
TA = −25° to +85°C
MC33341P
MC33341PG
Package
Shipping†
SOIC−8
98 Units / Rail
SOIC−8
(Pb−Free)
98 Units / Rail
SOIC−8
2500 / Tape & Reel
SOIC−8
(Pb−Free)
2500 / Tape & Reel
PDIP−8
50 Units / Rail
PDIP−8
(Pb−Free)
50 Units / Rail
†For information on tape and reel specifications, including part orientation and tape sizes, please refer to our Tape and Reel Packaging
Specifications Brochure, BRD8011/D.
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17
MC33341
PACKAGE DIMENSIONS
SOIC−8 NB
D SUFFIX
PLASTIC PACKAGE
CASE 751−07
ISSUE AH
NOTES:
1. DIMENSIONING AND TOLERANCING PER
ANSI Y14.5M, 1982.
2. CONTROLLING DIMENSION: MILLIMETER.
3. DIMENSION A AND B DO NOT INCLUDE
MOLD PROTRUSION.
4. MAXIMUM MOLD PROTRUSION 0.15 (0.006)
PER SIDE.
5. DIMENSION D DOES NOT INCLUDE DAMBAR
PROTRUSION. ALLOWABLE DAMBAR
PROTRUSION SHALL BE 0.127 (0.005) TOTAL
IN EXCESS OF THE D DIMENSION AT
MAXIMUM MATERIAL CONDITION.
6. 751−01 THRU 751−06 ARE OBSOLETE. NEW
STANDARD IS 751−07.
−X−
A
8
5
S
B
1
0.25 (0.010)
M
Y
M
4
K
−Y−
G
C
N
DIM
A
B
C
D
G
H
J
K
M
N
S
X 45 _
SEATING
PLANE
−Z−
0.10 (0.004)
H
D
0.25 (0.010)
M
Z Y
S
X
M
J
S
SOLDERING FOOTPRINT*
1.52
0.060
7.0
0.275
4.0
0.155
0.6
0.024
1.270
0.050
SCALE 6:1
mm Ǔ
ǒinches
*For additional information on our Pb−Free strategy and soldering
details, please download the ON Semiconductor Soldering and
Mounting Techniques Reference Manual, SOLDERRM/D.
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18
MILLIMETERS
MIN
MAX
4.80
5.00
3.80
4.00
1.35
1.75
0.33
0.51
1.27 BSC
0.10
0.25
0.19
0.25
0.40
1.27
0_
8_
0.25
0.50
5.80
6.20
INCHES
MIN
MAX
0.189
0.197
0.150
0.157
0.053
0.069
0.013
0.020
0.050 BSC
0.004
0.010
0.007
0.010
0.016
0.050
0 _
8 _
0.010
0.020
0.228
0.244
MC33341
PACKAGE DIMENSIONS
PDIP−8
P SUFFIX
PLASTIC PACKAGE
CASE 626−05
ISSUE L
8
NOTES:
1. DIMENSION L TO CENTER OF LEAD WHEN
FORMED PARALLEL.
2. PACKAGE CONTOUR OPTIONAL (ROUND OR
SQUARE CORNERS).
3. DIMENSIONING AND TOLERANCING PER ANSI
Y14.5M, 1982.
5
−B−
1
4
F
−A−
NOTE 2
L
C
J
−T−
MILLIMETERS
MIN
MAX
9.40
10.16
6.10
6.60
3.94
4.45
0.38
0.51
1.02
1.78
2.54 BSC
0.76
1.27
0.20
0.30
2.92
3.43
7.62 BSC
−−−
10_
0.76
1.01
INCHES
MIN
MAX
0.370
0.400
0.240
0.260
0.155
0.175
0.015
0.020
0.040
0.070
0.100 BSC
0.030
0.050
0.008
0.012
0.115
0.135
0.300 BSC
−−−
10_
0.030
0.040
N
SEATING
PLANE
D
H
DIM
A
B
C
D
F
G
H
J
K
L
M
N
M
K
G
0.13 (0.005)
M
T A
M
B
M
ON Semiconductor and
are registered trademarks of Semiconductor Components Industries, LLC (SCILLC). SCILLC reserves the right to make changes without further notice
to any products herein. SCILLC makes no warranty, representation or guarantee regarding the suitability of its products for any particular purpose, nor does SCILLC assume any liability
arising out of the application or use of any product or circuit, and specifically disclaims any and all liability, including without limitation special, consequential or incidental damages.
“Typical” parameters which may be provided in SCILLC data sheets and/or specifications can and do vary in different applications and actual performance may vary over time. All
operating parameters, including “Typicals” must be validated for each customer application by customer’s technical experts. SCILLC does not convey any license under its patent rights
nor the rights of others. SCILLC products are not designed, intended, or authorized for use as components in systems intended for surgical implant into the body, or other applications
intended to support or sustain life, or for any other application in which the failure of the SCILLC product could create a situation where personal injury or death may occur. Should
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and distributors harmless against all claims, costs, damages, and expenses, and reasonable attorney fees arising out of, directly or indirectly, any claim of personal injury or death
associated with such unintended or unauthorized use, even if such claim alleges that SCILLC was negligent regarding the design or manufacture of the part. SCILLC is an Equal
Opportunity/Affirmative Action Employer. This literature is subject to all applicable copyright laws and is not for resale in any manner.
PUBLICATION ORDERING INFORMATION
LITERATURE FULFILLMENT:
Literature Distribution Center for ON Semiconductor
P.O. Box 5163, Denver, Colorado 80217 USA
Phone: 303−675−2175 or 800−344−3860 Toll Free USA/Canada
Fax: 303−675−2176 or 800−344−3867 Toll Free USA/Canada
Email: [email protected]
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USA/Canada
Europe, Middle East and Africa Technical Support:
Phone: 421 33 790 2910
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Phone: 81−3−5773−3850
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19
ON Semiconductor Website: www.onsemi.com
Order Literature: http://www.onsemi.com/orderlit
For additional information, please contact your local
Sales Representative
MC33341/D