DS8096D 01

RT8096D
1A, 1.5MHz, 6V CMCOT Synchronous Step-Down Converter
General Description
Features
The RT8096D is a high efficiency synchronous stepdown DC/DC converter. Its input voltage range is from
2.5V to 6V and provides an adjustable regulated output
voltage from 0.6V to 3.4V while delivering up to 1A of
output current.





Efficiency Up to 95%
RDSON 160m HS / 110m LS
VIN Range 2.5V to 6V
VREF 0.6V with 2% Accuracy
CMCOT ™ Control Loop Design
for
Best
Transient Response, Robust Loop Stability with
Low-ESR (MLCC) COUT
The internal synchronous low on-resistance power
switches increase efficiency and eliminate the need for
an external Schottky diode. The Current Mode
Constant-On-time (CMCOT) operation with internal
compensation allows the transient response to be
optimized over a wide range of loads and output
capacitors. The RT8096D is available in the TSOT-235 and TSOT-23-6 packages.

Fixed Soft-Start 1.2ms; PGOOD Function in
TSOT-23-6

Cycle-by-Cycle Over Current Protection
Input Under Voltage Lockout
Output Under Voltage Protection (UVP Hiccup)
Thermal Shutdown Protection



Applications
Ordering Information

RT8096D

Package Type
J5 : TSOT-23-5
J6 : TSOT-23-6
Lead Plating System
G : Green (Halogen Free and Pb Free)

STB, Cable Modem, & xDSL Platforms
LCD TV Power Supply & Metering Platforms
General Purpose Point of Load (POL)
Marking Information
RT8096DHGJ5
UVP Trim Option
H: Hiccup
0N=DNN
PWM/PSM Mode
D : Forced PWM
0N= : Product Code
DNN : Date Code
RT8096DHGJ6
14=DNN
Note :
14= : Product Code
DNN : Date Code
Richtek products are :

RoHS compliant and compatible with the current
requirements of IPC/JEDEC J-STD-020.

Suitable for use in SnPb or Pb-free soldering processes.
Simplified Application Circuit
RT8096D
LX
VIN
VIN
CIN
L
VOUT
R1
EN
PG*
COUT
FB
GND
R2
*For TSOT-23-6 Package Only
Copyright © 2015 Richtek Technology Corporation. All rights reserved.
DS8096D-01
October
2015
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RT8096D
Pin Configurations
(TOP VIEW)
FB
VIN
FB
5
4
6
2
3
PG VIN
5
4
2
3
EN GND LX
EN GND LX
TSOT-23-5
TSOT-23-6
Functional Pin Description
Pin No.
Pin Name
Pin Function
TSOT-23-5
TSOT-23-6
1
1
EN
Enable Control Input.
2
2
GND
Power Ground.
3
3
LX
Switch Node.
4
4
VIN
Supply Voltage Input. The RT8096D operates from a 2.5V to 6V input.
5
6
FB
Feedback Voltage Input. An external resistor divider from the output to
GND, tapped to the FB pin, sets the output voltage.
--
5
PG
Power Good Indicator. The output of this pin is an open-drain with
external pull-up resistor. PG is pulled up when the FB voltage is within
90%, otherwise it is LOW.
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DS8096D-01
October
2015
RT8096D
Function Block Diagram
For TSOT-23-5 Package
EN
VIN
UVLO
Shut Down
Control
OTP
-
FB
VREF
Error
Amplifier
Ton
Comparator
+
-
+
RC
CCOMP
Logic
Control
LX
VIN
Driver
Current
Limit
Detector
LX
GND
Current
Sense
LX
Ton
LX
For TSOT-23-6 Package
EN
VIN
UVLO
Shut Down
Control
OTP
-
FB
VREF
Error
Amplifier
Comparator
+
+
RC
CCOMP
-
Logic
Control
VIN
Driver
Current
Limit
Detector
LX
GND
+
Current
Sense
-
LX
PG
Operation
The RT8096D is a synchronous low voltage step-down
converter that can support the input voltage range from
2.5V to 6V and the output current can be up to 1A. The
RT8096D uses a constant on-time, current mode
architecture. In normal operation, the high side PMOSFET is turned on when the switch controller is set
Low side MOSFET peak current is measured by internal
RSENSE. The error amplifier EA adjusts COMP voltage
by comparing the feedback signal (VFB) from the output
voltage with the internal 0.6V reference. When the load
current increases, it causes a drop in the feedback
voltage relative to the reference, then the COMP
by the comparator and is turned off when the Ton
comparator resets the switch controller.
voltage rises to allow higher inductor current to match
the load current.
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2015
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RT8096D
UV Comparator
If the feedback voltage (VFB) is lower than threshold
voltage 0.2V, the UV comparator's output will go high
and the switch controller will turn off the high side
MOSFET. The output under voltage protection is
designed to operate in Hiccup mode.
PGOOD Comparator
When the feedback voltage (VFB) is higher than
threshold voltage 0.54V, the PGOOD open drain output
will be high impedance. The internal PG MOSFET is
typical 100. The PGOOD signal delay time from EN is
about 2ms.
Enable Comparator
A logic-high enables the converter; a logic-low forces
the IC into shutdown mode.
Soft-Start (SS)
An internal current source charges an internal capacitor
to build the soft-start ramp voltage. The VFB voltage will
track the internal ramp voltage during soft-start interval.
The typical soft-start time is 1.2ms.
Over Current Protection (OCP)
The RT8096D provides over current protection by
detecting low side MOSFET valley inductor current. If
the sensed valley inductor current is over the current
limit threshold (1.5A typ.), the OCP will be triggered.
When OCP is tripped, the RT8096D will keep the over
current threshold level until the over current condition is
removed.
Thermal Shutdown (OTP)
The device implements an internal thermal shutdown
function when the junction temperature exceeds 150°C.
The thermal shutdown forces the device to stop
switching when the junction temperature exceeds the
thermal shutdown threshold. Once the die temperature
decreases below the hysteresis of 20°C, the device
reinstates the power up sequence.
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DS8096D-01
October
2015
RT8096D
Absolute Maximum Ratings
(Note 1)

Supply Input Voltage ---------------------------------------------------------------------------------------------0.3V to 6.5V

LX Pin Switch Voltage------------------------------------------------------------------------------------------- 0.3V to (VIN + 0.3V)
< 20ns ----------------------------------------------------------------------------------------------------------------4.5V to 7.5V

Power Dissipation, PD @ TA = 25C
TSOT-23-5 ----------------------------------------------------------------------------------------------------------0.43W
TSOT-23-6 ----------------------------------------------------------------------------------------------------------0.5W

Package Thermal Resistance
(Note 2)
TSOT-23-5, JA ----------------------------------------------------------------------------------------------------230.6C/W
TSOT-23-6, JA ----------------------------------------------------------------------------------------------------197.4C/W
TSOT-23-5, JC ----------------------------------------------------------------------------------------------------21.8C/W
TSOT-23-6, JC ----------------------------------------------------------------------------------------------------18.9C/W

Lead Temperature (Soldering, 10 sec.) ----------------------------------------------------------------------260C

Junction Temperature --------------------------------------------------------------------------------------------40C to 150C

Storage Temperature Range -----------------------------------------------------------------------------------65C to 150C

ESD Susceptibility
(Note 3)
HBM (Human Body Model) -------------------------------------------------------------------------------------2kV
Recommended Operating Conditions
(Note 4)

Supply Input Voltage ---------------------------------------------------------------------------------------------2.5V to 6V

Ambient Temperature Range-----------------------------------------------------------------------------------40C to 85C

Junction Temperature Range ----------------------------------------------------------------------------------40C to 125C
Electrical Characteristics
(VIN = 3.6V, TA = 25C, unless otherwise specified)
Parameter
Symbol
Min
Typ
Max
Unit
2.5
--
6
V
0.588
0.6
0.612
V
VFB = 3.3V
--
--
1
A
Active, VFB = 0.63V, Not Switching
--
300
--
Shutdown
--
--
1
Switching Leakage Current
--
--
1
A
Switching Frequency
--
1.5
--
MHz
Input Voltage
VIN
Feedback Reference Voltage
VREF
Feedback Leakage Current
IFB
DC Bias Current
Test Conditions
A
Switch On Resistance, High
RPMOS
ISW = 0.3A
--
160
--
m
Switch On Resistance, Low
RNMOS
ISW = 0.3A
--
110
--
m
Valley Current Limit
ILIM
1.1
1.5
2
A
Under-Voltage Lockout
Threshold
VUVLO
VDD Rising
--
2.25
2.5
VDD Falling
--
2
--
--
150
--
Over-Temperature Threshold
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October
2015
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C
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RT8096D
Parameter
Symbol
Test Conditions
Min
Typ
Max
Unit
Logic-High
VIH
1.5
--
--
Logic-Low
VIL
--
--
0.4
FB Rising
--
90
--
FB Falling
--
85
--
--
--
100

--
1.2
--
ms
Minimum Off Time
--
120
--
ns
Output Discharge Switch On
Resistance
--
1.8
--
k
Enable Input
Voltage
PG Pin Threshold
(relative to VOUT)
PG Open-Drain Impedance
(PG = low)
Soft-Start Time
TSS
V
%
Note 1. Stresses beyond those listed “Absolute Maximum Ratings” may cause permanent damage to the device. These are stress
ratings only, and functional operation of the device at these or any other conditions beyond those indicated in the
operational sections of the specifications is not implied. Exposure to absolute maximum rating conditions may affect device
reliability.
Note 2. JA is measured at TA = 25C on a high effective thermal conductivity four-layer test board per JEDEC 51-7. The first
layer of copper area is filled. JC is measured at the top of the package.
Note 3. Devices are ESD sensitive. Handling precaution recommended.
Note 4. The device is not guaranteed to function outside its operating conditions.
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DS8096D-01
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2015
RT8096D
Typical Application Circuit
VIN
CIN
10μF
RT8096D
LX
VIN
L
EN
CFF*
VOUT
R1
COUT
FB
PG*
GND
R2
*For TSOT-23-6 Package Only
*CFF : Optional for performance fine-tune
Table 1. Suggested Component Values
VOUT (V)
R1 (k)
R2 (k)
L (H)
COUT (F)
3.3
90
20
1 to 3.3
10
1.8
100
50
1 to 3.3
10
1.5
100
66.6
1 to 3.3
10
1.2
100
100
1 to 3.3
10
1.05
100
133
1 to 3.3
10
1
100
148
1 to 3.3
10
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2015
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RT8096D
Typical Operating Characteristics
Efficiency vs. Output Current
Efficiency vs. Output Current
100
100
90
80
VIN = 5V, VOUT = 3.3V
80
70
VIN = 3.3V, VOUT = 1.2V
70
Efficiency (%)
Efficiency (%)
90
60
50
40
30
50
40
30
20
10
10
0
0.2
0.4
0.6
0.8
VIN = 3.3V, VOUT = 1.2V
60
20
0
VIN = 5V, VOUT = 3.3V
0
0.001
1
0.01
Output Current (A)
Output Voltage vs. Output Current
1.28
3.40
1.26
3.38
1.24
Output Voltage (V)
Output Voltage (V)
1
Output Current (A)
Output Voltage vs. Output Current
1.22
1.20
1.18
1.16
3.36
3.34
3.32
3.30
3.28
1.14
VIN = 5V, VOUT = 3.3V
VIN = 3.3V, VOUT = 1.2V
1.12
3.26
0
0.2
0.4
0.6
0.8
1
0
0.2
Output Current (A)
0.4
0.6
0.8
1
Output Current (A)
Output Voltage vs. Input Voltage
Output Voltage vs. Input Voltage
1.26
3.40
3.38
Output Voltage (V)
1.24
Output Voltage (V)
0.1
1.22
1.20
1.18
1.16
3.36
3.34
3.32
3.30
3.28
3.26
1.14
3.24
VIN = 3V to 5.5V, VOUT = 1.2V, IOUT = 1A
1.12
VIN = 4.5V to 5.5V, V OUT = 3.3V, IOUT = 1A
3.22
3
3.5
4
4.5
5
Input Voltage (V)
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5.5
4.5
4.6
4.7
4.8
4.9
5
5.1
5.2
5.3
5.4
5.5
Input Voltage (V)
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RT8096D
Reference Voltage vs. Input Voltage
Switching Frequency vs. Temperature
0.65
1.8
Switching Frequency (MHz)1
Reference Voltage (V)
0.64
0.63
0.62
0.61
0.60
0.59
0.58
0.57
0.56
1.7
1.6
1.5
VIN = 5V, VOUT = 3.3V
1.4
VIN = 3.3V, VOUT = 1.2V
1.3
1.2
1.1
VIN = 2.5V to 5.5V, IOUT = 1A
IOUT = 0.5A
1.0
0.55
2.5
3
3.5
4
4.5
5
-50
5.5
-25
0
1.0
0.9
0.8
0.7
0.6
0.5
0.4
0.3
0.2
0.1
VEN = 0
-0.1
2.5
3
3.5
4
4.5
100
125
5
5.5
4.5
4.0
3.5
3.0
2.5
2.0
1.5
1.0
0.5
VEN = 0
0.0
-50
-25
0
25
50
75
100
125
Temperature (°C)
Quiescent Current vs. Temperature
Quiescent Current vs. Input Voltage
400
400
380
380
Quiescent Current (μA)
Quiescent Current (μA)
75
5.0
Input Voltage (V)
360
340
320
300
280
260
240
220
50
Shutdown Quiescent Current vs. Temperature
Shutdown Quiescent Current (μA)1
Shutdown Quiescent Current (μA)1
Shutdown Quiescent Current vs. Input Voltage
0.0
25
Temperature (°C)
Input Voltage (V)
VFB = 0.63V, LX No Switch
200
360
340
320
300
280
260
240
220
VIN = 5V
200
2.5
3
3.5
4
4.5
5
Input Voltage (V)
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2015
5.5
-50
-25
0
25
50
75
100
125
Temperature (°C)
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RT8096D
Inductor Current Limit vs. Temperature
3.0
2.5
2.5
Inductor Current (A)
Inductor Current (A)
Inductor Current Limit vs. Input Voltage
3.0
2.0
1.5
1.0
2.0
1.5
1.0
0.5
0.5
VOUT = 1.2V
VOUT = 1.2V
0.0
2.5
3
3.5
4
4.5
5
0.0
-50
5.5
-25
0
25
Input UVLO vs. Temperature
75
100
125
Enable Threshold vs. Temperature
2.5
1.4
2.4
Enable Threshold (V) 1
1.2
2.3
Input UVLO (V)
50
Temperature (°C)
Input Voltage (V)
Turn Off
2.2
2.1
2.0
1.9
Turn On
1.8
1.7
1.0
Enable On
0.8
Enable Off
0.6
0.4
0.2
1.6
VIN = 3.3V
VEN = 3.3V
0.0
1.5
-50
-25
0
25
50
75
100
-50
125
0
25
50
75
Temperature (°C)
Load Transient Response
Load Transient Response
VIN = 3.3V, VOUT = 1.2V,
IOUT = 0A to 1A, CFF = 22pF
VOUT
(50mV/Div)
100
125
VIN = 3.3V, VOUT = 1.2V,
IOUT = 0.5A to 1A, CFF = 22pF
VOUT
(20mV/Div)
IOUT
IOUT
(500mA/Div)
(500mA/Div)
Time (100s/Div)
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-25
Temperature (°C)
Time (100s/Div)
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2015
RT8096D
Voltage Ripple
Voltage Ripple
VOUT
(5mV/Div)
VOUT
(5mV/Div)
VLX
(2V/Div)
VLX
(2V/Div)
VIN = 3.3V, VOUT = 1.2V, IOUT = 1A
Time (500ns/Div)
Time (500ns/Div)
Power On from EN
Power Off from EN
VEN
(5V/Div)
VEN
(5V/Div)
VPGOOD
(2V/Div)
VPGOOD
(2V/Div)
VOUT
(1V/Div)
VOUT
(1V/Div)
IOUT
(1A/Div)
IOUT
(1A/Div)
VIN = 3.3V, VOUT = 1.2V, IOUT = 1A
VIN = 3.3V, VOUT = 1.2V, IOUT = 1A
Time (500s/Div)
Time (10s/Div)
Power On from EN
Power Off from EN
VEN
(5V/Div)
VEN
(5V/Div)
VPGOOD
(2V/Div)
VPGOOD
(2V/Div)
VOUT
(2V/Div)
VOUT
(2V/Div)
IOUT
(1A/Div)
IOUT
(1A/Div)
VIN = 5V, VOUT = 3.3V, IOUT = 1A
Time (500s/Div)
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DS8096D-01
October
VIN = 5V, VOUT = 3.3V, IOUT = 1A
2015
VIN = 5V, VOUT = 3.3V, IOUT = 1A
Time (10s/Div)
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RT8096D
Application Information
The RT8096D is a single-phase step-down converter. It
provides single feedback loop, constant on-time current
mode control with fast transient response. An internal
0.6V reference allows the output voltage to be precisely
regulated for low output voltage applications. A fixed
switching frequency (1.5MHz) oscillator and internal
compensation are integrated to minimize external
component count. Protection features include over
current protection, under voltage protection and over
temperature protection.
Output Voltage Setting
Connect a resistive voltage divider at the FB between
VOUT and GND to adjust the output voltage. The output
voltage is set according to the following equation :
VOUT = VREF   1 R1 
 R2 
where VREF is the feedback reference voltage 0.6V
(typ.).
VOUT
R1
FB
R2
GND
Figure 1. Setting VOUT with a Voltage Divider
Chip Enable and Disable
The EN pin allows for power sequencing between the
controller bias voltage and another voltage rail. The
RT8096D remains in shutdown if the EN pin is lower
than 400mV. When the EN pin rises above the VEN trip
point, the RT8096D begins a new initialization and softstart cycle.
voltage across the capacitor. This voltage clamps the
voltage at the FB pin, causing PWM pulse width to
increase slowly and in turn reduce the input surge
current. The internal 0.6V reference takes over the loop
control once the internal ramping-up voltage becomes
higher than 0.6V.
UVLO Protection
The RT8096D has input Under Voltage Lockout
protection (UVLO). If the input voltage exceeds the
UVLO rising threshold voltage (2.25V typ.), the
converter resets and prepares the PWM for operation.
If the input voltage falls below the UVLO
threshold voltage during normal operation, the
will stop switching. The UVLO rising and
threshold voltage has a hysteresis to prevent
caused reset.
falling
device
falling
noise-
Inductor Selection
The switching frequency (on-time) and operating point
(% ripple or LIR) determine the inductor value as shown
below :
L=
VOUT   VIN  VOUT 
fSW  LIR  ILOAD(MAX)  VIN
where LIR is the ratio of the peak-to-peak ripple current
to the average inductor current.
Find a low loss inductor having the lowest possible DC
resistance that fits in the allotted dimensions. The core
must be large enough not to saturate at the peak
inductor current (IPEAK) :
IPEAK = ILOAD(MAX) +  LIR  ILOAD(MAX) 
 2

The RT8096D provides an internal soft-start function to
The calculation above serves as a general reference.
To further improve transient response, the output
inductor can be further reduced. This relation should be
considered along with the selection of the output
capacitor.
prevent large inrush current and output voltage
overshoot when the converter starts up. The soft-start
Inductor saturation current should be chosen over IC’s
current limit.
Internal Soft-Start
(SS) automatically begins once the chip is enabled.
During soft-start, the internal soft-start capacitor
becomes charged and generates a linear ramping up
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DS8096D-01
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2015
RT8096D
Input Capacitor Selection
High quality ceramic input decoupling capacitor, such
as X5R or X7R, with values greater than 10F are
recommended for the input capacitor. The X5R and
X7R ceramic capacitors are usually selected for power
regulator capacitors because the dielectric material has
less capacitance variation and more temperature
stability.
Voltage rating and current rating are the key parameters
when selecting an input capacitor. Generally, selecting
an input capacitor with voltage rating 1.5 times greater
than the maximum input voltage is a conservatively safe
design.
The input capacitor is used to supply the input RMS
current, which can be approximately calculated using
the following equation :
IIN_RMS = ILOAD 
VOUT  VOUT 
 1
VIN 
VIN 
The next step is selecting a proper capacitor for RMS
current rating. One good design uses more than one
capacitor with low equivalent series resistance (ESR) in
parallel to form a capacitor bank.
The input capacitance value determines the input ripple
voltage of the regulator. The input voltage ripple can be
approximately calculated using the following equation :
VIN =
IOUT(MAX) VOUT  VOUT 

 1
CIN  fSW
VIN 
VIN 
Output Capacitor Selection
The output capacitor and the inductor form a low pass
filter in the Buck topology. In steady state condition, the
ripple current flowing into/out of the capacitor results in
ripple voltage. The output voltage ripple (VP-P) can be
calculated by the following equation :
1

VP_P = LIR  ILOAD(MAX)   ESR +
8  COUT  fSW 

When load transient occurs, the output capacitor
supplies the load current before the controller can
respond. Therefore, the ESR will dominate the output
voltage sag during load transient. The output voltage
undershoot (VSAG) can be calculated by the following
equation :
For a given output voltage sag specification, the ESR
value can be determined.
Another parameter that has influence on the output
voltage sag is the equivalent series inductance (ESL).
The rapid change in load current results in di/dt during
transient. Therefore, the ESL contributes to part of the
voltage sag. Using a capacitor with low ESL can obtain
better transient performance. Generally, using several
capacitors connected in parallel can have better
transient performance than using a single capacitor for
the same total ESR.
Thermal Considerations
For continuous operation, do not exceed absolute
maximum junction temperature. The maximum power
dissipation depends on the thermal resistance of the IC
package, PCB layout, rate of surrounding airflow, and
difference between junction and ambient temperature.
The maximum power dissipation can be calculated by
the following formula :
PD(MAX) = (TJ(MAX)  TA) / JA
where TJ(MAX) is the maximum junction temperature, TA
is the ambient temperature, and JA is the junction to
ambient thermal resistance.
For recommended operating condition specifications,
the maximum junction temperature is 125C. The
junction to ambient thermal resistance, JA, is layout
dependent. For TSOT-23-5 package, the thermal
resistance, JA, is 230.6C/W on a standard four-layer
thermal test board. For TSOT-23-6 package, the
thermal resistance, JA, is 197.4C/W on a standard
four-layer thermal test board. The maximum power
dissipation at TA = 25C can be calculated by the
following formula :
PD(MAX) = (125C  25C) / (230.6C/W) = 0.43W for
TSOT-23-5 package
PD(MAX) = (125C  25C) / (197.4C/W) = 0.5W for
TSOT-23-6 package
The maximum power dissipation depends on the
operating ambient temperature for fixed TJ(MAX) and
thermal resistance, JA. The derating curve in Figure 2
allows the designer to see the effect of rising ambient
temperature on the maximum power dissipation.
VSAG = ILOAD  ESR
Copyright © 2015 Richtek Technology Corporation. All rights reserved.
DS8096D-01
October
2015
is a registered trademark of Richtek Technology Corporation.
www.richtek.com
13
RT8096D
Maximum Power Dissipation (W)1
1.0
Four-Layer PCB
0.9
0.8
0.7
0.6
TSOT-23-6
0.5
0.4
0.3
TSOT-23-5
0.2
0.1
0.0
0
25
50
75
100
125
Ambient Temperature (°C)
Figure 2. Derating Curve of Maximum Power
Dissipation
Copyright © 2015 Richtek Technology Corporation. All rights reserved.
www.richtek.com
14
is a registered trademark of Richtek Technology Corporation.
DS8096D-01
October
2015
RT8096D
Outline Dimension
Symbol
Dimensions In Millimeters
Dimensions In Inches
Min
Max
Min
Max
A
0.700
1.000
0.028
0.039
A1
0.000
0.100
0.000
0.004
B
1.397
1.803
0.055
0.071
b
0.300
0.559
0.012
0.022
C
2.591
3.000
0.102
0.118
D
2.692
3.099
0.106
0.122
e
0.838
1.041
0.033
0.041
H
0.080
0.254
0.003
0.010
L
0.300
0.610
0.012
0.024
TSOT-23-5 Surface Mount Package
Copyright © 2015 Richtek Technology Corporation. All rights reserved.
DS8096D-01
October
2015
is a registered trademark of Richtek Technology Corporation.
www.richtek.com
15
RT8096D
Symbol
Dimensions In Millimeters
Dimensions In Inches
Min
Max
Min
Max
A
0.700
1.000
0.028
0.039
A1
0.000
0.100
0.000
0.004
B
1.397
1.803
0.055
0.071
b
0.300
0.559
0.012
0.022
C
2.591
3.000
0.102
0.118
D
2.692
3.099
0.106
0.122
e
0.838
1.041
0.033
0.041
H
0.080
0.254
0.003
0.010
L
0.300
0.610
0.012
0.024
TSOT-23-6 Surface Mount Package
Richtek Technology Corporation
14F, No. 8, Tai Yuen 1st Street, Chupei City
Hsinchu, Taiwan, R.O.C.
Tel: (8863)5526789
Richtek products are sold by description only. Richtek reserves the right to change the circuitry and/or specifications without notice at any time. Customers should
obtain the latest relevant information and data sheets before placing orders and should verify that such information is current and complete. Richtek cannot assume
responsibility for use of any circuitry other than circuitry entirely embodied in a Richtek product. Information furnished by Richtek is believed to be accurate and reliable.
However, no responsibility is assumed by Richtek or its subsidiaries for its use; nor for any infringements of patents or other rights of third parties which may result
from its use. No license is granted by implication or otherwise under any patent or patent rights of Richtek or its subsidiaries.
Copyright © 2015 Richtek Technology Corporation. All rights reserved.
www.richtek.com
16
is a registered trademark of Richtek Technology Corporation.
DS8096D-01
October
2015