16-Bit, 1600 MSPS, TxDAC+ Digital-toAnalog Converter AD9139 Data Sheet FEATURES GENERAL DESCRIPTION Selectable 1× or 2× interpolation filter Support input signal bandwidth up to 575 MHz Very small inherent latency variation: <2 DAC clock cycles Proprietary low spurious and distortion design 6-carrier GSM ACLR = 79 dBc at 200 MHz IF SFDR >85 dBc (bandwidth = 300 MHz) at zero IF Flexible 16-bit LVDS interface Supports word and byte load Multiple chip synchronization Fixed latency and data generator latency compensation FIFO eases system timing and includes error detection High performance, low noise PLL clock multiplier Digital inverse sinc filter Low power: 700 mW at 1230 MSPS 72-lead LFCSP The AD9139 is an 16-bit, high dynamic range digital-to-analog converter (DAC) that provides a sample rate of 1600 MSPS, permitting a multicarrier generation up to the Nyquist frequency. The AD9139 TxDAC+® includes features optimized for wideband communication applications, including 1× and 2× interpolation, a delay locked loop (DLL) powered high speed interface, sample error detection, and parity detection. A 3-wire serial port interface provides for the programming/readback of many internal parameters. A full-scale output current can be programmed over a range of 9 mA up to 33 mA. The AD9139 is available in a 72-lead LFCSP. PRODUCT HIGHLIGHTS 1. 2. APPLICATIONS Wireless communications: 3G/4G and MC-GSM base stations, wideband repeaters, software defined radios Wideband communications: point-to-point, LMDS/MMDS Transmit diversity/MIMO Instrumentation Automated test equipment 3. 4. 575 MHz achievable input signal bandwidth. Advanced low spurious and distortion design techniques provide high quality synthesis of wideband signals from baseband to high intermediate frequencies. Very small inherent latency variation simplifies both software and hardware design in the system. It allows easy multichip synchronization for most applications. Low power architecture improves power efficiency. FUNCTIONAL BLOCK DIAGRAM DLL 13-TAP DCIP/DCIN AD9139 16 HB1 2× DACOUTP DACOUTN DAC_CLK GAIN 1 INTERP MODE CTRL FIFO CTRL SED CTRL INTERFACE CTRL FRAMEP/PARITYP FRAMEN/PARITYN DAC 1 16-BIT DC OFFSET CONTROL GAIN CONTROL INV SINC FIFO 8-SAMPLE SED D0P/D0N LVDS DATA RECEIVER D15P/D15N 10 REF AND BIAS VREF FSADJ INTERNAL CLOCK TIMING AND CONTROL LOGIC PROGRAMMING REGISTERS SERIAL INPUT/OUTPUT PORT POWER-ON RESET MULTICHIP SYNCHRONIZATION DAC_CLK CLOCK MULTIPLIER DACCLKP DACCLKN REF RCVR REFP/SYNCP REFN/SYNCN 11744-001 IRQ2 RESET TXEN IRQ1 CS SCLK SDIO SYNC CLK RCVR Figure 1. Rev. A Document Feedback Information furnished by Analog Devices is believed to be accurate and reliable. However, no responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other rights of third parties that may result from its use. Specifications subject to change without notice. No license is granted by implication or otherwise under any patent or patent rights of Analog Devices. Trademarks and registered trademarks are the property of their respective owners. One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A. Tel: 781.329.4700 ©2013–2014 Analog Devices, Inc. All rights reserved. Technical Support www.analog.com AD9139 Data Sheet TABLE OF CONTENTS Features .............................................................................................. 1 Multidevice Synchronization and Fixed Latency ....................... 29 Applications ....................................................................................... 1 Very Small Inherent Latency Variation ................................... 29 General Description ......................................................................... 1 Further Reducing the Latency Variation................................. 29 Product Highlights ........................................................................... 1 Synchronization Implementation ............................................ 29 Functional Block Diagram .............................................................. 1 Synchronization Procedures ..................................................... 30 Revision History ............................................................................... 3 Interrupt Request Operation ........................................................ 32 Specifications..................................................................................... 4 Interrupt Working Mechanism ................................................ 32 DC Specifications ......................................................................... 4 Interrupt Service Routine .......................................................... 32 Digital Specifications ................................................................... 5 Temperature Sensor ....................................................................... 33 Latency Variation Specifications ................................................ 6 DAC Input Clock Configurations ................................................ 34 AC Specifications.......................................................................... 6 Driving the DACCLK and REFCLK Inputs ........................... 34 Operating Speed Specifications .................................................. 6 Direct Clocking .......................................................................... 34 Absolute Maximum Ratings ....................................................... 7 Clock Multiplication .................................................................. 34 Thermal Resistance ...................................................................... 7 PLL Settings ................................................................................ 35 ESD Caution .................................................................................. 7 Configuring the VCO Tuning Band ........................................ 35 Pin Configuration and Function Descriptions ............................. 8 Automatic VCO Band Select .................................................... 35 Typical Performance Characteristics ........................................... 11 Manual VCO Band Select ......................................................... 35 Terminology .................................................................................... 15 PLL Enable Sequence ................................................................. 35 Serial Port Operation ..................................................................... 16 Analog Outputs............................................................................... 36 Data Format ................................................................................ 16 Transmit DAC Operation.......................................................... 36 Serial Port Pin Descriptions ...................................................... 16 Interfacing to Modulators ......................................................... 37 Serial Port Options ..................................................................... 16 Reducing LO Leakage and Unwanted Sidebands .................. 38 Data Interface .................................................................................. 18 Start-Up Routine ............................................................................ 39 LVDS Input Data Ports .............................................................. 18 Device Configuration Register Map and Description ............... 40 Word Interface Mode ................................................................. 18 SPI Configure Register .............................................................. 42 Byte Interface Mode ................................................................... 18 Power-Down Control Register ................................................. 42 Data Interface Configuration Options .................................... 18 Interrupt Enable 0 Register ....................................................... 42 DLL Interface Mode ................................................................... 18 Interrupt Enable 1 Register ....................................................... 42 Parity ............................................................................................ 21 Interrupt Flag 0 Register............................................................ 43 SED Operation ............................................................................ 21 Interrupt Flag 1 Register............................................................ 43 SED Example ............................................................................... 22 Interrupt Select 0 Register ......................................................... 43 Delay Line Interface Mode ........................................................ 22 Interrupt Select 1 Register ......................................................... 44 FIFO Operation .............................................................................. 24 Frame Mode Register ................................................................. 44 Resetting the FIFO ..................................................................... 25 Data Control 0 Register ............................................................. 44 Serial Port Initiated FIFO Reset ............................................... 25 Data Control 1 Register ............................................................. 44 Frame Initiated FIFO Reset ....................................................... 25 Data Control 2 Register ............................................................. 45 Digital Datapath.............................................................................. 27 Data Control 3 Register ............................................................. 45 Interpolation Filters ................................................................... 27 Data Status 0 Register ................................................................ 45 Inverse Sinc Filter ....................................................................... 28 DAC Clock Receiver Control Register .................................... 46 Digital Function Configuration................................................ 28 Reference Clock Receiver Control Register ............................ 46 Rev. A | Page 2 of 56 Data Sheet AD9139 PLL Control Register ..................................................................46 Gain Step Control0 Register ...................................................... 52 PLL Control Register ..................................................................47 Gain Step Control1 Register ...................................................... 52 PLL Control Register ..................................................................47 TX Enable Control Register ...................................................... 52 PLL Status Register .....................................................................47 DAC Output Control Register .................................................. 53 PLL Status Register .....................................................................48 DLL Cell Enable 0 Register ........................................................ 53 DAC FS Adjust LSB Register .....................................................48 DLL Cell Enable 1 Register ........................................................ 53 DAC FS Adjust MSB Register ....................................................48 SED Control Register ................................................................. 53 Die Temperature Sensor Control Register ...............................48 SED Pattern S0 Low Bits Register ............................................. 54 Die Temperature LSB Register ..................................................48 SED Pattern S0 High Bits Register ............................................ 54 Die Temperature MSB Register .................................................49 SED Pattern S1 Low Bits Register ............................................. 54 Chip ID Register..........................................................................49 SED Pattern S1 High Bits Register ............................................ 54 Interrupt Configuration Register ..............................................49 SED Pattern S2 Low Bits Register ............................................. 54 Sync CTRL Register ....................................................................49 SED Pattern S2 High Bits Register ............................................ 54 Frame Reset CTRL Register .......................................................49 SED Pattern S3 Low Bits Register ............................................. 54 FIFO Level Configuration Register ..........................................50 SED Pattern S3 High Bits Register ............................................ 55 FIFO Level Readback Register ..................................................50 Parity Control Register ............................................................... 55 FIFO CTRL Register ...................................................................50 Parity Error Rising Edge Register ............................................. 55 Data Format Select Register.......................................................51 Parity Error Falling Edge Register ............................................ 55 Datapath Control Register .........................................................51 Version Register .......................................................................... 55 Interpolation Control Register ..................................................51 Packaging and Ordering Information .......................................... 56 Power-Down Data Input 0 Register..........................................51 Outline Dimensions ................................................................... 56 DAC_DC_OFFSET0 Register ...................................................51 Ordering Guide ........................................................................... 56 DAC_DC_OFFSET1 Register ...................................................51 DAC_GAIN_ADJ Register ........................................................52 REVISION HISTORY 3/14—Rev. 0 to Rev. A Change to Register 0x7F, Table 21.................................................41 Change to Table 80 ..........................................................................55 10/13—Revision 0: Initial Version Rev. A | Page 3 of 56 AD9139 Data Sheet SPECIFICATIONS DC SPECIFICATIONS TMIN to TMAX, AVDD33 = 3.3 V, DVDD18 = 1.8 V, CVDD18 = 1.8 V, IOUTFS = 20 mA, maximum sample rate, unless otherwise noted. Table 1. Parameter RESOLUTION ACCURACY Differential Nonlinearity (DNL) Integral Nonlinearity (INL) MAIN DAC OUTPUT Offset Error Gain Error Full-Scale Output Current Output Compliance Range Output Resistance Gain DAC Monotonicity Settling Time to Within ±0.5 LSB MAIN DAC TEMPERATURE DRIFT Offset Gain Reference Voltage REFERENCE Internal Reference Voltage Output Resistance ANALOG SUPPLY VOLTAGES AVDD33 CVDD18 DIGITAL SUPPLY VOLTAGES DVDD18 DVDD18 Variation over Operating Conditions 1 POWER CONSUMPTION 1× Mode 2× Mode Phase-Locked Loop Inverse Sinc Reduced Power Mode (Power-Down) AVDD33 Current CVDD18 Current DVDD18 Current OPERATING RANGE 1 Test Conditions/Comments Min Typ 16 Max ±2.1 ±3.7 With internal reference 10 kΩ external resistor between FSADJ and AVSS −0.001 −3.2 19.06 −1.0 0 +2 19.8 LSB LSB +0.001 +4.7 20.6 +1.0 10 Guaranteed 20 % FSR % FSR mA V MΩ ns 0.04 100 30 1.17 Unit Bits ppm/°C ppm/°C ppm/°C 1.19 V kΩ 5 3.13 1.7 3.3 1.8 3.47 1.9 V V 1.7 −2.5% 1.8 1.9 +2.5% V V 57.3 0.4 26.6 4.5 +85 mW mW mW mW mW mW mW mA mA mA °C fDAC = 614 MSPS fDAC = 1230 MSPS fDAC = 800 MSPS fDAC = 1600 MSPS 440 700 670 1150 70 60 fDAC = 1230 MSPS −40 +25 This parameter specifies the maximum allowable variation of DVDD18 over operating conditions compared with the DVDD18 presented to the device at the time the data interface DLL is enabled. Rev. A | Page 4 of 56 Data Sheet AD9139 DIGITAL SPECIFICATIONS TMIN to TMAX, AVDD33 = 3.3 V, DVDD18 = 1.8 V, CVDD18 = 1.8 V, IOUTFS = 20 mA, maximum sample rate, unless otherwise noted. Table 2. Parameter CMOS INPUT LOGIC LEVEL Input Logic High Logic Low CMOS OUTPUT LOGIC LEVEL Output Logic High Logic Low LVDS RECEIVER INPUTS Input Voltage Range Input Differential Threshold Input Differential Hysteresis Receiver Differential Input Impedance DLL SPEED RANGE DAC UPDATE RATE DAC Adjusted Update Rate DAC CLOCK INPUT (DACCLKP, DACCLKN) Differential Peak-to-Peak Voltage Common-Mode Voltage REFCLK/SYNCCLK INPUT (REFP/SYNCP, REFN/SYNCN) Differential Peak-to-Peak Voltage Common-Mode Voltage Input Clock Frequency SERIAL PORT INTERFACE Maximum Clock Rate Minimum Pulse Width High Low SDIO to SCLK Setup Time SDIO to SCLK Hold Time CS to SCLK Setup Time CS to SCLK Hold Time SDIO to SCLK Delay Symbol Min DVDD18 = 1.8 V DVDD18 = 1.8 V 1.2 DVDD18 = 1.8 V DVDD18 = 1.8 V Data and frame inputs 1.4 VIA or VIB VIDTH VIDTHH to VIDTHL RIN Typ 825 −175 0.6 V V 0.4 V V 575 1600 1150 800 500 1.25 2000 mV V 100 500 1.25 2000 mV V MHz 1.03 GHz ≤ fVCO ≤ 2.07 GHz SCLK 450 40 MHz 12.5 12.5 Wait time for valid output from SDIO Time for SDIO to relinquish the output bus 1.5 0.68 2.38 9.6 11 Rev. A | Page 5 of 56 1.4 8.5 1.2 With 2 mA loading With 2 mA loading mV mV mV Ω MHz MSPS MSPS MSPS 100 Self biased input, ac-coupled VIH VIL IIH IIL Unit 20 100 1× interpolation 2× interpolation tPWH tPWL tDS tDH tDCSB tDCSB tDV Max 1675 +175 250 SDIO High-Z to CS SDIO LOGIC LEVEL Voltage Input High Voltage Input Low Voltage Output High Voltage Output Low Test Conditions/Comments 1.36 0 ns ns ns ns ns ns ns ns 1.8 0 0.5 2 0.45 V V V V AD9139 Data Sheet LATENCY VARIATION SPECIFICATIONS Table 3. Parameter DAC LATENCY 1 VARIATION SYNC Off SYNC On 1 Min Typ Max Unit 1 0 2 1 DAC clock cycles DAC clock cycles DAC latency is defined as the elapsed time from a data sample clocked at the input to the device until the analog output begins to change. AC SPECIFICATIONS TMIN to TMAX, AVDD33 = 3.3 V, DVDD18 = 1.8 V, CVDD18 = 1.8 V, IOUTFS = 20 mA, maximum sample rate, unless otherwise noted. Table 4. Parameter SPURIOUS-FREE DYNAMIC RANGE (SFDR) fDAC = 737.28 MSPS Bandwidth (BW) = 125 MHz BW = 270 MHz fDAC = 983.04 MSPS BW = 360 MHz fDAC = 1228.8 MSPS BW = 200 MHz BW = 500 MHz TWO-TONE INTERMODULATION DISTORTION (IMD) fDAC = 737.28 MSPS fDAC = 983.04 MSPS fDAC = 1228.8 MSPS NOISE SPECTRAL DENSITY (NSD) fDAC = 737.28 MSPS fDAC = 983.04 MSPS fDAC = 1228.8 MSPS W-CDMA ADJACENT CHANNEL LEAKAGE RATIO (ACLR) fDAC = 983.04 MSPS fDAC = 1228.8 MSPS W-CDMA SECOND (ACLR) fDAC = 983.04 MSPS fDAC = 1228.8 MSPS Test Conditions/Comments −14 dBFS single tone fOUT = 200 MHz Min Typ Max Unit 85 80 dBc dBc 85 dBc 85 75 dBc dBc 80 82 80 dBc dBc dBc −160 −161.5 −164.5 dBm/Hz dBm/Hz dBm/Hz 81 83 80 dBc dBc dBc 85 86 86 dBc dBc dBc fOUT = 200 MHz fOUT = 280 MHz −12 dBFS each tone fOUT = 200 MHz fOUT = 200 MHz fOUT = 280 MHz Eight-tone, 500 kHz tone spacing fOUT = 200 MHz fOUT = 200 MHz fOUT = 280 MHz Single carrier fOUT = 200 MHz fOUT = 20 MHz fOUT = 280 MHz Single carrier fOUT = 200 MHz fOUT = 20 MHz fOUT = 280 MHz OPERATING SPEED SPECIFICATIONS Table 5. Interpolation Factor 1× 2× DVDD18, CVDD18 = 1.8 V ± 5% fDCI (MSPS) Max fDAC (MSPS) Max 575 1150 350 1400 DVDD18, CVDD18 = 1.9 V ± 5% or 1.8 V ± 2% fDCI (MSPS) Max fDAC (MSPS) Max 575 1150 375 1500 Rev. A | Page 6 of 56 DVDD18, CVDD18 = 1.9 V ± 2% fDCI (MSPS) Max fDAC (MSPS) Max 575 1150 400 1600 Data Sheet AD9139 ABSOLUTE MAXIMUM RATINGS THERMAL RESISTANCE Table 6. Parameter AVDD33 to GND DVDD18, CVDD18 to GND FSADJ, VREF, DACOUTP/DACOUTN, to GND D15P to D0P/D15N to D0N, FRAMEP/FRAMEN, DCIP/DCIN to GND DACCLKP/DACCLKN, REFP/SYNCP/REFN/SYNCN to GND RESET, IRQ1, IRQ2, CS, SCLK, SDIO to GND Junction Temperature Storage Temperature Range Rating −0.3 V to +3.6 V −0.3 V to +2.1 V −0.3 V to AVDD33 + 0.3 V −0.3 V to DVDD18 + 0.3 V −0.3 V to CVDD18 + 0.3 V The exposed pad (EPAD) must be soldered to the ground plane (AVSS) for the 72-lead LFCSP. The EPAD provides an electrical, thermal, and mechanical connection to the board. Typical θJA, θJB, and θJC values are specified for a 4-layer board in still air. Airflow increases heat dissipation, effectively reducing θJA and θJB. Table 7. Thermal Resistance −0.3 V to DVDD18 + 0.3 V Package 72-Lead LFCSP 125°C −65°C to +150°C ESD CAUTION Stresses above those listed under Absolute Maximum Ratings may cause permanent damage to the device. This is a stress rating only; functional operation of the device at these or any other conditions above those indicated in the operational section of this specification is not implied. Exposure to absolute maximum rating conditions for extended periods may affect device reliability. Rev. A | Page 7 of 56 θJA 20.7 θJB 10.9 θJC 1.1 Unit °C/W Conditions EPAD soldered to ground plane AD9139 Data Sheet 72 71 70 69 68 67 66 65 64 63 62 61 60 59 58 57 56 55 CVDD18 CVDD18 VREF FSADJ AVDD33 DACOUTP DACOUTN AVDD33 CVDD18 CVDD18 DACCLKP DACCLKN CVDD18 CVDD18 AVDD33 DNC DNC AVDD33 PIN CONFIGURATION AND FUNCTION DESCRIPTIONS 1 2 3 4 5 6 7 8 9 10 11 12 13 14 15 16 17 18 AD9139 TOP VIEW 54 53 52 51 50 49 48 47 46 45 44 43 42 41 40 39 38 37 CS SCLK SDIO IRQ1 IRQ2 DVDD18 DVDD18 D0N D0P D1N D1P DVDD18 D2N D2P D3N D3P D4N D4P 11744-002 DVDD18 D11P D11N D10P D10N D9P D9N D8P D8N DCIP DCIN D7P D7N D6P D6N D5P D5N DVDD18 19 20 21 22 23 24 25 26 27 28 29 30 31 32 33 34 35 36 CVDD18 REFP/SYNCP REFN/SYNCN CVDD18 RESET TXEN DVDD18 FRAMEP/PARITYP FRAMEN/PARITYN D15P D15N DVDD18 D14P D14N D13P D13N D12P D12N NOTES 1. DNC = DO NOT CONNECT. DO NOT CONNECT TO THIS PIN. 2. THE EXPOSED PAD MUST BE SOLDERED TO THE GROUND PLANE (AVSS, DVSS, CVSS). THE EPAD PROVIDES AN ELECTRICAL, THERMAL, AND MECHANICAL CONNECTION TO THE BOARD. Figure 2. Pin Configuration Table 8. Pin Function Descriptions Pin No. 1 2 3 4 5 6 Mnemonic CVDD18 REFP/SYNCP REFN/SYNCN CVDD18 RESET TXEN 7 DVDD18 8 9 10 11 12 FRAMEP/PARITYP FRAMEN/PARITYN D15P D15N DVDD18 13 14 15 16 17 18 19 D14P D14N D13P D13N D12P D12N DVDD18 20 21 22 23 D11P D11N D10P D10N Description 1.8 V PLL Supply. CVDD18 supplies the power to the clock receivers, clock multiplier, and clock distribution. PLL Reference Clock/Synchronization Clock Input, Positive. PLL Reference Clock/Synchronization Clock Input, Negative. 1.8 V PLL Supply. CVDD18 supplies the power to the clock receivers, clock multiplier, and clock distribution. Reset, Active Low. CMOS levels with respect to DVDD18. Recommended reset pulse length is 1 µs. Active High Transmit Path Enable. CMOS levels with respect to DVDD18. A low level on this pin triggers two selectable actions in the DAC. See Register 0x43 in Table 64 for details. 1.8 V Digital Supply. Pin 7 supplies power to the digital core, digital data ports, serial port input/output pins, RESET, IRQ1, and IRQ2. Frame/Parity Input, Positive. Frame/Parity Input, Negative. Data Bit 15 (MSB), Positive. Data Bit 15 (MSB), Negative. 1.8 V Digital Supply. Pin 12 supplies the power to the digital core and digital data ports, serial port input/output pins, RESET, IRQ1, and IRQ2. Data Bit 14, Positive. Data Bit 14, Negative. Data Bit 13, Positive. Data Bit 13, Negative. Data Bit 12, Positive. Data Bit 12, Negative. 1.8 V Digital Supply. Pin 19 supplies power to the digital core, digital data ports, serial port input/output pins, RESET, IRQ1, and IRQ2. Data Bit 11, Positive. Data Bit 11, Negative. Data Bit 10, Positive. Data Bit 10, Negative. Rev. A | Page 8 of 56 Data Sheet Pin No. 24 25 26 27 28 29 30 31 32 33 34 35 36 Mnemonic D9P D9N D8P D8N DCIP DCIN D7P D7N D6P D6N D5P D5N DVDD18 37 38 39 40 41 42 43 D4P D4N D3P D3N D2P D2N DVDD18 44 45 46 47 48 D1P D1N D0P D0N DVDD18 49 DVDD18 50 IRQ2 51 IRQ1 52 53 54 55 56 57 58 59 60 61 62 63 64 65 66 67 68 69 70 71 SDIO SCLK CS AVDD33 DNC DNC AVDD33 CVDD18 CVDD18 DACCLKN DACCLKP CVDD18 CVDD18 AVDD33 DACOUTN DACOUTP AVDD33 FSADJ VREF CVDD18 AD9139 Description Data Bit 9, Positive. Data Bit 9, Negative. Data Bit 8, Positive. Data Bit 8, Negative. Data Clock Input, Positive. Data Clock Input, Negative. Data Bit 7, Positive. Data Bit 7, Negative. Data Bit 6, Positive. Data Bit 6, Negative. Data Bit 5, Positive. Data Bit 5, Negative. 1.8 V Digital Supply. Pin 36 supplies the power to the digital core, digital data ports, serial port input/output pins, RESET, IRQ1, and IRQ2. Data Bit 4, Positive. Data Bit 4, Negative. Data Bit 3, Positive. Data Bit 3, Negative. Data Bit 2, Positive. Data Bit 2, Negative. 1.8 V Digital Supply. Pin 43 supplies the power to the digital core, digital data ports, serial port input/output pins, RESET, IRQ1, and IRQ2. Data Bit 1, Positive. Data Bit 1, Negative. Data Bit 0, Positive. Data Bit 0, Negative. 1.8 V Digital Supply. Pin 48 supplies the power to the digital core, digital data ports, serial port input/output pins, RESET, IRQ1, and IRQ2. 1.8 V Digital Supply. Pin 49 supplies the power to the digital core, digital data ports, serial port input/output pins, RESET, IRQ1, and IRQ2. Second Interrupt Request. Open-drain, active low output. Connect an external pull-up to DVDD18 through a 10 kΩ resistor. First Interrupt Request. Open-drain, active low output. Connect an external pull-up to DVDD18 through a 10 kΩ resistor. Serial Port Data Input/Output. CMOS levels with respect to DVDD18. Serial Port Clock Input. CMOS levels with respect to DVDD18. Serial Port Chip Select. Active low (CMOS levels with respect to DVDD18). 3.3 V Analog Supply. Do No Connect. Leave this pin floating. Do No Connect. Leave this pin floating. 3.3 V Analog Supply. 1.8 V Clock Supply. CVDD18 supplies the power to the clock receivers and clock distribution. 1.8 V Clock Supply. CVDD18 supplies the power to the clock receivers and clock distribution. DAC Clock Input, Negative. DAC Clock Input, Positive. 1.8 V Clock Supply. CVDD18 supplies the power to the clock receivers and clock distribution. 1.8 V Clock Supply. CVDD18 supplies the power to the clock receivers and clock distribution. 3.3 V Analog Supply. DAC Current Output, Negative. DAC Current Output, Positive. 3.3 V Analog Supply. Full-Scale Current Output Adjust. Place a 10 kΩ resistor from this pin to AVSS. Voltage Reference. Nominally 1.2 V output. Decouple VREF to AVSS. 1.8 V Clock Supply. Pin 71 supplies power to the clock receivers, clock multiplier, and clock distribution. Rev. A | Page 9 of 56 AD9139 Pin No. 72 Mnemonic CVDD18 EPAD Data Sheet Description 1.8 V Clock Supply. Pin 72 supplies power to the clock receivers, clock multiplier, and clock distribution. Exposed Pad. The exposed pad (EPAD) must be soldered to the ground plane (AVSS, DVSS, CVSS). The EPAD provides an electrical, thermal, and mechanical connection to the board. Rev. A | Page 10 of 56 Data Sheet AD9139 TYPICAL PERFORMANCE CHARACTERISTICS –40 –40 fDAC = 737.28MHz fDAC = 983.04MHz fDAC = 1228.8MHz –50 –70 –80 –80 –90 –90 –100 0 100 200 300 400 500 600 700 fOUT (MHz) –100 Figure 3. Single-Tone (0 dBFS) SFDR vs. fOUT in the First Nyquist Zone over fDAC 0 100 150 200 250 300 350 400 fOUT (MHz) Figure 6. Single-Tone SFDR Excluding 2nd and 3rd Harmonics vs. fOUT in the First Nyquist Zone over fDAC and Digital Back Off –40 –40 0dBFS –6dBFS –12dBFS –16dBFS –50 fDAC = 737.28MHz fDAC = 983.04MHz fDAC = 1228.8MHz –50 –60 –70 –70 –80 –80 –90 –90 100 200 300 400 500 600 700 fOUT (MHz) –100 11744-004 0 0 100 200 300 400 500 600 700 fOUT (MHz) Figure 4. Single-Tone Second Harmonic vs. fOUT in the First Nyquist Zone over Digital Back Off, fDAC = 1228.8 MHz 11744-008 IMD (dBc) –60 –100 Figure 7. Two-Tone Third IMD vs. fOUT over fDAC –40 –40 0dBFS –6dBFS –12dBFS –16dBFS –50 0dBFS –6dBFS –12dBFS –16dBFS –50 –60 –70 –70 –80 –80 –90 –90 –100 0 100 200 300 400 fOUT (MHz) 500 600 700 Figure 5. Single-Tone Third Harmonic vs. fOUT in the First Nyquist Zone over Digital Back Off, fDAC = 1228.8 MHz Rev. A | Page 11 of 56 –100 0 100 200 300 400 500 600 fOUT (MHz) Figure 8. Two-Tone Third IMD vs. fOUT over Digital Back Off, fDAC = 1228.8 MHz 700 11744-009 IMD (dBc) –60 11744-005 THIRD HARMONIC (dBc) 50 11744-006 SFDR (dBc) –70 11744-003 SFDR (dBc) 0dBFS –12dBFS –60 –60 SECOND HARMONIC (dBc) fDAC = 800MHz fDAC = 1600MHz –50 AD9139 Data Sheet –40 –150 PLL OFF PLL ON 0dBFS –12 dBFS PLL OFF PLL ON –50 –155 NSD (dBm/Hz) IMD (dBc) –60 –70 –160 –80 –165 0 100 200 300 400 500 600 700 fOUT (MHz) Figure 9. Two-Tone Third IMD vs. fOUT over PLL on and off, fDAC = 1228.8 MHz –145 –170 11744-010 –100 0 100 200 400 300 500 600 700 fOUT (MHz) 11744-013 –90 Figure 12. Single-Tone NSD vs. fOUT, over Digital Back Off, PLL on and off –60 fDAC = 737.28MHz fDAC = 983.04MHz fDAC = 1228.8MHz fDAC = 1228.8MHz fDAC = 983.04MHz –65 –150 PLL OFF PLL ON ACLR (dBc) NSD (dBm/Hz) –70 –155 –160 –75 –80 –165 0 100 200 300 400 500 600 700 fOUT (MHz) –90 11744-011 –170 0 100 200 300 400 500 600 fOUT (MHz) 11744-014 –85 Figure 13. 1-Carrier WCDMA 1st Adjacent ACLR vs. fOUT over fDAC PLL on and off Figure 10. Single-Tone (0 dBFS) NSD vs. fOUT over fDAC –150 0dBFS –6dBFS –12dBFS –16dBFS –60 PLL OFF PLL ON –70 ACLR (dBc) NSD (dBm/Hz) fDAC = 1228.8MHz fDAC = 983.04MHz –65 –155 –160 –75 –80 –165 100 200 300 400 fOUT (MHz) 500 600 700 –90 0 100 200 300 400 500 600 fOUT (MHz) Figure 11. Single-Tone NSD vs. fOUT, over Digital Back Off, fDAC = 1228.8 MHz Rev. A | Page 12 of 56 Figure 14. 1-Carrier WCDMA 2nd Adjacent ACLR vs. fOUT over fDAC PLL on and off 11744-015 0 11744-012 –85 –170 AD9139 11744-017 11744-023 Data Sheet Figure 15. Two-Tone Third IMD Performance, IF = 200 MHz, fDAC = 1228.8 MHz, −9 dBFS Figure 18. 4-Carrier WCDMA ACLR Performance, IF = 200 MHz, fDAC = 1228.8 MHz 1.0 1× INTERPOLATION 2× INTERPOLATION 0.9 POWER (W) 0.8 0.7 0.6 0.5 0.4 0.2 200 400 600 11744-019 0 800 1000 1200 1400 fDAC (MHz) 11744-024 0.3 Figure 19. Total Power Consumption vs. fDAC over Interpolation Figure 16. 1-Carrier WCDMA ACLR Performance, IF = 200 MHz, fDAC = 1228.8 MHz 350 1× INTERPOLATION 2× INTERPOLATION DVDD18 CURRENT (mA) 300 250 200 150 100 0 11744-021 0 Figure 17. Single-Tone Performance, IF = 200 MH, fDAC = 1228.8 MHz Rev. A | Page 13 of 56 200 400 600 800 1000 1200 fDAC (MHz) Figure 20. DVDD18 Current vs. fDAC over Interpolation 1400 11744-025 50 AD9139 Data Sheet 35 250 AVDD33 (mA) CVDD18 (mA), PLL OFF CVDD18 (mA), PLL ON DIGITAL GAIN AND OFFSET INVERSE SINC 30 SUPPLY CURRENT (mA) 25 20 15 10 150 100 50 0 0 200 400 600 800 1000 1200 1400 fDAC (MHz) Figure 21. DVDD18 Current vs. fDAC over Digital Functions 0 0 200 400 600 800 1000 1200 fDAC (MHz) Figure 22. CVDD18 and AVDD18 Current vs. fDAC Rev. A | Page 14 of 56 1400 11744-027 5 11744-026 DVDD18 CURRENT (mA) 200 Data Sheet AD9139 TERMINOLOGY Integral Nonlinearity (INL) INL is the maximum deviation of the actual analog output from the ideal output, determined by a straight line drawn from zero scale to full scale. Settling Time Settling time is the time required for the output to reach and remain within a specified error band around its final value, measured from the start of the output transition. Differential Nonlinearity (DNL) DNL is the measure of the variation in analog value, normalized to full scale, associated with a 1 LSB change in digital input code. Spurious Free Dynamic Range (SFDR) SFDR is the difference, in decibels, between the peak amplitude of the output signal and the peak spurious signal within the dc to Nyquist frequency of the DAC. Typically, the interpolation filters reject energy in this band. This specification, therefore, defines how well the interpolation filters work and the effect of other parasitic coupling paths on the DAC output. Offset Error Offset error is the deviation of the output current from the ideal of 0 mA. For DACOUTP, 0 mA output is expected when all inputs are set to 0. For DACOUTN, 0 mA output is expected when all inputs are set to 1. Gain Error Gain error is the difference between the actual and ideal output span. The actual span is determined by the difference between the output when all inputs are set to 1 and the output when all inputs are set to 0. Output Compliance Range The output compliance range is the range of allowable voltage at the output of a current output DAC. Operation beyond the maximum compliance limits can cause either output stage saturation or breakdown, resulting in nonlinear performance. Temperature Drift Temperature drift is specified as the maximum change from the ambient (25°C) value to the value at either TMIN or TMAX. For offset and gain drift, the drift is reported in ppm of fullscale range (FSR) per degree Celsius. For reference drift, the drift is reported in ppm per degree Celsius. Power Supply Rejection (PSR) PSR is the maximum change in the full-scale output as the supplies are varied from minimum to maximum specified voltages. Signal-to-Noise Ratio (SNR) SNR is the ratio of the rms value of the measured output signal to the rms sum of all other spectral components below the Nyquist frequency, excluding the first six harmonics and dc. The value for SNR is expressed in decibels. Interpolation Filter If the digital inputs to the DAC are sampled at a multiple rate of fDATA (interpolation rate), a digital filter can be constructed that has a sharp transition band near fDATA/2. Images that typically appear around fDAC (output data rate) can be greatly suppressed. Adjacent Channel Leakage Ratio (ACLR) ACLR is the ratio in decibels relative to the carrier (dBc) between the measured power within a channel relative to its adjacent channel. Complex Image Rejection In a traditional two-part upconversion, two images are created around the second IF frequency. These images have the effect of wasting transmitter power and system bandwidth. By placing the real part of a second complex modulator in series with the first complex modulator, either the upper or lower frequency image near the second IF can be rejected. Rev. A | Page 15 of 56 AD9139 Data Sheet SERIAL PORT OPERATION 54 CS SPI PORT 53 SCLK 52 SDIO 11744-028 The serial port is a flexible, synchronous serial communications port that allows easy interfacing to many industry standard microcontrollers and microprocessors. The serial I/O is compatible with most synchronous transfer formats, including both the Motorola SPI and Intel® SSR protocols. The interface allows read/write access to all registers that configure the AD9139. MSB first or LSB first transfer formats are supported. The serial port interface is a 3-wire only interface. The input and output share a single input/output (SDIO) pin. SERIAL PORT PIN DESCRIPTIONS Serial Clock (SCLK) The serial clock pin, SCLK, synchronizes data to and from the device and runs the internal state machines. The maximum frequency of SCLK is 40 MHz. All data input is read on the rising edge of SCLK. All data is driven out on the falling edge of SCLK. Chip Select (CS) Figure 23. Serial Port Interface Pins There are two phases to a communication cycle with the AD9139. Phase 1 is the instruction cycle (the writing of an instruction byte into the device), coincident with the first 16 SCLK rising edges. The instruction word provides the serial port controller with information regarding the data transfer cycle, Phase 2, of the communication cycle. The Phase 1 instruction word defines whether the upcoming data transfer is a read or write, together with the starting register address for the following data transfer. A logic high on the CS pin, followed by a logic low, resets the serial port timing to the initial state of the instruction cycle. From this state, the next 16 rising SCLK edges represent the instruction bits of the current I/O operation. The remaining SCLK edges are for Phase 2 of the communication cycle. Phase 2 is the actual data transfer between the device and the system controller. Phase 2 of the communication cycle is a transfer of one data byte. Registers change immediately upon writing to the last bit of each transfer byte. DATA FORMAT The instruction byte contains the information shown in Table 9. Table 9. Serial Port Instruction Word I15 (MSB) R/W A14 to A0 (Bit 14 to Bit 0 of the instruction word) determine the register that is accessed during the data transfer portion of the communication cycle. For multibyte transfers, A14 is the starting address; the device generates the remaining register addresses based on the SPI_LSB_FIRST bit. I[14:0] A[14:0] R/W (Bit 15 of the instruction word) determines whether a read or a write data transfer occurs after the instruction word write. Logic 1 indicates a read operation, and Logic 0 indicates a write operation. CS is an active low input that starts and gates a communication cycle. It allows the use of multiple devices on the same serial communications line. The SDIO pin enters a high impedance state when the CS input is high. During the communication cycle, CS remains low. Serial Data I/O (SDIO) The SDIO pin is a bidirectional data line. SERIAL PORT OPTIONS The serial port supports both MSB first and LSB first data formats; the SPI_LSB_FIRST bit (Register 0x00, Bit 6) controls this functionality. The default is MSB first (SPI_LSB_FIRST = 0). When SPI_LSB_FIRST = 0 (MSB first), the instruction and data bits must be written from MSB to LSB. Multibyte data transfers in MSB first format start with an instruction word that includes the register address of the most significant data byte. Subsequent data bytes must follow from high address to low address. In MSB first mode, the serial port internal word address generator decrements for each data byte of the multibyte communication cycle. When SPI_LSB_FIRST = 1 (LSB first), the instruction and data bits must be written from LSB to MSB. Multibyte data transfers in LSB first format start with an instruction word that includes the register address of the least significant data byte. Subsequent data bytes must follow from low address to high address. In LSB first mode, the serial port internal word address generator increments for each data byte of the multibyte communication cycle. When the MSB first mode is active, the serial port controller data address decrements from the data address written toward 0x00 for multibyte I/O operations. If the LSB first mode is active, the serial port controller data address increments from the data address written toward 0xFF for multibyte I/O operations. Rev. A | Page 16 of 56 Data Sheet AD9139 tDCSB INSTRUCTION CYCLE tSCLK DATA TRANSFER CYCLE CS CS tPWH SCLK R/W A14 A13 A3 A2 A1 A0 D7N D6N D5N D30 D20 D10 D00 tDS SDIO Figure 24. Serial Register Interface Timing, MSB First INSTRUCTION CYCLE tDH INSTRUCTION BIT 15 INSTRUCTION BIT 14 11744-031 SCLK 11744-029 SDIO tPWL Figure 26. Timing Diagram for Serial Port Register Write CS DATA TRANSFER CYCLE CS SCLK A0 A1 A2 A12 A13 A14 R/W D00 D10 D20 D4N D5N D6N D7N tDV SDIO Figure 25. Serial Register Interface Timing, LSB First DATA BIT n DATA BIT n – 1 Figure 27. Timing Diagram for Serial Port Register Read Rev. A | Page 17 of 56 11744-032 SDIO 11744-030 SCLK AD9139 Data Sheet DATA INTERFACE LVDS INPUT DATA PORTS DATA INTERFACE CONFIGURATION OPTIONS The AD9139 has a 16-bit LVDS bus that accepts 16-bit data either in word wide (16-bit) or byte wide (8-bit) formats. In the word wide interface mode, the data is sent over the entire 16-bit data bus. In the byte wide interface mode, the data is sent over the lower 8-bit (D7 to D0) LVDS bus. Table 10 lists the pin assignment of the bus and the SPI register configuration for each mode. To provide more flexibility for the data interface, additional options are listed in Table 11. Table 11. Data Interface Configuration Options Register 0x26, Bit 7 DATA_FORMAT Table 10. LVDS Input Data Modes Interface Mode Word Byte Input Data Width D15 to D0 D7 to D0 DLL INTERFACE MODE A source synchronous LVDS interface is used between the data host and the AD9139 to achieve high data rates while simplifying the interface. The FPGA or ASIC feeds the AD9139 with 16-bit input data. Together with the input data, the FPGA or ASIC provides a DDR DCI. SPI Register Configuration Register 0x26, Bit 0 = 0 Register 0x26, Bit 0 = 1 WORD INTERFACE MODE In word mode, the digital clock input (DCI) signal is a reference bit that generates a double data rate (DDR) data sampling clock. Time align the DCI signal with the data. A delay locked loop (DLL) circuit, designed to operate with DCI clock rates between 250 MHz and 575 MHz, generates a phase shifted version of the DCI signal, called a data sampling clock (DSC), to register the input data on both the rising and falling edges. AD9139 WORD MODE INPUT DATA[15:0] S1 S2 S3 11744-033 S0 DCI Figure 28. AD9139 Timing Diagram for Word Mode BYTE INTERFACE MODE In byte mode, the required sequence of the input data stream is S0[15:8], S0[7:0], S1[15:8], S1[7:0], and so forth. A frame signal is required to align the order of input data bytes properly. Time align both the DCI signal and frame signal with the data. The rising edge of the frame indicates the start of the sequence. The frame can be either a one shot or periodical signal as long as its first rising edge is correctly captured by the device. For a one shot frame, the frame pulse must be held at high for at least one DCI cycle. For a periodical frame, the frequency must be fDCI/(2 × n) Figure 29 is an example of signal timing in byte mode. AD9139 WORD MODE S0[15:8] S0[7:0] S1[15:8] As shown in Figure 31, the DCI clock edges must be coincident with the data bit transitions with minimum skew and jitter. The nominal sampling point of the input data occurs in the middle of the DCI clock edges because this point corresponds to the center of the data eye. This is also equivalent to a nominal phase shift of 90°of the DCI clock. The data timing requirements are defined by a data valid window (DVW) that is dependent on the data clock input skew, input data jitter, and the variations of the DLL delay line across delay settings. The DVW is defined as DVW = tDATA PERIOD − tDATA SKEW − tDATA JITTER The available margin for data interface timing is given by tMARGIN = DVW − (tS + tH) The difference of the setup and hold times, which is also called the keep out window, or KOW, is the area where data transitions are prohibited. The timing margin allows the user to set the DLL delay, as shown in Figure 30. where n is a positive integer, that is, 1, 2, 3, … INPUT DATA[7:0] Description Select between binary and twos complement formats. S1[7:0] 11744-034 DCI FRAME Figure 29. Timing Diagram for Byte Mode Rev. A | Page 18 of 56 Data Sheet AD9139 tH tDATA JITTER tS INPUT DATA DATA EYE tDATA PERIOD DCI DATA SAMPLE CLOCK tH + tS tDCI SKEW DLL PHASE DELAY tDATA JITTER DATA EYE INPUT DATA tDATA PERIOD 11744-035 DCI DATA SAMPLE CLOCK Figure 30. LVDS Data Port Timing Requirements Figure 30 shows that the ideal location for the DSC signal is 90° out of phase from the DCI input; however, due to skew of the DCI relative to the data, it may be necessary to change the DSC phase offset to sample the data at the center of its eye diagram. Vary the sampling instance in discrete increments by offsetting the nominal DLL phase shift value of 90° via Register 0x0A, Bits[3:0]. This register is a signed value. The MSB is the sign and the LSBs are the magnitude. The following equation defines the phase offset relationship: Phase Offset = 90° + n × 11.25°, |n| < 7 where n is the DLL phase offset setting. Figure 31 shows the DSC setup and hold times with respect to the DCI signal and data signals. Table 12 lists the guaranteed values across the operating conditions. These values were obtained using a 50% duty cycle and a DCI swing of 450 mV p-p. For best performance, maintain a duty cycle variation below ±5% and set the DCI input as high as possible, up to 1200 mV p-p. Table 12. DLL Phase Setup and Hold Times (Guaranteed) Frequency, fDCI (MHz) 307 368 491 DATA 614 DCI tS tH 11744-036 DSC Figure 31. LVDS Data Port Setup and Hold Times Rev. A | Page 19 of 56 Time (ps) tS tH tS tH tS tH tS tH Data Port Setup and Hold Times (ps) at DLL Phase −3 0 +3 −125 −385 −695 834 1120 1417 −70 −305 −534 753 967 1207 −81 −245 −402 601 762 928 −54.0 −167 −277 497 603 721 AD9139 Data Sheet Table 13. DLL Phase Setup and Hold Times (Typical) Frequency, fDCI 1 (MHz) 250 275 300 325 350 375 400 425 450 475 500 525 550 575 1 Time (ps) tS tH tS tH tS tH tS tH tS tH tS tH tS tH tS tH tS tH tS tH tS tH tS tH tS tH tS tH Data Port Setup and Hold Times (ps) at DLL Phase −6 −93 468 −87 451 −82 422 −46 405 −23 383 −7 401 −46 385 4 358 11 354 −15 355 9 313 −7 311 −5 300 8 312 −5 −196 579 −172 537 −166 500 −114 483 −92 451 −82 466 −98 445 −52 408 −34 406 −51 399 −28 354 −52 356 −39 340 −28 348 −4 −312 707 −264 646 −256 598 −190 563 −180 524 −150 504 −161 503 −110 465 −92 457 −95 451 −77 399 −100 395 −74 378 −66 379 −3 −416 825 −364 757 −341 703 −271 647 −252 607 −225 569 −243 546 −170 524 −147 516 −147 499 −128 445 −147 438 −107 423 −102 414 −2 −530 947 −464 878 −426 803 −358 740 −328 682 −315 641 −303 604 −229 595 −209 573 −198 556 −183 500 −187 489 −147 468 −143 453 −1 −658 1067 −556 977 −515 897 −447 832 −409 762 −391 718 −384 674 −297 625 −269 637 −255 613 −233 555 −237 537 −192 510 −181 496 0 −770 1188 −653 1092 −622 1000 −538 914 −491 844 −461 783 −448 748 −394 692 −324 693 −313 675 −288 615 −285 592 −249 560 −245 544 +1 −878 1315 −756 1218 −715 1105 −612 1000 −574 930 −526 863 −513 826 −449 762 −386 731 −366 727 −333 668 −335 645 −302 610 −280 599 +2 −983 1442 −859 1311 −809 1203 −706 1100 −654 1011 −595 941 −578 890 −517 829 −446 792 −425 779 −390 726 −387 692 −352 659 −336 654 +3 −1093 1570 −956 1423 −900 1303 −806 1200 −731 1097 −661 1025 −643 965 −579 900 −509 852 −480 815 −438 783 −436 746 −397 710 −366 708 +4 −1193 1697 −1053 1537 −1001 1411 −891 1292 −819 1186 −726 1106 −713 1039 −641 966 −564 917 −530 873 −495 825 −483 799 −440 756 −406 759 +5 −1289 1777 −1151 1653 −1097 1522 −966 1380 −889 1277 −786 1187 −771 1110 −704 1032 −622 983 −585 930 −545 881 −530 850 −486 810 −443 806 +6 −1412 1876 −1251 1728 −1184 1612 −1044 1476 −959 1358 −853 1264 −833 1178 −752 1097 −672 1042 −640 988 −594 934 −581 909 −529 865 −488 847 Table 13 shows characterization data for selected fDCI frequencies. Other frequencies are possible; use Table 13 to estimate performance. Table 13 shows the typical times for various DCI clock frequencies that are required to calculate the data valid margin. Use Table 13 to determine the amount of margin that is available for tuning of the DSC sampling point. Maximizing the opening of the eye in both the DCI and data signals improves the reliability of the data port interface. Use differential controlled impedance traces of equal length (that is, delay) between the host processor and the AD9139 input. To ensure coincident transitions with the data bits, implement the DCI signal as an additional data line with an alternating (010101…) bit sequence from the same output drivers that are used for the data. The DCI signal is ac-coupled by default; thus, removing the DCI signal may cause DAC output chatter due to randomness on the DCI input. To avoid this, disable the DAC output whenever the DCI signal is not present by setting the DAC output current power-down bit in Register 0x01[7] to 1. When the DCI signal is again present, enable the DAC output by programming Register 0x01[7] to 0. Register 0x0D optimizes the DLL stability over the operating frequency range. Table 14 shows the recommended settings. Table 14. DLL Configuration Options DCI Speed ≥350 MHz <350 MHz Register 0x0D 0x06 0x86 Poll the status of the DLL by reading the data status register at Address 0x0E. Bit 0 indicates that the DLL is running and attempting lock; Bit 7 is 1 when the DLL has locked. Bit 2 is 1 when a valid data clock input (DCI) is detected. The warning bits in [6:4] in Register 0x0E can be used as indicators that the DAC may be operating in a nonideal location in the delay line. Note that these bits are read at the SPI port speed, which is much slower than the actual speed of the DLL. This means they can only show a snapshot of what is happening as opposed to giving real-time feedback. Rev. A | Page 20 of 56 Data Sheet AD9139 In the following DLL configuration example, fDCI = 600 MHz, DLL is enabled, and DLL phase offset = 0. 1. 0x5E → 0xFE /* Turn off LSB delay cell*/ 2. 0x0D → 0x06 /* Select DLL configure options */ 3. 0x0A → 0xC0 /* Enable DLL and duty cycle correction. Set DLL phase offset to 0 */ 4. Read 0x0E[7:4] /* Expect 1000b if the DLL is locked */ DLL Configuration Example 2 In the following DLL configuration example, fDCI = 300 MHz, DLL is enable, and DLL phase offset = 0. 1. 0x5E → 0xFE /* Turn off LSB delay cell*/ 2. 0x0D → 0x86 /* Select DLL configure options */ 3. 0x0A → 0xC0 /* Enable DLL and duty cycle correction. Set DLL phase offset to 0 */ 4. Read 0x0E[7:4] /* Expect 1000b if the DLL is locked */ PARITY The data interface can be continuously monitored by enabling the parity bit feature in Register 0x6A[7] and configuring the frame/parity bit as parity by setting Register 0x09 = 0x21. In this case, the host sends a parity bit with each data sample. This bit is set according to the following formulas, where n is the data sample that is being checked: For even parity, XOR[FRM(n), D0(n), D1(n), D2(n), …, D15(n)] = 0 For odd parity, XOR[FRM(n), D0(n), D1(n), D2(n), …, D15(n)] = 1 The parity bit is calculated over 17 bits (including the frame/parity bit). If a parity error occurs, the parity error counter (Register 0x6B or Register 0x6C) increments. Parity errors on the bits sampled by the rising edge of the DCI signal increment the rising edge parity counter (Register 0x6B) and set the PARERRRIS bit (Register 0x6A[0]). Parity errors on the bits sampled by the falling edge of DCI increment the falling edge parity counter (Register 0x6C) and set the PARERRFAL bit (Register 0x6A[1]). The parity counter continues to accumulate until it clears or until it reaches a maximum value of 255. To clear the count, write a 1 to Register 0x6A[5]. To trigger an IRQ when a parity error occurs, write 1 to Bit 7 in Register 0x04. This IRQ triggers when there is either a rising edge or falling edge parity error. Observe the status of the IRQ pin via Register 0x06[7] or by using the selected IRQx pin. Clear the IRQ by writing a 1 to Register 0x06[7]. Use the parity bit feature to validate the interface timing. As described previously, the host provides a parity bit with the data samples, as well as configures the AD9139 to generate an IRQ. The user can then sweep the sampling instance of the input registers of the AD9139 to determine at what point sampling errors occur. The sampling instance can be varied in discrete increments by offsetting the nominal DLL phase shift value of 90° via SPI Register 0x0A[3:0]. SED OPERATION The AD9139 provides on-chip sample error detection (SED) circuitry that simplifies verification of the input data interface. The SED compares the input data samples captured at the digital input pins with a set of comparison values. The comparison values are loaded into registers through the SPI port. Differences between the captured values and the comparison values are detected. Options are available for customizing SED test sequencing and error handling. The SED circuitry allows the application to test a short user defined pattern to confirm that the high speed source synchronous data bus is correctly implemented and meets the timing requirement. Unlike the parity bit, the SED circuitry is expected to be used during initial system calibration, before the AD9139 is in use in the application. The SED circuitry operates on a data set made up of user defined input words, denoted as S0, S1, S2, and S3. The user defined pattern consists of sequential data-word samples (S0 is sampled on the rising edge of DCI, S1 is sampled on the following falling edge of DCI, S2 is sampled on the following DCI rising edge, and S3 is sampled on the following DCI falling edge). The user loads this data pattern in the byte format into Register 0x61 through Register 0x68. The depth of the user defined pattern is selectable via Bit 4 of the SED_CTRL register (0x60). A default of 0, means a depth of two (using S0 and S1), and a 1 means a depth of four (using S0, S1, S2, and S3, and requiring the use of frame signal input to define S0 to the SED state machine). To properly align the input samples using a depth of 4, S0 is indicated by asserting the frame signal for a minimum of two complete input samples as shown in. The frame signal can be issued once at the start of the data transmission, or it can be asserted repeatedly at intervals coinciding with the S0 word. FRAME DATA[15:0] S0 S1 S2 S3 S0 S1 11744-037 DLL Configuration Example 1 Figure 32. Timing Diagram of Extended FRAMEx Signal Required to Align Input Data for SED The SED has three flag bits (Register 0x60, Bit 0, Bit 1, and Bit 2) that indicate the results of the input sample comparisons. The sample error detected bit (Register 0x60, Bit 0) is set when an error is detected and remains set until cleared. The autosample error detection (AED) mode is an autoclear mode that has two effects: it activates the compare fail bit and the compare pass bit (Register 0x60, Bit 1 and Bit 2). The compare pass bit sets if the last comparison indicated the sample was error free. The compare fail bit sets if an error is Rev. A | Page 21 of 56 AD9139 Data Sheet DELAY LINE INTERFACE MODE detected. The compare fail bit is automatically cleared by the reception of eight consecutive error free comparisons when autoclear mode is enabled. The sample error flag can be configured to trigger an IRQ when active, if desired, by enabling the appropriate bit in the event flag register (Register 0x04, Bit 6). SED EXAMPLE Normal Operation The following example illustrates the AD9139 SED configuration for continuously monitoring the input data and assertion of an IRQ when a single error is detected. 2. 3. 4. Write to the following registers to enable the SED and load the comparison values with a four-deep user pattern. Comparison values can be chosen arbitrarily; however, choosing values that require frequent bit toggling provides the most robust test. a. Register 0x61[7:0]→ S0[7:0] b. Register 0x62[7:0]→ S0[15:8] c. Register 0x63[7:0]→ S1[7:0] d. Register 0x64[7:0]→ S1[15:8] e. Register 0x65[7:0]→ S2[7:0] f. Register 0x66[7:0]→ S2[15:8] g. Register 0x67[7:0]→ S3[7:0] h. Register 0x68[7:0]→ S3[15:8] Enable SED. a. Register 0x60 → 0xD0 b. Register 0x60 → 0x90 Enable the SED error detect flag to assert the IRQx pin. a. Register 0x04[6] = 1 Begin transmitting the input data pattern (FRAMEx is also required because the depth of the pattern is 4). Table 15. Delay Line Setup and Hold Times (Guaranteed) Delay Setting Register 0x5E[7:0] Register 0x5F[2:0] tS (ns)1 tH (ns) |tS + tH| (ns) 1 0 0x00 0x60 −0.81 1.96 1.15 1 0x80 0x67 −0.97 2.20 1.23 3 0xFE 0x67 −1.28 2.79 1.51 There is a fixed 1.38 ns delay on the DCI signal when the delay line is enabled. Each tap adds a nominal delay of 200 ps to the fixed delay. To achieve the best timing margin, that is, to center the setup and hold window in the middle of the data eye, the user may need to add a delay on the data bus with respect to the DCI signal in the data source. Figure 33 is an example of calculating the optimal external delay. Register 0x0D[4] configures the DCI signal coupling settings for optimal interface performance over the operating frequency range. It is recommended that this bit be set to 1 (dc-coupled DCI) in the delay line interface mode. tDELAY = 0.13ns tDATA PERIOD = 2.5ns INPUT DATA[15:0] WITH OPTIMIZED DELAY 2 0xF0 0x67 −1.13 2.53 1.40 The negative sign indicates the direction of the setup time. The setup time is defined as positive when it is on the left side of the clock edge and negative when it is on the right side of the clock edge. DATA EYE |tS| = 0.81ns |tH| = 1.96ns DCI = 200MHz NO DATA TRANSITION Figure 33. Example of Interfacing Timing in the Delay Line-Based Mode Rev. A | Page 22 of 56 11744-038 1. The DLL is designed to help ease the interface timing requirements in very high speed data rate applications. The DLL has a minimum supported interface speed of 250 MHz, as shown in Table 2. For interface rates below this speed, use the interface delay line. In this mode, the DLL is powered off and a four-tap delay line is provided for the user to adjust the timing between the data bus and the DCI. Table 15 specifies the setup and hold times for each delay tap. Data Sheet AD9139 Interface Timing Requirements SPI Sequence to Enable Delay Line-Based Mode The following example shows how to calculate the optimal delay at the data source to achieve the best sampling timing in the delay line interface mode: Use the following SPI sequence to enable the delay line-based mode: • • fDCI = 200 MHz Delay setting = 0 The shadow area in Figure 33 is the interface setup and hold time window set to 0. To optimize the interface timing, this window must be placed in the middle of the data transitions. Because the input is double data rate, the available data period is 2.5 ns. Therefore, the optimal data bus delay, with respect to the DCI signal at the data source, can be calculated as t DELAY = (| t S | + | t H |) t DATA PERIOD − = 1.38 − 1.25 = 0.13 ns 2 2 Rev. A | Page 23 of 56 1. 0x5E → 0x00 /* Configure the delay setting */ 2. 0x5F → 0x60 3. 4. 0x0D → 0x16 /* DC couple DCI */ 0x0A → 0x00 /* Turn off DLL and duty cycle correction */ AD9139 Data Sheet FIFO OPERATION The AD9139 adopts source synchronous clocking in the data receiver (see the Data Interface section). The nature of source synchronous clocking is the creation of a separate clock domain at the receiving device. In the DAC, it is the DAC clock domain, that is, the DACCLK. Therefore, there are two clock domains inside of the DAC: the DCI and the DACCLK. Often, these two clock domains are not synchronous, requiring an additional stage to adjust the timing for proper data transfer. In the AD9139, a FIFO stage is inserted between the DCI and DACCLK domains to transfer the received data into the core clock domain (DACCLK) of the DAC. The AD9139 contains a 2-channel, 16-bit wide, eight-word deep FIFO. The FIFO acts as a buffer that absorbs timing variations between the two clock domains. The timing budget between the two clock domains in the system is significantly relaxed due to the depth of the FIFO. Figure 34 shows the block diagram of the datapath through the FIFO. The input data is latched into the device, formatted, and then written into the FIFO register, which is determined by the FIFO write pointer. The value of the write pointer is incremented every time a new word is loaded into the FIFO. Meanwhile, data is read from the FIFO register, which is determined by the read pointer, and fed into the digital datapath. The value of the read pointer is incremented every time data is read into the datapath from the FIFO. The FIFO pointers are incremented at the data rate, which is the DACCLK rate divided by the interpolation rate. Valid data is transmitted through the FIFO as long as the FIFO does not overflow (full) or underflow (empty). An overflow or underflow condition occurs when the write pointer and read pointer point to the same FIFO slot. This simultaneous access of data leads to unreliable data transfer through the FIFO and must be avoided. Normally, data is written to and read from the FIFO at the same rate to maintain a constant FIFO depth. If data is written to the FIFO faster than data is read, the FIFO depth increases. If data is read from the FIFO faster than data is written to it, the FIFO depth decreases. For optimal timing margin, maintain the FIFO depth near half full (a difference of four between the write pointer and read pointer values). The FIFO depth represents the FIFO pipeline delay and is part of the overall latency of the AD9139. FIFO WRITE CLOCK FIFO READ CLOCK DACCLK ÷INT FIFO FIFO SLOT 0 DATA RECEIVER LATCHED DATA[15:0] DATA FORMAT SPI FIFO RESET REG 0x25[0] READ POINTER FIFO SLOT 3 [15:0] FIFO SLOT 4 [15:0] WRITE POINTER FRAME FIFO SLOT 2 [15:0] DATA PATH DAC FIFO SLOT 5 FIFO SLOT 6 FIFO SLOT 7 RESET LOGIC FIFO LEVEL FIFO LEVEL REQUEST REG 0x23 Figure 34. Block Diagram of FIFO Rev. A | Page 24 of 56 11744-039 DCI INPUT DATA[15:0] FIFO SLOT 1 RETIMED DCI Data Sheet AD9139 RESETTING THE FIFO SERIAL PORT INITIATED FIFO RESET Upon device power-on, the read and write pointers start to roll around the FIFO from an arbitrary slot; consequently, the FIFO depth is unknown. To avoid a concurrent read and write to the same FIFO address and to assure a fixed pipeline delay from power-on to power-on, it is important to reset the FIFO pointers to a known state each time the device powers on or wakes up. This state is specified in the requested FIFO level (FIFO depth and FIFO level are used interchangeably in this data sheet), which consists of two parts: the integer FIFO level and the fractional FIFO level. A SPI initiated FIFO reset is the most common method to reset the FIFO. To initialize the FIFO level through the serial port, toggle FIFO_SPI_RESET_REQUEST (Register 0x25, Bit 0) from 0 to 1 and back to 0. When the write to this register is complete, the FIFO level is initialized to the requested FIFO level and the readback of FIFO_SPI_RESET_ACK (Register 0x25, Bit 1) is set to 1. The FIFO level readback, in the same format as the FIFO level request, must be within ±1 DACCLK cycle of the requested level. For example, if the requested value is 0x40 in 2× interpolation, the readback value should be one of the following: 0x31, 0x40, or 0x41. The range of ±1 DACCLK cycle indicates the default DAC latency uncertainty from power-on to power-on without turning on synchronization. The integer FIFO level represents the difference of the states between the read and write points in the unit of input data period (1/fDATA). The fractional FIFO level represents the difference of the FIFO pointers that is smaller than the input data period. The resolution of the fractional FIFO level is the input data period divided by the interpolation ratio and, thus, it is equal to one DACCLK cycle. The exact FIFO level, that is, the FIFO latency, can be calculated by FIFO Latency = Integer Level + Fractional Level Because the FIFO has eight data slots, there are eight possible FIFO integer levels. The maximum supported interpolation rate in the AD9139 is 2× interpolation. Therefore, there are two possible FIFO fractional levels. Two 3-bit registers in Register 0x23 are assigned to represent the two FIFO levels, as follows: • • Bits[6:4] represent the FIFO integer level Bits[2:0] represent the FIFO fractional level For example, if the interpolation rate is 2× and the desired total FIFO depth is 4.5 input data periods, set the FIFO_LEVEL_ CONFIG (Register 0x23) to 0x41 (4 means four data cycles and 1 means one DAC cycle, which is half of a data cycle, in this case). Reset the FIFO and initialize the FIFO level using either of the following methods: • • Serial port (SPI) initiated FIFO reset Frame initiated FIFO reset The recommended procedure for a serial port FIFO reset is as follows: 1. 2. 3. 4. 5. 6. 7. 8. 9. Configure the DAC in the desired interpolation mode (Register 0x28[7]). Ensure that the DACCLK and DCI clocks are running and stable at the clock inputs. Program Register 0x23 to 0x41. Request the FIFO level reset by setting Register 0x25[0] to 1. Verify that the device acknowledges the request by setting Register 0x25[1] to 1. Remove the request by setting Register 0x25[0] to 0. Verify that the device drops the acknowledge signal by setting Register 0x25[1] to 0. Read back Register 0x06[2] and Register 0x06[1]. If both bits are 0, continue to Step 9. If any of the two bits is 1, program Register 0x23 to 0x40. Read back Register 0x24 multiple times to verify that the actual FIFO level is set to the requested level (Register 0x23), and that the readback values are stable. By design, the readback is within ±1 DACCLK around the requested level. FRAME INITIATED FIFO RESET The frame input has two functions. One function is to indicate the beginning of a byte stream in the byte interface mode, as described in the Data Interface section. The other function is to initialize the FIFO level by asserting the frame signal high for at least the time interval required to load two samples of data to the DAC. This corresponds to one DCI period in word mode and two DCI periods in byte mode. Note that this requirement of the frame pulse length is longer than that of the frame signal when it serves only to assemble the byte stream. The device accepts either a continuous frame or a one shot frame signal. Rev. A | Page 25 of 56 AD9139 Data Sheet In the continuous reset mode, the FIFO responds to every valid frame pulse and resets itself. In the one shot reset mode, the FIFO responds only to the first valid frame pulse after the FRAME_RESET_MODE bits (Register 0x22[1:0]) are set. Therefore, even with a continuous frame input, the FIFO resets one time only; this prevents the FIFO from toggling between the two states from periodic resets. The one shot frame reset mode is the default and the recommended mode. The recommended procedure for a frame initiated FIFO reset is as follows: 1. 2. 3. 4. 5. 6. 7. 8. 9. Configure the DAC in the desired interpolation mode (Register 0x28[7]). Ensure that the DACCLK and DCI clocks are running and stable at the clock inputs. Ensure that the DLL is locked (if using DLL Mode) or the DCI clock is being sent properly (if using bypass mode). Program Register 0x23 to 0x41. Configure the FRAME_RESET_MODE bits (Register 0x22[1:0]) to 10. Choose one shot frame mode by writing 0 to EN_CON_FRAME_RESET (Register 0x22[2]). Toggle the frame input from 0 to 1 and back to 0. The pulse width must be longer than the minimum requirement. Read back Register 0x06[2] and Register 0x06[1]. If both bits are 0, continue to Step 9. If any of the two bits are 1, program Register 0x23 to 0x40. Read back Register 0x24 multiple times to verify that the actual FIFO level is set to the requested level (Register 0x23) and the readback values are stable. By design, the readback should be within ±1 DACCLK around the requested level. These procedures apply in synchronization off mode only. For resetting FIFO in synchronization on mode, refer to the synchronization procedure in the Multidevice Synchronization and Fixed Latency section. FIFO reset is one of the steps to achieve synchronization. Monitoring the FIFO Status Monitor the real-time FIFO status from SPI Register 0x24, which reflects the real-time FIFO depth after a FIFO reset. Without timing drifts in the system, this readback does not change from that which resulted from the FIFO reset. When there is a timing drift or other abnormal clocking situation, the FIFO level readback can change. However, as long as the FIFO does not overflow or underflow, there is no error in data trans-mission. The status bits in Register 0x06, Bits[2:1] indicate if there are FIFO underflows or overflows. Latch the status of the two bits to trigger the hardware interrupts, IRQ1 and IRQ2. To enable latching and interrupts, configure the corresponding bits in Register 0x03 and Register 0x04. Rev. A | Page 26 of 56 Data Sheet AD9139 DIGITAL DATAPATH 0.02 The block diagram in Figure 35 shows the functionality of the digital datapath. The digital processing includes 0 One half-band interpolation filter An inverse sinc filter A gain and offset adjustment block DIGITAL GAIN AND OFFSET ADJUSTMENT –0.02 –0.04 –0.06 –0.10 Figure 35. Block Diagram of Digital Datapath 0 0.05 0.10 0.15 0.20 0.25 0.30 0.35 0.40 0.45 1.8 2.0 FREQUENCY (Hz) INTERPOLATION FILTERS 11744-041 –0.08 Figure 36. Pass-Band Detail of 2× Mode The transmit path contains a half-band interpolation filter. The interpolation filters provides a 2× increase in output data rate and a low-pass function. 0 –10 –20 MAGNITUDE (dB) The AD9139 provides two interpolation modes. Each mode offers a different usable signal bandwidth in an operating mode. Which mode to select depends on the required signal bandwidth and the DAC update rate. Refer to Table 5 for the maximum speed and signal bandwidth of each interpolation mode. 10 The usable bandwidth in 1× interpolation is the DCI rate or half of the input data rate. The usable bandwidth in 2× interpolation is 0.8 times the DCI rate or 0.4 times the input data rate. It is defined as the frequency band over which the filters have a pass-band ripple of less than ±0.001 dB and a stop-band rejection of greater than 85 dB. –30 –40 –50 –60 –70 –80 –90 –100 0 0.2 0.4 0.6 0.8 1.0 1.2 1.4 1.6 FREQUENCY (Hz) Figure 37. All-Band Response of 2× Mode 2× Interpolation Mode Figure 36 and Figure 37 show the pass-band and all-band filter response for 2× mode. Note that the transition from the transition band to the stop band is much sharper than the transition from the pass band to the transition band. Therefore, when the desired output signal moves out of the defined pass band, the signal image, which is supposed to be suppressed by the stop band, grows faster than the droop of the signal itself due to the degraded pass-band flatness. In cases where the degraded image rejection is acceptable or can be compensated by the analog low-pass filter at the DAC output, it is possible to let the output signal extend beyond the specified usable signal bandwidth. Rev. A | Page 27 of 56 11744-042 INV SINC 11744-040 HB1 MAGNITUDE (dB) AD9139 Data Sheet Upper Coefficient H(55) H(54) H(53) H(52) H(51) H(50) H(49) H(48) H(47) H(46) H(45) H(44) H(43) H(42) H(41) H(40) H(39) H(38) H(37) H(36) H(35) H(34) H(33) H(32) H(31) H(30) H(29) Integer Value −4 0 +13 0 −32 0 +69 0 −134 0 +239 0 −401 0 +642 0 −994 0 +1512 0 −2307 0 +3665 0 −6638 0 +20,754 +32,768 INVERSE SINC FILTER The AD9139 provides a digital inverse sinc filter to compensate for the DAC rolloff over frequency. The inverse sinc (sinc−1) filter is a seven-tap FIR filter. Figure 38 shows the frequency response of sin(x)/x rolloff, the inverse sinc filter, and their composite response. The composite response has less than ±0.05 dB passband ripple up to a frequency of 0.4 × fDAC. 1 0 –1 sin(x)/x ROLLOFF SINC–1 FILTER COMPOSITE –2 –3 –4 –5 0 0.05 0.10 0.15 0.20 0.25 0.30 0.35 0.40 FREQUENCY (Hz) 0.45 0.50 11744-043 Lower Coefficient H(1) H(2) H(3) H(4) H(5) H(6) H(7) H(8) H(9) H(10) H(11) H(12) H(13) H(14) H(15) H(16) H(17) H(18) H(19) H(20) H(21) H(22) H(23) H(24) H(25) H(26) H(27) H(28) To provide the necessary peaking at the upper end of the pass band, the inverse sinc filter has an intrinsic insertion loss of approximately 3.8 dB. Offset the loss of the digital gain by increasing the digital gain adjustment setting to minimize the impact on the output signal-to-noise ratio (SNR). However, care is needed to ensure that the additional digital gain does not cause signal saturation, especially at high output frequencies. The sinc−1 filter is disabled by default; it can be enabled by setting the INVSINC_ENABLE bit to 1 in Register 0x27[7]). MAGNITUDE (dB) Table 16. Half-Band Filter 1 Coefficient Figure 38. Responses of sin(x)/x Roll-Off (Blue), Sinc−1 Filter (Red), and Composite of Both (Black) Table 17. Inverse Sinc Filter Lower Coefficient H(1) H(2) H(3) H(4) Upper Coefficient H(7) H(6) H(5) Integer Value −1 +4 −16 +192 DIGITAL FUNCTION CONFIGURATION The inverse sinc filter can be enabled or disabled. The pipeline latency of the DAC is dependent on which of the digital function blocks are enabled or disabled. If fixed DAC pipeline latency is desired during operation, leave each digital function block always enabled or always disabled after initial configuration. Rev. A | Page 28 of 56 Data Sheet AD9139 MULTIDEVICE SYNCHRONIZATION AND FIXED LATENCY A DAC introduces a variation of pipeline latency to a system. The latency variation causes the phase of a DAC output to vary from power-on to power-on. Therefore, the output from different DAC devices may not be perfectly aligned even with well aligned clocks and digital inputs. The skew between multiple DAC outputs varies from power-on to power-on. In applications such as transmit diversity or digital predistortion, where deterministic latency is desired, the variation of the pipeline latency must be minimized. Deterministic latency in this data sheet is defined as a fixed time delay from the digital input to the analog output in a DAC from power-on to power-on. Multiple DAC devices are considered synchronized to each other when each DAC in this group has the same constant latency from power-on to power-on. Three conditions must be identical in all of the ready-to-sync devices before these devices are considered synchronized: • • • The phase of DAC internal clocks The FIFO level The alignment of the input data VERY SMALL INHERENT LATENCY VARIATION The innovative architecture of the AD9139 minimizes the inherent latency variation. The worst-case variation in the AD9139 is two DAC clock cycles. For example, in the case of a 1.6 GHz sample rate, the variation is less than 1.25 ns in any scenario. Therefore, without turning on the synchronization engine, the DAC outputs from multiple AD9139 devices are guaranteed to be aligned within two DAC clock cycles, regardless of the timing between the DCI and the DACCLK. No additional clocks are required to achieve this accuracy. The user must reset the FIFO in each DAC device through the SPI at startup. Therefore, the AD9139 can decrease the complexity of system design in multiple transmit channel applications. Note the alignment of the DCI signals in the design. The DCI signal is used as a reference in the AD9139 design to align the FIFO and the phase of internal clocks in multiple parts. The achieved DAC output alignment depends on how well the DCI signals are aligned at the input of each device. The following equation is the expression of the worst-case DAC output alignment accuracy in the case of DCI signal mismatches: tSK (OUT) = tSK (DCI) + 2/fDAC where: tSK (OUT) is the worst-case skew between the DAC outputs from two AD9139 devices. tSK (DCI) is the skew between two DCI signals at the DCI input of the two AD9139 devices. fDAC is the DACCLK frequency. The better the alignment of the DCI signals, the smaller the overall skew between the two DAC outputs. FURTHER REDUCING THE LATENCY VARIATION For applications that require finer synchronization accuracy (DAC latency variation < 2 DAC clock cycles), the AD9139 has a provision for enabling multiple devices to be synchronized to each other within a single DAC clock cycle. To reduce further the latency variation in the DAC, the synchronization machine must be turned on and two external clocks (frame and sync) must be generated in the system and fed to all the DAC devices. Setup and Hold Timing Requirement The sync clock (SYNCCLK) serves as a reference clock in the system to reset the clock generation circuitry in multiple AD9139 devices simultaneously. Inside the DAC, the sync clock is sampled by the DACCLK to generate a reference point for aligning the internal clocks; consequently, there is a setup and hold timing requirement between the sync clock and the DAC clock. Adopting the continuous frame reset mode (where the FIFO and sync engine periodically reset) demands meeting the timing requirements between the sync clock and the DAC clock; otherwise, the device can lose lock and corrupt the output. In the one shot frame reset mode, it is still recommended that this timing be met at the time when the sync routine is run because not meeting the timing can degrade the sync alignment accuracy by one DAC clock cycle, as shown in Table 18. The AD9139 also provides a mode by which to synchronize the device in a one shot manner and to continue to monitor the synchronization status. It provides a continuous sync and frame clock to synchronize the device once and ignore the clock cycles after detecting the first valid frame pulse. In this way, the user can monitor the sync status without periodically resynchronizing the device; to engage one shot sync mode, set Register 0x22[2] to 0. Table 18. Sync Clock and DAC Clock Setup and Hold Times Falling Edge Sync Timing (Default) tS (ns) tH (ns)1 |tS + tH| (ns) 1 Min (ps) 324 −92 232 The negative sign indicates the direction of the setup time. The setup time is defined as positive when it is on the left side of the clock edge and negative when it is on the right side of the clock edge. SYNCHRONIZATION IMPLEMENTATION The AD9139 allows the user to choose either the rising or falling edge of the DAC clock to sample the sync clock, which makes it easier to meet the timing requirements. Ensure that the sync clock, fSYNC, is 1/8 × fDCI or slower by a factor of 2n, n being an integer (1, 2, 3…). Note that there is a limit on how slow the sync clock can be because of the ac coupling nature of the sync clock receiver. Choose an appropriate value of the ac coupling capacitors to ensure that the signal swing meets the data sheet specification, as listed in Table 2. Rev. A | Page 29 of 56 AD9139 Data Sheet The frame clock resets the FIFO in multiple AD9139 devices. The frame can be either a one shot or continuous clock. In either case, the pulse width of the frame must be longer than one DCI cycle in the word mode and two DCI cycles in the byte mode. When the frame is a continuous clock, fFRAME, ensure that it is 1/8 × fDCI or slower by a factor of 2n, n being an integer (1, 2, 3…). One shot frame reset is the recommended method. Because the DCI and the DAC clock are generated in two separate clock domains, timing drifts between the two clocks can cause the FIFO level to toggle between two values in the continuous reset mode and, thus, to corrupt the DAC output. Table 19 lists the requirements of the frame clock in various conditions. SYNCHRONIZATION PROCEDURES When the sync accuracy of an application is less precise than two DAC clock cycles, it is recommended to turn off the synchronization machine because no additional steps are required, other than the regular start-up procedure sequence. For applications that require more precise sync accuracy than two DAC clock cycles, use the procedures in the following sections to set up the system and configure the device. Table 19. Frame Clock Speed and Pulse Width Requirement Sync Clock One Shot Continuous 1 Maximum Speed N/A1 fDCI/8 Minimum Pulse Width For both one shot and continuous sync clocks, word mode = one DCI cycle, and byte mode = two DCI cycles. N/A means not applicable. Rev. A | Page 30 of 56 Data Sheet AD9139 1. DAC HARDWARE RESET. PULL THE DAC RESET PIN FROM HIGH TO LOW THEN BACK TO HIGH. 2. SET UP DAC INTERPOLATION MODE. PROGRAM REG 0x28 3. RUN CLOCKS (DAC CLOCK, SYNC CLOCK, DCI, FRAME). 4. MAKE SURE DLL IS LOCKED IF IN DLL MODE, OR DELAY LINE IS ENABLED AND PROPERLY CONFIGURED IF IN DELAY LINE MODE. SYSTEM SETUP; PROGRAM DAC INTERPOLATION MODES SET FIFO OFFSET TO 0 WRITE REG 0x23 = 0x00 ENABLE SYNC ENGINE WRITE REG 0x21 = 0x01, IF RISING EDGE SYNC. OR = 0x03, IF FALLING EDGE SYNC. WRITE REG 0x22 = 0x18 IN THIS MODE, THE PART ONLY RESPONDS TO THE FIRST VALID FRAME PULSE AND RESETS THE FIFO ONE TIME. SET FRAME UPDATE MODE REG 0x05[6:5] = 0b00 REG 0x05[6] = 0b1 READ REG 0x05[6:5] ([SYNC_LOST;SYNC_LOCKED]). IF THE SYNC-DAC SETUP/HOLD TIMES ARE NOT MET, THE SYNC MAY NOT LOCK. CHANGE THE SYNC EDGE WHEN REENABLING THE SYNC NEXT ROUND. SYNC LOST/LOCK FLAG BITS? DISABLE SYNC REG 0x05 [6:5] = 0b01 CALCULATE AND ADJUST FIFO OFFSET . LEVEL. ADJUST FIFO OFFSET TO ACHIEVE THE OPTIMAL FIFO 1. READ BACK REG 0x24. LET A = REG 0x24[6:4], B = REG 0x24[2:0]. 2. LET X = INTERPOLATION RATE. (VALID NUMBERS ARE 1 AND 2). 3. OFFSET = (4 × X + 1) – (A × X + B) 4. IF OFFSET ≥ 0, OFFSET = OFFSET. ELSE OFFSET = 8 × X + OFFSET. 5. LET A’ = FLOOR (OFFSET/X), B’ = OFFSET – (A’) × X 6. WRITE REG 0x23[6:4] = A’, REG 0x23[2:0] = B’. 7. SAVE A’ AND B’. (USE THE SAME A’ AND B’ VALUES WHEN ADJUSTING THE FIFO OFFSET IN THE OTHER DACs). REG 0x06[2:1] = 0b00 FIFO UF/OFF LAG BITS? READ REG 0x06[2:1]. IF NO FLAGS, SYNCHRONIZATION IS COMPLETE. SKIP THE NEXT STEP. IF EITHER BIT IS 1, FOLLOW THE NEXT STEP. REG 0x06[2:1] ≠ 0b00 FURTHER ADJUST FIFO OFFSET WAKE UP DACs AND RUN READ REG 0x23 AND RECORD IT AS RB1. WRITE REG 0x23 = RB1 – 0x01; READ REG 0x23 AND RECORD IT AS RB2. WRITE REG 0x23 = RB2 + 0x01 1. WAKE UP DACs WRITE REG 0x01 = 0x00. 2. START DATA TRANSMISSION. Figure 39. Synchronization Procedure Diagram Rev. A | Page 31 of 56 11744-044 WRITE REG 0x21 = 0x00 AD9139 Data Sheet INTERRUPT REQUEST OPERATION The AD9139 provides an interrupt request output signal on Pin 50 and Pin 51 (IRQ2 and IRQ1, respectively) to notify an external host processor of significant device events. Upon assertion of the interrupt, query the device to determine the precise event that occurred. The IRQ1 pin and IRQ2 pin are open-drain, active low outputs. Pull the IRQx pin high (DVDD18 supply) external to the device. The IRQx pin can be tied to the interrupt pins of other devices with open-drain outputs to wire-OR these pins together. method is by writing 1 to the corresponding event flag bit. The second method is to use a hardware or software reset to clear the INTERRUPT_SOURCE signal. The IRQ2 circuitry works in the same way as the IRQ1 circuitry. Any one or multiple event flags can be enabled to trigger the IRQx pins. The user can select one or both hardware interrupt pins for the enabled event flags. Register 0x07 and Register 0x08 determine the pin to which each event flag is routed. Set Register 0x07 and Register 0x08 to 0 for IRQ1 and set these registers to 1 for IRQ2. Eleven event flags provide visibility into the device. These flags are located in the two event flag registers, Register 0x05 and Register 0x06. The behavior of each event flag is independently selected in the interrupt enable registers, Register 0x03 and Register 0x04. When the flag interrupt enable is active, the event flag latches and triggers the IRQ1 and/or IRQ2 pins. When the flag interrupt is disabled, the event flag monitors the source signal, but the IRQ1 and IRQ2 pins remain inactive. INTERRUPT SERVICE ROUTINE Interrupt request management starts by selecting the set of event flags that require host intervention or monitoring. Enable the events that require host action so that the host is notified when they occur. For events requiring host intervention upon IRQx activation, run the following routine to clear an interrupt request: INTERRUPT WORKING MECHANISM 1. Figure 40 shows the interrupt related circuitry and how the event flag signals propagate to the IRQx output. The INTERRUPT_ ENABLE signal represents one bit from the interrupt enable register. The EVENT_FLAG_SOURCE signal represents one bit from the event flag register. The EVENT_FLAG_SOURCE signal represents one of the device signals that can be monitored, such as the PLL_LOCK signal from the PLL phase detector or the FIFO_OVERFLOW signal from the FIFO controller. 2. 3. 4. 5. 6. When an interrupt enable bit is set high, the corresponding event flag bit reflects a positively tripped version of the EVENT_FLAG_ SOURCE signal; that is, the event flag bit is latched on the rising edge of the EVENT_FLAG_SOURCE signal. This signal also asserts the external IRQx pins. Read the status of the event flag bits that are being monitored. Set the interrupt enable bit low to monitor the unlatched EVENT_FLAG_SOURCE signal directly. Perform any actions that may be required to clear the EVENT_FLAG_SOURCE signal. In many cases, no specific actions are required. Read the event flag to verify that the actions taken have cleared the EVENT_FLAG_SOURCE signal. Clear the interrupt by writing 1 to the event flag bit. Set the interrupt enable bits of the events to be monitored. Note that some EVENT_FLAG_SOURCE signals are latched signals. Clear these signals by writing to the corresponding event flag bit. For more information about each of the event flags, see the Device Configuration Register Map and Description section. When an interrupt enable bit is set low, the event flag bit reflects the present status of the EVENT_FLAG_SOURCE signal, and the event flag has no effect on the external IRQx pins. Clear the latched version of an event flag (the INTERRUPT_ SOURCE signal) in one of two ways. The recommended 0 1 EVENT_FLAG IRQ INTERRUPT_ENABLE EVENT_FLAG_SOURCE INTERRUPT_ SOURCE OTHER INTERRUPT SOURCES 11744-045 WRITE_1_TO_EVENT_FLAG DEVICE_RESET Figure 40. Simplified Schematic of IRQx Circuitry Rev. A | Page 32 of 56 Data Sheet AD9139 TEMPERATURE SENSOR The AD9139 has a diode-based temperature sensor for measuring the temperature of the die. The temperature reading is accessed using Register 0x1D and Register 0x1E. The temperature of the die can be calculated as TDIE (DIETEMP[15:0] 41,237) 106 TA = TDIE – PD × θJA = 50 – 0.8 × 20.7 = 33.4°C where TDIE is the die temperature in degrees Celsius. The temperature accuracy is ±7°C typical over the −40°C to +85°C range with one point temperature calibration against a known temperature. See Figure 41 for a typical plot of the die temperature code readback vs. die temperature. where: TA is the ambient temperature in degrees Celsius. TDIE is the die temperature in degrees Celsius. PD is power consumption of the device. θJA is the thermal resistance from junction to ambient of the AD9139, as shown in Table 7. To use the temperature sensor, it must be enabled by setting Register 0x1C[0] to 1. In addition, to obtain accurate readings, set the die temperature control register (Register 0x1C) to 0x03. 51000 49000 47000 45000 43000 41000 39000 37000 35000 –40 –30 –20 –10 0 10 20 30 40 50 60 70 80 90 TEMPERATURE (°C) 11744-046 DIE CODE READBACK Estimates of the ambient temperature can be made if the power dissipation of the device is known. For example, if the device power dissipation is 800 mW and the measured die temperature is 50°C, then calculate the ambient temperature as Figure 41. Die Temperature Code Readback vs. Die Temperature Rev. A | Page 33 of 56 AD9139 Data Sheet DAC INPUT CLOCK CONFIGURATIONS The AD9139 DAC sample clock (DACCLK) can be sourced directly or by clock multiplying. Clock multiplying employs the on-chip phase-locked loop (PLL) that accepts a reference clock operating at a submultiple of the desired DACCLK rate. The PLL then multiplies the reference clock up to the desired DACCLK frequency, which then generates all of the internal clocks required by the DAC. The clock multiplier provides a high quality clock that meets the performance requirements of most applications. Using the on-chip clock multiplier removes the burden of generating and distributing the high speed DACCLK. The second mode bypasses the clock multiplier circuitry and sources DACCLK directly to the DAC core. This mode lets the user source a very high quality clock directly to the DAC core. DRIVING THE DACCLK AND REFCLK INPUTS The DACCLKx and REFCLKx differential inputs share similar clock receiver input circuitry (see Figure 42 for a simplified circuit diagram of the input). The on-chip clock receiver has a differential input impedance of about 10 kΩ. It is self biased to a commonmode voltage of about 1.25 V. Drive the inputs by differential PECL or LVDS drivers with ac coupling between the clock source and the receiver. 1nF~100nF AD9139 DACCLKP, REFP/SYNCP Direct clocking with a low noise clock produces the lowest noise spectral density at the DAC outputs. To select the differential clock inputs as the source for the DAC sampling clock, set the PLL enable bit (Register 0x12[7]) to 0. This powers down the internal PLL clock multiplier and selects the input from the DACCLKP and DACCLKN pins as the source for the internal DAC sampling clock. The REFCLKx input can remain floating. The device also has clock duty cycle correction circuitry and differential input level correction circuitry. Enabling these circuits can provide improved performance in some cases. The control bits for these functions are in Register 0x10 and Register 0x11. CLOCK MULTIPLICATION The on-chip PLL clock multiplier circuit generates the DAC sample rate clock from a lower frequency reference clock. When the PLL enable bit (Register 0x12[7]) is set to 1, the clock multiplication circuit generates the DAC sampling clock from the lower rate REFCLK input and the DACCLKx input remains floating. See Figure 43 for the functional diagram of the clock multiplier. The clock multiplier circuit operates such that the VCO outputs a frequency, fVCO, equal to the REFCLKx input signal frequency multiplied by N1 × N0. N1 is the divide ratio of the loop divider; N0 is the divide ratio of the VCO divider. fVCO = fREFCLK × (N1 × N0) 5kΩ 1Nf~100nF 5kΩ DACCLKN, REFN/SYNCN The DAC sample clock frequency, fDACCLK, is equal to 1.25V fDACCLK = fREFCLK × N1 11744-047 100Ω Figure 42. Clock Receiver Input Simplified Equivalent Circuit The minimum input drive level to the differential clock input is 100 mV p-p differential. The optimal performance is achieved when the clock input signal is between 800 mV p-p differential and 1.6 V p-p differential. Whether using the on-chip clock multiplier or sourcing the DACCLK directly, the input clock signal to the device must have low jitter and fast edge rates to optimize the DAC noise performance. REFP/SYNCP (PIN 2) REFN/SYNCN (PIN 3) PHASE FREQUENCY DETECTION The output frequency of the VCO must be chosen to keep fVCO in the optimal operating range of 1.0 GHz to 2.1 GHz. It is important to select a frequency of the reference clock and values of N1 and N0 so that the desired DACCLK frequency can be synthesized and the VCO output frequency is in the correct range. ADC PLL CHARGE PUMP CURRENT REG 0x14[4:0] PLL LOOP BW REG 0x14[7:5] CHARGE PUMP ON-CHIP LOOP FILTER VCO (1GHz~2.1GHz) LOOP DIVIDER REG 0x15[1:0] VCO DIVIDER REG 0x15[3:2] DIVIDE BY 2, 4, 8, OR 16 DIVIDE BY 1, 2, OR 4 DACCLKP (PIN 62) VCO CONTROL VOLTAGE REG 0x16[3:0] DACCLK DACCLKN (PIN 61) PLL ENABLE REG 0x12[7] Figure 43. PLL Clock Multiplier Circuit Rev. A | Page 34 of 56 11744-048 RECOMMENDED EXTERNAL CIRCUITRY DIRECT CLOCKING Data Sheet AD9139 PLL SETTINGS 61 The PLL circuitry requires three settings to be programmed to their nominal values. The PLL values listed in Table 20 are the recommended settings for these parameters. 53 57 49 45 PLL BAND 41 Table 20. PLL Settings Optimal Setting (Binary) 111 00111 0 33 29 25 21 17 13 9 5 1 950 CONFIGURING THE VCO TUNING BAND 1150 1350 1550 1750 1950 VCO FREQUENCY (MHz) The PLL VCO has a valid operating range from approximately 1.03 GHz to 2.07 GHz covered in 64 overlapping frequency bands. For any desired VCO output frequency, there may be several valid PLL band select values. See Figure 44 for the frequency bands of a typical device. Device-to-device variations and operating temperature affect the actual band frequency range. Therefore, it is necessary to determine the optimal PLL band select value for each individual device. 2150 11744-049 PLL SPI Control Register PLL Loop Bandwidth PLL Charge Pump Current PLL Cross Point Control Enable Register Address 0x14[7:5] 0x14[4:0] 0x15[4] 37 Figure 44. PLL Lock Range for a Typical Device MANUAL VCO BAND SELECT The device includes a manual band select mode (PLL auto manual enable, Register 0x12[6] = 1) that lets the user select the VCO tuning band. In manual mode, the VCO band is set directly with the value written to the manual VCO band bits (Register 0x12[5:0]). AUTOMATIC VCO BAND SELECT PLL ENABLE SEQUENCE The device has an automatic VCO band select feature on chip. Using the automatic VCO band select feature is a simple and reliable method of configuring the VCO frequency band. Enable this feature by starting the PLL in manual mode and then placing the PLL in autoband select mode by setting Register 0x12 to a value of 0xC0 and then to a value of 0x80. When these values are written, the device executes an automated routine that determines the optimal VCO band setting for the device. To enable the PLL in automatic or manual mode properly, the following sequence must be followed: The setting selected by the device ensures that the PLL remains locked over the full −40°C to +85°C operating temperature range of the device without further adjustment. The PLL remains locked over the full temperature range even if the temperature during initialization is at one of the temperature extremes. 3. 4. 5. Automatic Mode Sequence 1. 2. Configure the loop divider and the VCO divider registers for the desired divide ratios. Set 00111 to PLL charge pump current and 111 to PLL loop bandwidth for the best performance. Register 0x14 = 0xE7 (default). Set the PLL mode to manual using Register 0x12[6] = 1. Enable the PLL using Register 0x12[7] = 1. Set the PLL mode to automatic using Register 0x12[6] = 0. Manual Mode 1. 2. 3. 4. 5. Rev. A | Page 35 of 56 Configure the loop divider and the VCO divider registers for the desired divide ratios. Set 00111 to PLL charge pump current and 111 to PLL loop bandwidth for the best performance. Register 0x14 = 0xE7 (default). Select the desired band using Register 0x12[5:0]. Set the PLL mode to manual using Register 0x12[6] = 1. Enable the PLL using Register 0x12[7] = 1. AD9139 Data Sheet ANALOG OUTPUTS TRANSMIT DAC OPERATION 35 DAC FSADJUST REG 0x18, 0x19 0 0 200 DACOUTN 400 600 800 DAC GAIN CODE 1000 Figure 46. DAC Full-Scale Current vs. DAC Gain Code CURRENT SCALING Transmit DAC Transfer Function 11744-050 10kΩ RSET Figure 45. Simplified Block Diagram of DAC Core The DAC has a 1.2 V band gap reference with an output impedance of 5 kΩ. The reference output voltage appears on the VREF pin. When using the internal reference, decouple the VREF pin to AVSS with a 0.1 µF capacitor. Use the internal reference only for external circuits that draw dc currents of 2 µA or less. For dynamic loads or static loads greater than 2 µA, buffer the VREF pin. If desired, the internal reference can be overdriven by applying an external reference (from 1.10 V to 1.30 V) to the pin. A 10 kΩ external resistor, RSET, must be connected from the FSADJ pin to AVSS. This resistor, together with the reference control amplifier, sets up the correct internal bias currents for the DAC. Because the full-scale current is inversely proportional to this resistor, the tolerance of RSET is reflected in the full-scale output amplitude. The full-scale current equation, where the DAC gain is set in Register 0x18 and Register 0x19, is as follows: I FS = 15 5 DACOUTP VREF FSADJ 20 10 DAC 5kΩ 0.1µF 25 11744-051 1.2V 30 IFS (mA) Figure 45 shows a simplified block diagram of the transmit path DACs. The DAC core consists of a current source array, a switch core, digital control logic, and full-scale output current control. The DAC full-scale output current (IOUTFS) is nominally 20 mA. The output currents from the DACOUTP and DACOUTN pins are complementary, meaning that the sum of the two currents always equals the full-scale current of the DAC. The digital input code to the DAC determines the effective differential current delivered to the load. VREF 3 × 72 + × DAC gain RSET 16 For nominal values of VREF (1.2 V), RSET (10 kΩ), and DAC gain (512), the full-scale current of the DAC is typically 20 mA. The DAC full-scale current is adjustable from 8.64 mA to 31.68 mA by setting the DAC gain parameter, as shown in Figure 46. The output currents from the DACOUTP and DACOUTN pins are complementary, meaning that the sum of the two currents always equals the full-scale current of the DAC. The digital input code to the DAC determines the effective differential current delivered to the load. The DACOUTP pin provides maximum output current when all bits are high. The output currents vs. DACCODE for the DAC outputs is expressed as DACCODE I OUTP = × I OUTFS 2N IOUTN = IOUTFS – IOUTP (1) (2) where DACCODE = 0 to 2N − 1. Transmit DAC Output Configurations The optimum noise and distortion performance of the AD9139 is realized when it is configured for differential operation. The common-mode rejection of a transformer or differential amplifier significantly reduces the common-mode error sources of the DAC outputs. These common-mode error sources include even-order distortion products and noise. The enhancement in distortion performance becomes more significant as the frequency content of the reconstructed waveform increases and/or its amplitude increases. This is due to the first-order cancellation of various dynamic common-mode distortion mechanisms, digital feedthrough, and noise. Figure 47 shows the most basic DAC output circuitry. A pair of resistors, RO, converts each of the complementary output currents to a differential voltage output, VOUT. Because the current outputs of the DAC are high impedance, the differential driving point impedance of the DAC outputs, ROUT, is equal to 2 × RO. See Figure 48 for the output voltage waveforms. Rev. A | Page 36 of 56 Data Sheet AD9139 DACOUTP + VOUTP 67 DACOUTP VOUT VOUTN IBBP RBIP 50Ω – 11744-052 RO ADL537x AD9139 RO DACOUTN RLI 100Ω RBIN 50Ω 66 IBBN DACOUTN Figure 47. Basic Transmit DAC Output Circuit AD9139 67 DACOUTP QBBN RBQN 50Ω VCM VN 66 VP QBBP DACOUTN Figure 49. Typical Interface Circuitry Between the AD9139 and the ADL537x Family of Modulators 0 The baseband inputs of the ADL537x family require a dc bias of 500 mV. The nominal midscale output current on each output of the DAC is 10 mA (one-half the full-scale current). Therefore, a single 50 Ω resistor to ground from each of the DAC outputs results in the desired 500 mV dc common-mode bias for the inputs to the ADL537x. The addition of the load resistor in parallel with the modulator inputs reduces the signal level. The peak-to-peak voltage swing of the transmitted signal is 11744-053 VOUT –VPEAK Figure 48. Output Voltage Waveforms The common-mode signal voltage, VCM, is calculated as I FS × RO 2 VSIGNAL = I FS × The differential peak-to-peak output voltage, VPEAK, is calculated as (2 × R B × R L ) (2 × R B + R L ) Baseband Filter Implementation VPEAK = 2 × IFS × RO Most applications require a baseband anti-imaging filter between the DAC and the modulator to filter out Nyquist images and broadband DAC noise. The filter can be inserted between the termination resistors at the DAC output and the signal level setting resistor across the modulator input. This configuration establishes the input and output impedances for the filter. INTERFACING TO MODULATORS The AD9139 interfaces to the ADL537x family of modulators with a minimal number of components. An example of the recommended interface circuitry is shown in Figure 49. Figure 50 shows a fifth-order, low-pass filter. Splitting the filter capacitors into two and grounding the center point creates a common-mode low-pass filter that provides additional common-mode rejection of high frequency signals. A purely differential filter can pass common-mode signals. For more details about interfacing the AD9139 DAC to an IQ modulator,see the Circuits from the Lab™, Circuit Note CN-0205, Interfacing the ADL5375 I/Q Modulator to the AD9122 Dual Channel, 1.2 GSPS High Speed DAC on the Analog Devices website. 50Ω AD9139 22pF 33nH 33nH 33nH 33nH 3.6pF 50Ω 3pF 6pF 22pF 140Ω ADL537x 3pF Figure 50. DAC Modulator Interface with Fifth-Order, Low-Pass Filter Rev. A | Page 37 of 56 11744-055 VCM = RLQ 100Ω RBQP 50Ω 11744-054 +VPEAK AD9139 Data Sheet REDUCING LO LEAKAGE AND UNWANTED SIDEBANDS (Register 0x18 through Register 0x19) can be used to calibrate the gain of the transmit paths to optimize sideband suppression. Analog quadrature modulators can introduce unwanted signals at the local oscillator (LO) frequency caused by dc offset voltages in the I and Q baseband inputs, as well as feedthrough paths from the LO input to the output. For more information about suppressing LO leakage and sideband image, refer to Application Note AN-1039, Correcting Imperfections in IQ Modulators to Improve RF Signal Fidelity and Application Note AN-1100, Wireless Transmitter IQ Balance and Sideband Suppression from the Analog Devices website. Effective sideband suppression requires both gain and phase matching of the I and Q signals. The DAC FS adjust registers Rev. A | Page 38 of 56 Data Sheet AD9139 START-UP ROUTINE To ensure reliable start up of the AD9139, certain sequences must be followed. Read 0x25[1] /* Expect 1b if the FIFO reset is complete */ Read 0x24 /* The readback should be one of the three values: 0x30, 0x40, or 0x50 */ Device Configuration and Start-Up Sequence 1 1. 2. 3. 4. Set fDCI = 600 MHz, fDATA = 1200 MHz, and interpolation to 1×. Enable the PLL, and set fREF = 300 MHz. Enable the inverse sinc filter. Use the DLL-based interface mode and set DLL phase offset = 0. /* Enable Inverse SINC filter */ 0x27 → 0x80 /* Power up DAC outputs */ Derived PLL Settings 0x01 → 0x00 The following PLL settings are derived from the device configuration: Device Configuration and Start-Up Sequence 2 • • • • 1. fDAC = 1200 × 1 = 1200 MHz. fVCO= fDAC = 1200 MHz (1 GHz < fVCO < 2 GHz). VCO divider = fVCO/fDAC = 1. Loop divider = fDAC/fREF = 4. 2. 3. 4. Start-Up Sequence 1 1. 2. 3. 4. 5. Power up the device (no specific power supply sequence is required). Apply stable DAC clock. Apply stable DCI clock. Feed stable input data. Issue hardware reset (optional). Set fDCI = 200 MHz, fDATA = 400 MHz, fDAC = 800 MHz, and interpolation to 2×. Disable PLL. Enable the inverse sinc filter. Use the delay line-based interface mode with a delay setting of 0. Start-Up Sequence 2 1. Power up the device (no specific power supply sequence is required). Apply stable DAC clock. Apply stable DCI clock. Feed stable input data. Issue a hardware reset (optional). /* Device configuration register write sequence */ 2. 3. 4. 5. 0x00 → 0x20 /* Issue software reset */ /* Device configuration register write sequence */ /* Configure PLL */ 0x00 → 0x20 /* Issue software reset */ 0x20 → 0x01 /* Device Startup Configuration */ 0x14 → 0xE7 /* Configure PLL loop BW and charge pump current */ 0x15 → 0xC1 /* Configure VCO divider and loop divider */ 0x12 → 0xC0 /*Enable the PLL */ 0x20 → 0x01 /* Device Startup Configuration */ /* Configure Data Interface */ 0x5E → 0x00 /* Configure the delay setting */ 0x5F → 0x60 0x12 → 0x80 Wait 10ms 0x0D → 0x16 /* DC couple DCI */ Read 0x16[7] /* Expect 1b if the PLL is locked */ 0x0A → 0x00 /* Turn off DLL and duty cycle correction */ /* Configure Interpolation filter */ /* Configure Data Interface */ 0x28 → 0x00 /* 2× interpolation */ 0x5E → 0xFE /* Turn off LSB delay cell */ 0x0A → 0xC0 /* Enable the DLL and duty cycle correction. Set DLL phase offset to 0 */ Read 0x0E[7:4] /* Expect 1000b if the DLL is locked */ /* Reset FIFO */ Follow the serial port FIFO reset procedure in the FIFO Operation section. /* Enable Inverse SINC filter */ /* Configure Interpolation filter */ 0x28 → 0x80 /* 1× interpolation */ 0x27 → 0x80 /* Reset FIFO */ /* Power up DAC outputs */ 0x25 → 0x01 0x01 → 0x00 Rev. A | Page 39 of 56 AD9139 Data Sheet DEVICE CONFIGURATION REGISTER MAP AND DESCRIPTION Table 21. Device Configuration Register Map Reg 0x00 Name Common Bits [7:0] Bit 7 Reserved Bit 6 SPI_LSB_ FIRST Reserved Bit 5 DEVICE_RESET 0x01 PD_ CONTROL INTERRUPT_ ENABLE0 [7:0] PD_DAC [7:0] Reserved ENABLE_ SYNC_LOST ENABLE_ SYNC_DONE ENABLE_PLL_ LOST ENABLE_PLL_ LOCKED [7:0] ENABLE_ PARITY_FAIL ENABLE_SED_ FAIL ENABLE_ SYNC_ LOCKED ENABLE_DLL_ WARNING 0x04 INTERRUPT_ ENABLE1 ENABLE_DLL_ LOCKED Reserved ENABLE_FIFO_ UNDERFLOW 0x05 [7:0] Reserved SYNC_LOST SYNC_LOCKED SYNC_DONE PLL_LOST PLL_LOCKED [7:0] PARITY_ FAIL Reserved SED_FAIL Reserved 0x08 IRQ_SEL1 [7:0] 0x09 0x0A FRAME_MODE DATA_CNTR_0 [7:0] [7:0] DLL_ WARNING SEL_SYNC_ LOCKED SEL_DLL_ WARNING PARUSAGE DLL_LOCKED 0x07 INTERRUPT_ FLAG0 INTERRUPT_ FLAG1 IRQ_SEL0 0x0B 0x0C 0x0D DATA_CNTR_1 DATA_CNTR_2 DATA_CNTR_3 [7:0] [7:0] [7:0] 0x0E DATA_STAT_0 [7:0] 0x10 DACCLK_ [7:0] RECEIVER_ CTRL REFCLK_ [7:0] RECEIVER_CTRL DACCLK_ DUTYCYCLE_ CORRECTION DUTYCYCLE_ CORRECTION 0x12 PLL_CTRL0 [7:0] PLL_ENABLE 0x14 0x15 PLL_CTRL2 PLL_CTRL3 [7:0] [7:0] 0x16 0x17 0x18 0x19 PLL_STATUS0 PLL_STATUS1 DAC_FS_ADJ0 DAC_FS_ADJ1 [7:0] [7:0] [7:0] [7:0] PLL_LOCK 0x1C DIE_TEMP_ SENSOR_CTRL DIE_TEMP_LSB DIE_TEMP_MSB CHIP_ID INTERRUPT_ CONFIG SYNC_CTRL [7:0] Reserved FRAME_RST_ CTRL FIFO_LEVEL_ CONFIG FIFO_LEVEL_ READBACK FIFO_CTRL [7:0] 0x03 0x06 0x11 0x1D 0x1E 0x1F 0x20 0x21 0x22 0x23 0x24 0x25 0x26 0x27 DATA_ FORMAT_SEL DATAPATH_ CTRL [7:0] SEL_PARITY_ FAIL PD_DATARCV SEL_SYNC_ LOST SEL_SED_FAIL Reserved DUTY_ CORRECTION_ EN CLEAR_WARN Reserved DLL_WARN DLL_START_ WARNING DACCLK_ CROSSPOINT_ CTRL_ENABLE REFCLK_ CROSSPOINT_ CTRL_ENABLE Reserved Reserved Bit 3 Reserved SEL_SYNC_ DONE SEL_DLL_ LOCKED FRMUSAGE Reserved DLL_ ENABLE LOW_ DCI_EN DLL_LOCK Bit 4 AUTO_MANUAL_ SEL PLL_LOOP_BW DIGLOGIC_DIVIDER Reserved Bit 0 Reset RW 0x00 RW PD_DEVICE PD_DACCLK PD_FRAME 0xC0 RW 0x00 RW 0x00 RW 0x00 R 0x00 R 0x00 RW 0x00 RW 0x00 0x40 RW RW 0x39 0x64 0x06 RW RW RW 0x00 R 0xFF RW 0x5F RW 0x00 RW 0xE7 0xC9 RW RW 0x00 0x00 0xF9 0xE1 R R RW RW 0x02 RW 0x00 0x00 0x0A 0x00 R R R RW 0x00 RW 0x12 RW 0x40 RW 0x00 R 0x00 RW Reserved Reserved BG_TRIM 0x00 RW FS_CURRENT 0x00 RW DLL_ RUNNING REFCLK_CROSSPOINT_LEVEL PLL_CP_CURRENT VCO_DIVIDER ARM_FRAME [7:0] Reserved INTEGER_FIFO_LEVEL_REQUEST Reserved [7:0] Reserved INTEGER_FIFO_LEVEL_READBACK Reserved [7:0] LOOP_DIVIDER VCO_CTRL_VOLTAGE_READBACK PLL_BAND_READBACK DAC_FULLSCALE_ADJUST_LSB RESERVED DAC_FULLSCALE_ADJUST_ MSB REF_CURRENT DIE_TEMP_ SENSOR_EN DIE_TEMP_LSB DIE_TEMP_MSB CHIP_ID INTERRUPT_CONFIGURATION Reserved SYNC_CLK_ SYNC_ EDGE_SEL ENABLE FRAME_RESET_MODE EN_CON_ FRAME_RESET FRACTIONAL_FIFO_LEVEL_REQUEST FRACTIONAL_FIFO_LEVEL_READBACK Reserved FIFO_SPI_ RESET_ACK Reserved Reserved ENABLE_ Reserved FIFO_ OVERFLOW Reserved Reserved Reserved DC_COUPLE_ Reserved LOW_EN DLL_END_ Reserved DCI_ON Reserved WARNING DACCLK_CROSSPOINT_LEVEL Reserved DATA_ FORMAT INVSINC_ ENABLE Reserved FIFO_ FIFO_ Reserved UNDERFLOW OVERFLOW SEL_PLL_LOST SEL_PLL_ Reserved LOCKED Reserved FIFO_ FIFO_ Reserved UNDERFLOW OVERFLOW Reserved FRAME_PIN_USAGE DLL_PHASE_OFFSET CROSSPOINT_ CTRL_EN [7:0] [7:0] Bit 1 PLL_MANUAL_BAND [7:0] [7:0] [7:0] [7:0] [7:0] Bit 2 Reserved DIG_GAIN_ DCOFFSET_ ENABLE Rev. A | Page 40 of 56 Reserved FIFO_SPI_ RESET_ REQUEST DATA_BUS_ WIDTH Data Sheet AD9139 Reg 0x28 Name Bits INTERPOLATION_ [7:0] CTRL 0x39 LVDS_IN_PWR_ DOWN_0 DAC_DC_ OFFSET0 DAC_DC_ OFFSET1 DAC_DIG_GAIN GAIN_STEP_ CTRL0 GAIN_STEP_ CTRL1 TX_ENABLE_ CTRL [7:0] 0x44 DAC_ OUTPUT_ CTRL [7:0] 0x5E ENABLE_DLL_ DELAY_CELL0 ENABLE_DLL_ DELAY_CELL1 SED_CTRL SED_PATT_ L_S0 SED_PATT_ H_S0 SED_PATT_ L_S1 SED_PATT_ H_S1 SED_PATT_ L_S2 SED_PATT_ H_S2 SED_PATT_ L S3 SED_PATT_ H_S3 PARITY_CTRL [7:0] 0x3B 0x3C 0x3F 0x41 0x42 0x43 0x5F 0x60 0x61 0x62 0x63 0x64 0x65 0x66 0x67 0x68 0x6A 0x6B 0x6C 0x7F PARITY_ ERR_RISING PARITY_ ERR_FALLING Version Bit 7 Bit 6 INTERPOLATION_ MODE Bit 5 Bit 4 Bit 3 Bit 2 Reserved Bit 1 Bit 0 PWR_DOWN_DATA_INPUT_BITS Reset RW 0x00 RW 0x00 RW [7:0] DAC_DC_OFFSET_LSB 0x00 RW [7:0] DAC_DC_OFFSET_MSB 0x00 RW DAC_DIG_GAIN RAMP_UP_STEP 0x20 0x01 RW RW RAMP_DOWN_STEP 0x01 RW TXENABLE_ 0x07 POWER_ DOWN_EN FIFO_ 0x8F ERROR_ SHUTDOWN_ EN 0xFF RW [7:0] [7:0] [7:0] Reserved Reserved DAC_OUTPUT_ STATUS DAC_OUTPUT_ ON Reserved [7:0] DAC_OUTPUT_ CTRL_EN Reserved FIFO_WARNING_ SHUTDOWN_EN TXENABLE_ SLEEP_ EN Reserved ENABLE_DLL_DELAY_CELL[7:0] [7:0] [7:0] [7:0] TXENABLE_ GAINSTEP_ EN Reserved SED_ENABLE SED_ERR_CLEAR ENABLE_DLL_DELAY_CELL[10:8] AED_ENABLE SED_DEPTH Reserved SED_PATTERN_RISE_S0 [7:0] AED_PASS AED_FAIL SED_FAIL RW 0x67 RW 0x00 0x00 RW RW [7:0] SED_PATTERN_RISE_S0 [15:8] 0x00 RW [7:0] SED_PATTERN_FALL_S1 [7:0] 0x00 RW [7:0] SED_PATTERN_FALL_S1 [15:8] 0x00 RW [7:0] SED_PATTERN_RISE_S2 [7:0] 0x00 RW [7:0] SED_PATTERN_RISE_S2 [15:8] 0x00 RW [7:0] SED_PATTERN_FALL_S3 [7:0] 0x00 RW [7:0] SED_PATTERN_FALL_S3 [15:8] 0x00 RW 0x00 RW [7:0] PARITY_ENABLE PARITY_EVEN PARITY_ ERR_CLEAR Reserved PARERRFAL PARERRRIS [7:0] PARITY RISING EDGE ERROR COUNT 0x00 R [7:0] PARITY FALLING EDGE ERROR COUNT 0x00 R [7:0] Version 0x0B R Rev. A | Page 41 of 56 AD9139 Data Sheet SPI CONFIGURE REGISTER Address: 0x00, Reset: 0x00, Name: Common Table 22. Bit Descriptions for Common Bit No. 6 Bit Name SPI_LSB_FIRST Settings 0 1 5 DEVICE_RESET Description Serial port communication, MSB first or LSB first selection. MSB first. LSB first. The device resets when 1 is written to this bit. DEVICE_RESET is a self clear bit. After the reset, the bit returns to 0 automatically. The readback is always 0. Reset 0 Access R/W 0 R/W POWER-DOWN CONTROL REGISTER Address: 0x01, Reset: 0xC0, Name: PD_CONTROL Table 23. Bit Descriptions for PD_CONTROL Bit No. 7 Bit Name PD_DAC 6 5 Reserved PD_DATARCV 2 PD_DEVICE 1 PD_DACCLK 0 PD_FRAME Settings Description The DAC is powered down when PD_DAC is set to 1. This bit powers down only the analog portion of the DAC. The DAC digital data path is not affected. Must set to default value. The data interface circuitry is powered down when PD_DATARCV is set to 1. This bit powers down the data interface and the write side of the FIFO. The band gap circuitry is powered down when set to 1. This bit powers down the entire chip. The DAC clock powers down when PD_DEVICE is set to 1. This bit powers down the DAC clocking path and, thus, the majority of the digital functions. The frame receiver powers down when PD_FRAME is set to 1. The frame signal is internally pulled low. Set to 1 when frame is not used. Reset 1 Access R/W 1 0 R/W R/W 0 R/W 0 R/W 0 R/W INTERRUPT ENABLE 0 REGISTER Address: 0x03, Reset: 0x00, Name: INTERRUPT_ENABLE0 Table 24. Bit Descriptions for INTERRUPT_ENABLE0 Bit No. 6 5 4 3 2 Bit Name ENABLE_SYNC_LOST ENABLE_SYNC_LOCKED ENABLE_SYNC_DONE ENABLE_PLL_LOST ENABLE_PLL_LOCKED Settings Description Enable interrupt for sync lost. Enable interrupt for sync lock. Enable interrupt for sync done. Enable interrupt for PLL lost. Enable interrupt for PLL locked. Reset 0 0 0 0 0 Access R/W R/W R/W R/W R/W INTERRUPT ENABLE 1 REGISTER Address: 0x04, Reset: 0x00, Name: INTERRUPT_ENABLE1 Table 25. Bit Descriptions for INTERRUPT_ENABLE1 Bit No. 7 6 5 4 2 1 Bit Name ENABLE_PARITY_FAIL ENABLE_SED_FAIL ENABLE_DLL_WARNING ENABLE_DLL_LOCKED ENABLE_FIFO_UNDERFLOW ENABLE_FIFO_OVERFLOW Settings Description Enable interrupt for parity failure. Enable interrupt for SED failure. Enable interrupt for DLL warning. Enable interrupt for DLL locked. Enable interrupt for FIFO underflow. Enable interrupt for FIFO overflow. Rev. A | Page 42 of 56 Reset 0 0 0 0 0 0 Access R/W R/W R/W R/W R/W R/W Data Sheet AD9139 INTERRUPT FLAG 0 REGISTER Address: 0x05, Reset: 0x00, Name: INTERRUPT_FLAG0 Table 26. Bit Descriptions for INTERRUPT_FLAG0 Bit No. 6 5 4 3 2 Bit Name SYNC_LOST SYNC_LOCKED SYNC_DONE PLL_LOST PLL_LOCKED Settings Description SYNC_LOST is set to 1 when sync is lost. SYNC_LOCKED is set to 1 when sync is locked. SYNC_DONE is set to 1 when sync is done. PLL_LOST is set to 1 when PLL loses lock. PLL_LOCKED is set to 1 when PLL is locked. Reset 0 0 0 0 0 Access R R R R R Reset 0 0 0 0 0 Access R R R R R 0 R INTERRUPT FLAG 1 REGISTER Address: 0x06, Reset: 0x00, Name: INTERRUPT_FLAG1 Table 27. Bit Descriptions for INTERRUPT_FLAG1 Bit No. 7 6 5 4 2 Bit Name PARITY_FAIL SED_FAIL DLL_WARNING DLL_LOCKED FIFO_UNDERFLOW 1 FIFO_OVERFLOW Settings Description PARITY_FAIL is set to 1 when the parity check fails. SED_FAIL is set to 1 when the SED comparison fails. DLL_WARNING is set to 1 when the DLL raises a warning. DLL_LOCKED is set to 1 when the DLL is locked. FIFO_UNDERFLOW is set to 1 when the FIFO read pointer catches the FIFO write pointer. FIFO_OVERFLOW is set to 1 when the FIFO write pointer catches the FIFO read pointer. INTERRUPT SELECT 0 REGISTER Address: 0x07, Reset: 0x00, Name: IRQ_SEL0 Table 28. Bit Descriptions for IRQ_SEL0 Bit No. 6 Bit Name SEL_SYNC_LOST 5 Settings 0 1 Description Selects the IRQ1 pin. Selects the IRQ2 pin. Reset 0 Access R/W SEL_SYNC_LOCKED 0 1 Selects the IRQ1 pin. Selects the IRQ2 pin. 0 R/W 4 SEL_SYNC_DONE 0 1 Selects the IRQ1 pin. Selects the IRQ2 pin. 0 R/W 3 SEL_PLL_LOST 0 1 Selects the IRQ1 pin. Selects the IRQ2 pin. 0 R/W 2 SEL_PLL_LOCKED 0 1 Selects the IRQ1 pin. Selects the IRQ2 pin. 0 R/W Rev. A | Page 43 of 56 AD9139 Data Sheet INTERRUPT SELECT 1 REGISTER Address: 0x08, Reset: 0x00, Name: IRQ_SEL1 Table 29. Bit Descriptions for IRQ_SEL1 Bit No. 7 Bit Name SEL_PARITY_FAIL 6 Settings 1 0 Description Selects the IRQ2 pin. Selects the IRQ1 pin. Reset Access SEL_SED_FAIL 1 0 Selects the IRQ2 pin. Selects the IRQ1 pin. 0 R/W 5 SEL_DLL_WARNING 0 Selects the IRQ1 pin. 0 R/W 0 R/W 4 SEL_DLL_LOCKED 1 0 Selects the IRQ2 pin. Selects the IRQ1 pin. 2 SEL_FIFO_UNDERFLOW 0 R/W 1 0 Selects the IRQ2 pin. Selects the IRQ1 pin. 1 SEL_FIFO_OVERFLOW 0 R/W 1 0 Selects the IRQ2 pin. Selects the IRQ1 pin. 0 R/W FRAME MODE REGISTER Address: 0x09, Reset: 0x00, Name: FRAME_MODE Table 30. Bit Descriptions for FRAME_MODE Bit No. 5 4 [1:0] Bit Name PARUSAGE FRMUSAGE FRAME_PIN_USAGE Description Must be set to 1 when parity is used. Must be set to 1 when frame is used. 0 = no effect. 1 = parity. 2 = frame. 3 = reserved. Reset 0 0 0x0 Access R/W R/W R/W DATA CONTROL 0 REGISTER Address: 0x0A, Reset: 0x40, Name: DATA_CNTR_0 Table 31. Bit Descriptions for DATA_CNTR_0 Bit No. 7 Bit Name DLL_ENABLE 6 DUTY_CORRECTION_EN [3:0] DLL_PHASE_OFFSET Description 1 = enable DLL. 0 = disable DLL. 1 = enable duty cycle correction. 0 = disable duty cycle correction. Locked phase = 90° + n × 11.25°, where n is the 4-bit signed magnitude number. Reset 0 Access R/W 1 R/W 0x0 R/W DATA CONTROL 1 REGISTER Address: 0x0B, Reset: 0x39, Name: DATA_CNTR_1 Table 32. Bit Descriptions for DATA_CNTR_1 Bit No. 7 [6:0] Bit Name CLEAR_WARN Reserved Description 1: clears data receiver warning bits (Register 0x0E[6:4]). Must write the default value for optimal performance. Rev. A | Page 44 of 56 Reset 0 0x39 Access R/W R/W Data Sheet AD9139 DATA CONTROL 2 REGISTER Address: 0x0C, Reset: 0x64, Name: DATA_CNTR_2 Table 33. Bit Descriptions for DATA_CNTR_2 Bit No. [7:0] Bit Name Reserved Description Must write the default value for optimal performance. Reset 0x64 Access R/W DATA CONTROL 3 REGISTER Address: 0x0D, Reset: 0x06, Name: DATA_CNTR_3 Table 34. Bit Descriptions for DATA_CNTR_3 Bit No. 7 Bit Name LOW_DCI_EN 4 DC_COUPLE_LOW_EN [3:0] Reserved Description Set to 0 when the DLL is enabled and the DCI rate ≥350 MHz. Set to 1 when the DLL is enabled and the DCI rate <350 MHz. Set to 0 when the DLL is enabled and the delay line is disabled. Set to 1 when the DLL is disabled and the delay line is enabled. It is recommended that DLL mode be used for DCI rates faster than 250 MHz and delay line mode be used for DCI rates slower than 250 MHz. Must write the default value for optimal performance. Reset 0 Access R/W 0 R/W 0x6 R/W DATA STATUS 0 REGISTER Address: 0x0E, Reset: 0x00, Name: DATA_STAT_0 Table 35. Bit Descriptions for DATA_STAT_0 Bit No. 7 6 5 4 3 2 1 0 Bit Name DLL_LOCK DLL_WARN DLL_START_WARNING DLL_END_WARNING Reserved DCI_ON Reserved DLL_RUNNING Description 1 = DLL lock. 1 = DLL near the beginning/end of the delay line. 1 = DLL at the beginning of the delay line. 1 = DLL at the end of the delay line. Reserved. 1 = user has provided a DCI clock. Reserved. 1 = closed-loop DLL attempting to lock. 0 = delay fixed at middle of the delay line. Rev. A | Page 45 of 56 Reset 0 0 0 0 0 0 0 0 Access R R R R R R R R AD9139 Data Sheet DAC CLOCK RECEIVER CONTROL REGISTER Address: 0x10, Reset: 0xFF, Name: DACCLK_RECEIVER_CTRL Table 36. Bit Descriptions for DACCLK_RECEIVER_CTRL Bit No. 7 Bit Name DACCLK_DUTYCYCLE_CORRECTION 6 5 Reserved DACCLK_CROSSPOINT_CTRL_ENABLE [4:0] DACCLK_CROSSPOINT_LEVEL Settings 01111 11111 Description Enables duty cycle correction at the DACCLK input. For best performance, the default and recommended status is turned on. Must write the default value for optimal performance Enables crosspoint control at the DACCLK input. For best performance, the default and recommended status is turned on. A twos complement value. For best performance, set the DACCLK_CROSSPOINT_LEVEL to the default value. Highest crosspoint. Lowest crosspoint. Reset 1 Access R/W 1 1 R/W R/W 0x1F R/W Reset 0 Access RW 1 0 R/W RW 0x1F RW Reset 0 0 Access R/W R/W 0x00 R/W REFERENCE CLOCK RECEIVER CONTROL REGISTER Address: 0x11, Reset: 0x5F, Name: REFCLK_RECEIVER_CTRL Table 37. Bit Descriptions for REFCLK_RECEIVER_CTRL Bit No. 7 Bit Name DUTYCYCLE_CORRECTION 6 5 Reserved REFCLK_CROSSPOINT_CTRL_ENABLE [4:0] REFCLK_CROSSPOINT_LEVEL Settings 01111 11111 Description Enables duty cycle correction at the REFCLK input. For best performance, the default and recommended status is turned off. Must write the default value for optimal performance. Enables crosspoint control at the REFCLK input. For best performance, the default and recommended status is turned off. A twos complement value. For best performance, set REFCLK_CROSSPOINT_LEVEL to the default value. Highest crosspoint. Lowest crosspoint. PLL CONTROL 0 REGISTER Address: 0x12, Reset: 0x00, Name: PLL_CTRL0 Table 38. Bit Descriptions for PLL_CTRL0 Bit No. 7 6 Bit Name PLL_ENABLE AUTO_MANUAL_SEL Settings 0 1 [5:0] PLL_MANUAL_BAND 000000 111111 Description Enables PLL clock multiplier. PLL band selection mode. Automatic mode. Manual mode. PLL band setting in manual mode. 64 bands in total, covering a 1 GHz to 2.1 GHz VCO range. Lowest band (1.03 GHz). Highest band (2.07 GHz). Rev. A | Page 46 of 56 Data Sheet AD9139 PLL CONTROL 2 REGISTER Address: 0x14, Reset: 0xE7, Name: PLL_CTRL2 Table 39. Bit Descriptions for PLL_CTRL2 Bit No. [7:5] Bit Name PLL_LOOP_BW Settings Description Selects the PLL loop filter bandwidth. The default and recommended setting is 111 for optimal PLL performance. Lowest setting. Highest setting. Sets nominal PLL charge pump current. The default and recommended setting is 00111 for optimal PLL performance. Lowest setting. Highest setting. 0x00 0x1F [4:0] PLL_CP_CURRENT 0x00 0x1F Reset 0x7 Access R/W 0x07 R/W PLL CONTROL 3 REGISTER Address: 0x15, Reset: 0xC9, Name: PLL_CTRL3 Table 40. Bit Descriptions for PLL_CTRL3 Bit No. [7:6] Bit Name DIGLOGIC_DIVIDER Settings 00 01 10 11 4 CROSSPOINT_CTRL_EN [3:2] VCO_DIVIDER 00 01 10 11 [1:0] LOOP_DIVIDER 00 01 10 11 Description REFCLKx to PLL digital clock divide ratio. The PLL digital clock drives the internal PLL logics. The divide ratio must be set to ensure that the PLL digital clock is below 75 MHz. fREFCLK/fDIG = 2. fREFCLK/fDIG = 4. fREFCLK/fDIG = 8. fREFCLK/fDIG = 16. Enable loop divider crosspoint control. The default and recommended setting is set to 0 for optimal PLL performance. PLL VCO divider. This divider determines the ratio of the VCO frequency to the DACCLK frequency. fVCO/fDACCLK = 1. fVCO/fDACCLK = 2. fVCO/fDACCLK = 4. fVCO/fDACCLK = 4. PLL loop divider. This divider determines the ratio of the DACCLK frequency to the REFCLK frequency. fDACCLK/fREFCLK = 2. fDACCLK/fREFCLK = 4. fDACCLK/fREFCLK = 8. fDACCLK/fREFCLK = 16. Reset 0x3 Access R/W 0 R/W 0x2 R/W 0x1 R/W PLL STATUS 0 REGISTER Address: 0x16, Reset: 0x00, Name: PLL_STATUS0 Table 41. Bit Descriptions for PLL_STATUS0 Bit No. 7 [3:0] Bit Name PLL_LOCK VCO_CTRL_VOLTAGE_READBACK Settings 1111 0111 0000 Description PLL clock multiplier output is stable. VCO control voltage readback. A binary value. The highest VCO control voltage. The midvalue when a proper VCO band is selected. When the PLL is locked, selecting a higher VCO band decreases this value and selecting a lower VCO band increases this value. The lowest VCO control voltage. Rev. A | Page 47 of 56 Reset 0 0x0 Access R R AD9139 Data Sheet PLL STATUS 1 REGISTER Address: 0x17, Reset: 0x00, Name: PLL_STATUS1 Table 42. Bit Descriptions for PLL_STATUS1 Bit No. [5:0] Bit Name PLL_BAND_READBACK Settings Description Indicates the VCO band that is currently selected. Reset 0x00 Access R Description See Register 0x19. Reset 0xF9 Access R/W Description Bandgap trim code. Set to the default value for optimal performance. DAC full-scale adjust, Bits[9:0] sets the full-scale current of the DAC. The full-scale current can be adjusted from 8.64 mA to 31.68 mA. The default value (0x1F9) sets the full-scale current to 20 mA. Reset 0x7 Access R/W 0x1 R/W DAC FS ADJUST LSB REGISTER Address: 0x18, Reset: 0xF9, Name: DAC_FS_ADJ0 Table 43. Bit Descriptions for DAC_FS_ADJ0 Bit No. [7:0] Bit Name DAC_FULLSCALE_ADJUST_LSB Settings DAC FS ADJUST MSB REGISTER Address: 0x19, Reset: 0xE1, Name: DAC_FS_ADJ1 Table 44. Bit Descriptions for DAC_FS_ADJ1 Bit No. [7:5] Bit Name BG_TRIM [1:0] DAC_FULLSCALE_ADJUST_MSB Settings DIE TEMPERATURE SENSOR CONTROL REGISTER Address: 0x1C, Reset: 0x02, Name: DIE_TEMP_SENSOR_CTRL Table 45. Bit Descriptions for DIE_TEMP_SENSOR_CTRL Bit No. [6:4] Bit Name FS_CURRENT Settings 000 001 … 110 111 [3:1] REF_CURRENT 000 001 … 110 111 0 DIE_TEMP_SENSOR_EN Description Temperature sensor ADC full-scale current. Using the default setting is recommended. 50 μA. 62.5 μA. … 125 μA. 137.5 μA. Temperature sensor ADC reference current. Using the default setting is recommended. 12.5 μA. 19 μA. … 50 μA. 56.5 μA. Enable the on-chip temperature sensor. Reset 0x0 Access R/W 0x1 R/W 0x0 R/W Description This register is used together with Register 0x1E. Reset 0x00 Access R DIE TEMPERATURE LSB REGISTER Address: 0x1D, Reset: 0x00, Name: DIE_TEMP_LSB Table 46. Bit Descriptions for DIE_TEMP_LSB Bit No. [7:0] Bit Name DIE_TEMP_LSB Settings Rev. A | Page 48 of 56 Data Sheet AD9139 DIE TEMPERATURE MSB REGISTER Address: 0x1E, Reset: 0x00, Name: DIE_TEMP_MSB Table 47. Bit Descriptions for DIE_TEMP_MSB Bit No. [7:0] Bit Name DIE_TEMP_MSB Settings Description Die temperature, Bits[15:0] indicate the approximate die temperature. For more information, see the Temperature Sensor section. Reset 0x00 Access R CHIP ID REGISTER Address: 0x1F, Reset: 0x0A, Name: CHIP_ID Table 48. Bit Descriptions for CHIP_ID Bit No. [7:0] Bit Name CHIP_ID Settings Description The AD9139 chip ID is 0x0A. Reset 0x0A Access R Reset 0x00 Access R/W INTERRUPT CONFIGURATION REGISTER Address: 0x20, Reset: 0x00, Name: INTERRUPT_CONFIG Table 49. Bit Descriptions for INTERRUPT_CONFIG Bit No. [7:0] Bit Name INTERRUPT_CONFIGURATION Settings 0x00 0x01 Description Test mode. Recommended mode (described in the Interrupt Request Operation section). SYNC CONTROL REGISTER Address: 0x21, Reset: 0x00, Name: SYNC_CTRL Table 50. Bit Descriptions for SYNC_CTRL Bit No. 1 Bit Name SYNC_CLK_EDGE_SEL Settings 0 1 0 SYNC_ENABLE Description Selects the sampling edge of the DACCLK on the sync clock. SYNC CLK is sampled by rising edges of DACCLK. SYNC CLK is sampled by falling edges of DACCLK. Enables multichip synchronization. Reset 0 Access R/W 0 R/W FRAME RESET CONTROL REGISTER Address: 0x22, Reset: 0x12, Name: FRAME_RST_CTRL Table 51. Bit Descriptions for FRAME_RST_CTRL Bit No. 3 Bit Name ARM_FRAME 2 EN_CON_FRAME_RESET Settings 0 1 [1:0] FRAME_RESET_MODE 10 11 Description This bit is used to retrigger a frame reset in one shot mode (when Bit 2 is set to 0). Setting this bit to 1 requests that the device respond to the next valid frame pulse. Frame reset mode selection. Responds to the first valid frame pulse and resets the FIFO one time only. This is the default and recommended mode. Responds to every valid frame pulse and resets the FIFO continuously. These bits determine what is to be reset when the device receives a valid frame signal. FIFO. None. Rev. A | Page 49 of 56 Reset 0 Access R/W 0 R/W 0x2 R/W AD9139 Data Sheet FIFO LEVEL CONFIGURATION REGISTER Address: 0x23, Reset: 0x40, Name: FIFO_LEVEL_CONFIG Table 52. Bit Descriptions for FIFO_LEVEL_CONFIG Bit No. [6:4] Bit Name INTEGER_FIFO_LEVEL_REQUEST Settings Description Set the integer FIFO level. This is the difference between the read pointer and the write pointer values in the unit of input data rate (fDATA). The default and recommended FIFO level is integer level = 4 and fractional level = 0. See the FIFO Operation section for details. 0 1 … 7 Set the fractional FIFO level. This is the difference between the read pointer and the write pointer values in the unit of DACCLK rate (FDAC). The maximum allowed setting value = interpolation rate − 1. See the FIFO Operation section for details. 0 1 000 001 … 111 [2:0] FRACTIONAL_FIFO_LEVEL_REQUEST 000 001 Reset 0x4 Access R/W 0x0 R/W Reset 0x0 Access R 0x0 R FIFO LEVEL READBACK REGISTER Address: 0x24, Reset: 0x00, Name: FIFO_LEVEL_READBACK Table 53. Bit Descriptions for FIFO_LEVEL_READBACK Bit No. [6:4] Bit Name INTEGER_FIFO_LEVEL_READBACK Settings [2:0] FRACTIONAL_FIFO_LEVEL_READBACK Description The integer FIFO level read back. The difference between the overall FIFO level request and readback is within two DACCLK cycles. See the FIFO Operation section for details. The fractional FIFO level read back. This value is used in combination with the readback in Bit[6:4]. FIFO CONTROL REGISTER Address: 0x25, Reset: 0x00, Name: FIFO_CTRL Table 54. Bit Descriptions for FIFO_CTRL Bit No. 1 0 Bit Name FIFO_SPI_RESET_ACK FIFO_SPI_RESET_REQUEST Settings Description Acknowledge a serial port initialized FIFO reset. Initialize a FIFO reset via the serial port. Rev. A | Page 50 of 56 Reset 0x0 0x0 Access R R/W Data Sheet AD9139 DATA FORMAT SELECT REGISTER Address: 0x26, Reset: 0x00, Name: DATA_FORMAT_SEL Table 55. Bit Descriptions for DATA_FORMAT_SEL Bit No. 7 Bit Name DATA_FORMAT Settings 0 1 0 DATA_BUS_WIDTH 0 1 Description Select binary or twos complement data format. Input data in twos complement format. Input data in binary format. Data interface mode. See the LVDS Input Data Ports section for information about the operation of the different interface modes. Word mode; 16-bit interface bus width. Byte mode; 8-bit interface bus width. Reset 0 Access R/W 0 R/W DATAPATH CONTROL REGISTER Address: 0x27, Reset: 0x00, Name: DATAPATH_CTRL Table 56. Bit Descriptions for DATAPATH_CTRL Bit No. 7 5 Bit Name INVSINC_ENABLE DIG_GAIN_DCOFFSET_ENABLE Settings Description Enable the inverse sinc filter. Enable digital gain adjustment and dc offset. Reset 0 0 Access RW RW INTERPOLATION CONTROL REGISTER Address: 0x28, Reset: 0x00, Name: INTERPOLATION_CTRL Table 57. Bit Descriptions for INTERPOLATION_CTRL Bit No. 7 Bit Name INTERPOLATION_MODE Settings Description Interpolation mode selection. 2× mode. 1× mode. 0 1 Reset 0x0 Access RW POWER-DOWN DATA INPUT 0 REGISTER Address: 0x39, Reset: 0x00, Name: LVDS_IN_PWR_DOWN_0 Table 58. Bit Descriptions for LVDS_IN_PWR_DOWN_0 Bit No. [3:0] Bit Name PWR_DOWN_DATA_INPUT_BITS Settings Description Powers down Data Input Bits[3:0]. Each bit controls one data input bit. These bits can be powered down individually. Reset 0x0 Access R/W Reset 0x00 Access RW Reset 0x00 Access RW DAC DC OFFSET 0 REGISTER Address: 0x3B, Reset: 0x00, Name: DAC_DC_OFFSET0 Table 59. Bit Descriptions for DAC_DC_OFFSET0 Bit No. [7:0] Bit Name DAC_DC_OFFSET_LSB Settings Description See Register 0x3C. DAC DC OFFSET 1 REGISTER Address: 0x3C, Reset: 0x00, Name: DAC_DC_OFFSET1 Table 60. Bit Descriptions for DAC_DC_OFFSET1 Bit No. [7:0] Bit Name DAC_DC_OFFSET_MSB Settings Description DAC DC offset, Bits[15:0], is a dc value that is added directly to the sample values written to the DAC. Rev. A | Page 51 of 56 AD9139 Data Sheet DAC GAIN ADJ REGISTER Address: 0x3F, Reset: 0x20, Name: DAC_DIG_GAIN Table 61. Bit Descriptions for DAC_GAIN_ADJ Bit No. [5:0] Bit Name DAC_DIG_GAIN Settings Description This register is the 6-bit digital gain adjust. The bit weighting is MSB = 20, LSB = 2−5, which yields a multiplier range of 0 to 2 or −∞ to 6 dB. The default gain setting is 0x20, which maps to unity gain (0 dB). Reset 0x20 Access RW Reset 0x01 Access RW Reset 0x0 Access RW 0x0 R 0x01 RW GAIN STEP CONTROL 0 REGISTER Address: 0x41, Reset: 0x01, Name: GAIN_STEP_CTRL0 Table 62. Bit Descriptions for GAIN_STEP_CTRL0 Bit No. [5:0] Bit Name RAMP_UP_STEP Settings Description This register sets the step size of the increasing gain. The digital gain increases by the configured amount in every four DAC cycles until the gain reaches the setting in DAC_GAIN_ADJ (Register 0x3F). The bit weighting is MSB = 21, LSB = 2−4. Note that the value in this register must not be greater than the values in the DAC_GAIN_ADJ. GAIN STEP CONTROL 1 REGISTER Address: 0x42, Reset: 0x01, Name: GAIN_STEP_CTRL1 Table 63. Bit Descriptions for GAIN_STEP_CTRL1 Bit No. 7 Bit Name DAC_OUTPUT_STATUS 6 DAC_OUTPUT_ON [5:0] RAMP_DOWN_STEP Settings Description This bit indicates the DAC output on/off status. When the DAC output is automatically turned off, this bit is 1. In the case where the DAC output is automatically turned off in the Tx enable mode, this register allows for turning on the DAC output manually. It is a self clear bit. This register sets the step size of the decreasing gain. The digital gain decreases by the configured amount in every four DAC cycles until the gain reaches zero. The bit weighting is MSB = 21, LSB = 2−4. Note that the value in this register must not be greater than the values in the DAC_GAIN_ADJ (Register 0x3F). TX ENABLE CONTROL REGISTER Address: 0x43, Reset: 0x07, Name: TX_ENABLE_CTRL Table 64. Bit Descriptions for TX_ENABLE_CTRL Bit No. 2 Bit Name TXENABLE_GAINSTEP_EN 1 TXENABLE_SLEEP_EN 0 TXENABLE_POWER_DOWN_EN Settings Description DAC output gradually turns on/off under the control of the TXENABLE signal from the TXEN pin according to the settings in Register 0x41 and Register 0x42. When set to 1, the device enters sleep mode when the TXENABLE signal from the TXEN pin is low. When set to 1, the device enters power-down mode when the TXENABLE signal from the TXEN pin is low. Rev. A | Page 52 of 56 Reset 1 Access RW 1 RW 1 RW Data Sheet AD9139 DAC OUTPUT CONTROL REGISTER Address: 0x44, Reset: 0x8F, Name: DAC_OUTPUT_CTRL Table 65. Bit Descriptions for DAC_OUTPUT_CTRL Bit No. 7 Bit Name DAC_OUTPUT_CTRL_EN Settings 3 FIFO_WARNING_SHUTDOWN_EN 0 FIFO_ERROR_SHUTDOWN_EN Description Enable the DAC output control. This bit needs to be set to 1 to enable the rest of the bits in this register. When this bit and Bit 7 are both high, if a FIFO warning occurs, the DAC output shuts down automatically. By default, this function is on. The DAC output is turned off when the FIFO reports warnings. Reset 0x1 Access RW 0x1 RW 0x1 RW Reset 0xFF Access RW DLL CELL ENABLE 0 REGISTER Address: 0x5E, Reset: 0xFF, Name: ENABLE_DLL_DELAY_CELL0 Table 66. Bit Descriptions for ENABLE_DLL_DELAY_CELL0 Bit No. [7:0] Bit Name DELAY_CELL_ENABLE [7:0] Description Set each bit to enable or disable the delay cell. Delay cell number corresponds to bit number. 1 = enable delay cell (default). 0 = disable delay cell. Different recommended values should be used in DLL mode and delay line mode. See the DLL Interface Mode section. DLL CELL ENABLE 1 REGISTER Address: 0x5F, Reset: 0x67, Name: ENABLE_DLL_DELAY_CELL1 Table 67. Bit Descriptions for ENABLE_DLL_DELAY_CELL1 Bit No. [7:3] [2:0] Bit Name Reserved DELAY_CELL_ENABLE [10:8] Description Must write the default value for optimal performance. Set each bit to enable or disable the delay cell. Delay cell numbers are (10, 9, 8) corresponding to bits (2, 1, 0). 1 = enable delay cell (default). 0 = disable delay cell. Reset 0x0C 0x7 Access RW RW Reset 0 0 0 0 0 0 0 0 Access RW RW RW RW R RW R R SED CONTROL REGISTER Address: 0x60, Reset: 0x00, Name: SED_CTRL Table 68. Bit Descriptions for SED_CTRL Bit No. 7 6 5 4 3 2 1 0 Bit Name SED_ENABLE SED_ERR_CLEAR AED_ENABLE SED_DEPTH Reserved AED_PASS AED_FAIL SED_FAIL Description Set to 1 to enable the SED compare logic. When 1, clears all SED reported error bits, Bit 2, Bit 1, and Bit 0. When 1, enables the AED function (SED with autoclear after eight passing sets). 0 = SED depth of two words, 1 = SED depth of four words. Reserved. When AED = 1, it signals eight true compare cycles. When AED = 1, it signals a mismatch in comparison. Signals that an SED mismatch in comparison occurred (with SED or AED enabled). Rev. A | Page 53 of 56 AD9139 Data Sheet SED PATTERN S0 LOW BITS REGISTER Address: 0x61, Reset: 0x00, Name: SED_PATT_L_S0 Table 69. Bit Descriptions for SED_PATT_L_S0 Bit No. [7:0] Bit Name SED_PATTERN_RISE_S0 [7:0] Description SED S0 rising edge low bits. Reset 0x00 Access RW Description SED S0 rising edge high bits. Reset 0x00 Access RW Description SED S1 falling edge low bits. Reset 0x00 Access RW Description SED S1 falling edge high bits. Reset 0x00 Access RW SED PATTERN S0 HIGH BITS REGISTER Address: 0x62, Reset: 0x00, Name: SED_PATT_H_S0 Table 70. Bit Descriptions for SED_PATT_H_S0 Bit No. [7:0] Bit Name SED_PATTERN_RISE_S0 [15:8] SED PATTERN S1 LOW BITS REGISTER Address: 0x63, Reset: 0x00, Name: SED_PATT_L_S1 Table 71. Bit Descriptions for SED_PATT_L_S1 Bit No. [7:0] Bit Name SED_PATTERN_FALL_S1 [7:0] SED PATTERN S1 HIGH BITS REGISTER Address: 0x64, Reset: 0x00, Name: SED_PATT_H_S1 Table 72. Bit Descriptions for SED_PATT_H_S1 Bit No. [7:0] Bit Name SED_PATTERN_FALL_S1 [15:8] SED PATTERN S2 LOW BITS REGISTER Address: 0x65, Reset: 0x00, Name: SED_PATT_L_S2 Table 73. Bit Descriptions for SED_PATT_L_S2 Bit No. [7:0] Bit Name SED_PATTERN_RISE_S2 [7:0] Description SED S2 rising edge low bits. Reset 0x00 Access RW Description SED S2 rising edge high bits. Reset 0x00 Access RW Description SED S3 falling edge low bits. Reset 0x00 Access RW SED PATTERN S2 HIGH BITS REGISTER Address: 0x66, Reset: 0x00, Name: SED_PATT_H_S2 Table 74. Bit Descriptions for SED_PATT_H_S2 Bit No. [2:0] Bit Name SED_PATTERN_RISE_S2 [15:8] SED PATTERN S3 LOW BITS REGISTER Address: 0x67, Reset: 0x00, Name: SED_PATT_L_S3 Table 75. Bit Descriptions for SED_PATT_L_S3 Bit No. [7:0] Bit Name SED_PATTERN_FALL_S3 [7:0] Rev. A | Page 54 of 56 Data Sheet AD9139 SED PATTERN S3 HIGH BITS REGISTER Address: 0x68, Reset: 0x00, Name: SED_PATT_H_S3 Table 76. Bit Descriptions for SED_PATT_H_S3 Bit No. [2:0] Bit Name SED_PATTERN_FALL_S3 [15:8] Description SED S3 falling edge high bits. Reset 0x00 Access RW PARITY CONTROL REGISTER Address: 0x6A, Reset: 0x00, Name: PARITY_CTRL Table 77. Bit Descriptions for PARITY_CTRL Bit No. 7 6 Bit Name PARITY_ENABLE PARITY_EVEN 5 [4:2] 1 0 PARITY_ERR_CLEAR Reserved PARERRFAL PARERRRIS Settings 1 0 1 Description Enable parity. Odd parity. Even parity. Set to 1 to clear parity error counters. Reserved. When 1, signals a falling edge parity error was detected. When 1, signals a rising edge parity error was detected. Reset 0 0 Access RW RW 0 0x0 0 0 RW R R R Reset 0x00 Access R Reset 0x00 Access R PARITY ERROR RISING EDGE REGISTER Address: 0x6B, Reset: 0x00, Name: PARITY_ERR_RISING Table 78. Bit Descriptions for PARITY_ERR_RISING Bit No. [7:0] Bit Name PARITY RISING EDGE ERROR COUNT Description Number of rising edge-based errors detected (S0 and S2). Clipped to 256. PARITY ERROR FALLING EDGE REGISTER Address: 0x6C, Reset: 0x00, Name: PARITY_ERR_FALLING Table 79. Bit Descriptions for PARITY_ERR_FALLING Bit No. [7:0] Bit Name PARITY FALLING EDGE ERROR COUNT Description Number of falling edge-based errors detected (S1 and S3). Clipped to 256. VERSION REGISTER Address: 0x7F, Reset: 0x0B, Name: Version Table 80. Bit Descriptions for Version Bit No. [7:0] Bit Name Version Settings Description Chip version Rev. A | Page 55 of 56 Reset 0x0B Access R AD9139 Data Sheet PACKAGING AND ORDERING INFORMATION OUTLINE DIMENSIONS 10.10 10.00 SQ 9.90 0.60 0.42 0.24 0.60 0.42 0.24 0.30 0.23 0.18 55 54 72 1 PIN 1 INDICATOR PIN 1 INDICATOR 9.85 9.75 SQ 9.65 0.50 BSC 0.50 0.40 0.30 18 37 BOTTOM VIEW 0.80 MAX 0.65 TYP 0.05 MAX 0.02 NOM COPLANARITY 0.08 0.20 REF SEATING PLANE 0.25 MIN 8.50 REF FOR PROPER CONNECTION OF THE EXPOSED PAD, REFER TO THE PIN CONFIGURATION AND FUNCTION DESCRIPTIONS SECTION OF THIS DATA SHEET. COMPLIANT TO JEDEC STANDARDS MO-220-VNND-4 06-25-2012-A 1.00 0.85 0.80 19 36 TOP VIEW 12° MAX 6.15 6.00 SQ 5.85 EXPOSED PAD Figure 51. 72-Lead Lead Frame Chip Scale Package [LFCSP_VQ] 10 mm × 10 mm Body, Very Thin Quad (CP-72-7) Dimensions shown in millimeters ORDERING GUIDE Model 1 AD9139BCPZ AD9139BCPZRL AD9139-EBZ AD9139-DUAL-EBZ 1 Temperature Range −40°C to +85°C −40°C to +85°C Package Description 72-lead LFCSP_VQ 72-lead LFCSP_VQ Evaluation Board for Single AD9139 Evaluation Evaluation Board for Dual AD9139 Evaluation Z = RoHS Compliant Part. ©2013–2014 Analog Devices, Inc. All rights reserved. Trademarks and registered trademarks are the property of their respective owners. D11744-0-3/14(A) Rev. A | Page 56 of 56 Package Option CP-72-7 CP-72-7