PHILIPS PCF50732

INTEGRATED CIRCUITS
DATA SHEET
PCF50732
Baseband and audio interface for
GSM
Objective specification
File under Integrated Circuits, IC17
1999 May 03
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
CONTENTS
PCF50732
14
LIMITING VALUES
15
THERMAL CHARACTERISTICS
16
DC CHARACTERISTICS
17
AC CHARACTERISTICS
18
FUNCTIONAL CHARACTERISTICS
18.1
18.2
18.3
18.4
18.5
18.6
18.7
18.8
Baseband transmit (BSI to TXI/Q)
Baseband receive (RXI/Q to BSI)
Voice band transmit (microphone to ASI)
Voice band receive (ASI to earphone)
Auxiliary digital-to-analog converters
Auxiliary analog-to-digital converters:
AUXADC1, AUXADC2, AUXADC3 and
AUXADC4
Typical total current consumption
Typical output loads
19
APPLICATION INFORMATION
19.1
19.2
Wake-up procedure from Sleep mode
Microphone input connection and test set-up
20
PACKAGE OUTLINES
21
SOLDERING
21.1
Introduction to soldering surface mount
packages
Reflow soldering
Wave soldering
Manual soldering
Suitability of surface mount IC packages for
wave and reflow soldering methods
1
FEATURES
2
APPLICATIONS
3
GENERAL DESCRIPTION
4
ORDERING INFORMATION
5
QUICK REFERENCE DATA
6
BLOCK DIAGRAM
7
PINNING
8
FUNCTIONAL DESCRIPTION
8.1
8.2
General
Baseband and voice band reference voltages
9
BASEBAND CODEC
9.1
9.2
9.3
Baseband transmit path
Baseband receive path
Baseband Serial Interface (BSI)
10
VOICE BAND CODEC
10.1
10.2
10.3
Voice band receive path
Voice band transmit path
Voice band digital circuitry
11
AUXILIARY FUNCTIONS
11.1
11.2
11.3
11.4
Automatic Gain Control (AGC): AUXDAC1
Automatic Frequency Control (AFC):
AUXDAC2
Power ramping: AUXDAC3
Auxiliary analog-to-digital converter (AUXADC)
21.2
21.3
21.4
21.5
12
CONTROL SERIAL INTERFACE (CSI)
22
DEFINITIONS
12.1
12.2
23
LIFE SUPPORT APPLICATIONS
12.3
The serial interface
Control Serial Interface (CSI) timing
characteristics
Control register block
13
VOICE BAND SIGNAL PROCESSOR (VSP)
13.1
13.2
13.3
13.4
Hardware description
VSP assembler language
Descriptions of the VSP instruction set
The assembler/emulator
1999 May 03
2
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
1
• The digital Baseband Serial Interface (BSI), which
exchanges baseband data between the PCF50732 and
the digital signal processor. The interface also includes
signals to power-up and power-down the baseband
transmit (TX) and receive (RX) paths.
FEATURES
• Low power and low voltage device in 0.25 micron
CMOS technology; supply voltage: analog 2.7 V
(typical) and digital 1.5 V (typical)
• Compatible with GSM phase 2 and DCS1800
recommendations
The voice band CODEC is a complete analog front-end
circuit. It consists of four parts:
• Complete in-phase and quadrature component interface
paths between the Digital Signal Processor (DSP) and
RF circuitry
• The receive path, which converts a digital signal to an
analog signal for an earpiece, an external loudspeaker
or a buzzer
• Complete linear PCM CODEC for audio signal
conversion between earphone/microphone and DSP
• The transmit path, which receives the analog external
signal from a microphone and converts it into a digital
signal
• Four auxiliary analog inputs for measurement purposes
(e.g. battery monitoring)
• The Voice band Signal Processor (VSP), which filters
the voice band data
• Three auxiliary analog outputs for control purposes
(i.e. AFC, AGC and power ramping control)
• The digital Audio Serial Interface (ASI), which
connects the digital linear PCM signals of the receive
and transmit paths to an external DSP. The voice band
data is coded in 16-bit linear PCM twos complement
words.
• Separate baseband, audio and control serial interfaces
• Voice band Signal Processor (VSP) for flexible audio
data processing.
2
APPLICATIONS
The auxiliary Analog-to-Digital Converter (ADC)
section consists of four input channels specified for battery
management applications.
The CMOS integrated circuit PCF50732, Baseband and
audio interface for GSM, is dedicated to wireless
telephone handsets conforming to the GSM
recommendations phases 1 and 2, DCS1800 and
PCS1900.
3
PCF50732
The auxiliary Digital-to-Analog Converter (DAC)
section consists of three DACs for Automatic Gain Control
(AGC), for Automatic Frequency Control (AFC) and for
power ramping.
The Control Serial Interface (CSI) is used to program a
set of control registers, to store the power amplifier
ramping characteristics into the dedicated RAM and to
transmit auxiliary ADC values to the DSP. It also controls
switches, modes and power status of the different parts of
the IC.
GENERAL DESCRIPTION
The baseband CODEC is a complete interface circuit
between the RF part in a mobile communication handset
and the Digital Signal Processor (DSP). It consists of three
parts:
• The receive path, which transforms the quadrature
signals from the RF (I/Q) to digital signals
• The transmit path, which transforms a bitstream to
analog quadrature signals for the RF devices
4
ORDERING INFORMATION
PACKAGE
TYPE NUMBER
NAME
PCF50732H
1999 May 03
LQFP48
DESCRIPTION
plastic low profile quad flat package; 48 leads; body 7 × 7 × 1.4 mm
3
VERSION
SOT313-2
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
5
PCF50732
QUICK REFERENCE DATA
SYMBOL
PARAMETER
CONDITIONS
MIN.
TYP.
MAX.
UNIT
VDDD
digital supply voltage
1.0
1.5
2.75
V
VDDA
analog supply voltage
VDDA ≥ VDDD
2.5
2.7
2.75
V
IDDA
analog supply current
VDDD = 1.5 V; VDDA = 2.7 V;
RXON active
−
3.5
−
mA
Pav
average power consumption
VDDD = 1.5 V; VDDA = 2.7 V; note 1
−
15
−
mW
Istb(tot)
total standby current
−
10
−
µA
fclk
master clock frequency
−
13.0
−
MHz
Tamb
operating ambient temperature
−40
+27
+85
°C
Note
1. Without load on audio outputs EARP, EARN, AUXSP and BUZ.
1999 May 03
4
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
6
PCF50732
BLOCK DIAGRAM
VDDD
handbook, full pagewidth
VDDA(vb)
VDDA(bb)
7
25
VDDA(vbo) VDDA(ref)
37
34
47
REFERENCE
VOLTAGES AND
CURRENTS
PCF50732
TXON
BIEN
BIOCLK
BDIO
RXON
BOEN
10
10-BIT
DAC
LP
10
10-BIT
DAC
LP
19
15
BSI
23
ADC
24
DIGITAL
FILTER
20
18
21
22
2
ADC
27
M
U
X
28
29
30
AUXST
CCLK
CEN
CDI
CDO
AMPCTRL
ACLK
AFS
ADI
ADO
MCLK
RESET
13
9
64 × 10-BIT
SRAM
DAC3
CTL
10
11
CSI
12
10
AUXDAC3
10-BIT
33
12
AUXDAC2
12-BIT
32
8
AUXDAC1
8-BIT
31
14
4
3
2
VOICE BAND
SIGNAL
PROCESSOR
DECIMATION
FILTER
IRAM
NOISE
SHAPER
MICADC
40
2
41
M
U
X
38
39
ASI
46
1
6
EARDAC
1 MHz
CLOCK
GENERATOR
5
8
26
42
48
OUTPUT
AMPLIFIER
45
OUTPUT
AMPLIFIER
44
OUTPUT
AMPLIFIER
43
35
MGR988
VSSD
VSSA(bb)
VSSA(vb) VSSA(vbo) VSSA(ref)
Fig.1 Block diagram.
1999 May 03
Vref
GMSK
MODULATOR
16
17
36
5
QP
QN
IP
IN
AUXADC1
AUXADC2
AUXADC3
AUXADC4
AUXDAC3
AUXDAC2
AUXDAC1
MICP
MICN
AUXMICP
AUXMICN
EARP
EARN
AUXSP
BUZ
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
7
PCF50732
PINNING
PIN
SYMBOL
NR. TYPE(1)
DESCRIPTION
ACTIVE
LEVEL
ACTIVE
EDGE
IDD
ADO
1
O/TS
−
−
1.5 mA
audio digital interface PCM data output to DSP
ADI
2
I
−
−
−
audio digital interface PCM data input from DSP
AFS
3
I
−
rising
−
audio digital interface PCM frame synchronization signal
from DSP
ACLK
4
I
−
rising
−
audio digital interface PCM clock signal from DSP
RESET
5
I
LOW
−
−
asynchronous reset input
MCLK
6
I
−
rising
−
low-swing master clock input; fclk = 13 MHz; integrated
capacitive coupling
VDDD
7
P
−
−
−
digital power supply
VSSD
8
G
−
−
−
digital ground
CCLK
9
I
−
falling
−
control bus clock input from DSP
CEN
10
I
LOW
−
−
control bus data enable from DSP
CDI
11
I
−
−
−
control bus data input from DSP
CDO
12
O/TS
−
−
1.5 mA
AUXST
13
I
HIGH
−
−
AMPCTRL
14
O
−
−
1.5 mA
control bus data output to DSP
status control signal for activation of AUXDAC1,
AUXDAC2 and MCLK input
general purpose output pin
BIOCLK
15
O/TS
−
−
3 mA
BIEN
16
O
LOW
−
1.5 mA
baseband transmit interface data enable signal
BDIO
17
I/O
−
−
1.5 mA
baseband interface data I/O from/to DSP
BOEN
18
O
LOW
−
1.5 mA
baseband receive interface data enable signal
TXON
19
I
HIGH
−
−
baseband transmit path activation signal
RXON
20
I
HIGH
−
−
baseband receive path activation signal
baseband interface data clock
IP
21
I/O
−
−
−
(I) baseband differential positive input/output to IF circuit
IN
22
I/O
−
−
−
(I) baseband differential negative input/output to
IF circuit
QP
23
I/O
−
−
−
(Q) baseband differential positive input/output to
IF circuit
QN
24
I/O
−
−
−
(Q) baseband differential negative input/output to
IF circuit
VDDA(bb)
25
P
−
−
−
baseband power supply (analog)
VSSA(bb)
26
G
−
−
−
baseband ground (analog)
AUXADC1
27
I
−
−
−
auxiliary ADC input 1 for battery voltage measurement
AUXADC2
28
I
−
−
−
auxiliary ADC input 2
AUXADC3
29
I
−
−
−
auxiliary ADC input 3
AUXADC4
30
I
−
−
−
auxiliary ADC input 4
AUXDAC1
31
O
−
−
−
auxiliary DAC output for AGC; max. load 50 pF // 2 kΩ
AUXDAC2
32
O
−
−
−
auxiliary DAC output for AFC; max. load 50 pF // 10 kΩ
1999 May 03
6
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
PCF50732
PIN
SYMBOL
NR. TYPE(1)
DESCRIPTION
ACTIVE
LEVEL
ACTIVE
EDGE
IDD
AUXDAC3
33
O
−
−
−
auxiliary DAC output for power ramping; maximum load
50 pF, ±600 µA
VDDA(ref)
34
P
−
−
−
reference voltage power supply (analog)
VSSA(ref)
35
G
−
−
−
reference voltage ground (analog)
Vref
36
I/O
−
−
−
band gap reference voltage noise decoupling
VDDA(vb)
37
P
−
−
−
voice band voltage power supply
AUXMICP
38
I
−
−
−
auxiliary microphone differential positive input
AUXMICN
39
I
−
−
−
auxiliary microphone differential negative input
MICP
40
I
−
−
−
microphone differential positive input
MICN
41
I
−
−
−
microphone differential negative input
VSSA(vb)
42
G
−
−
−
voice band ground
BUZ
43
O
−
−
−
buzzer output
AUXSP
44
O
−
−
−
auxiliary speaker output
EARN
45
O
−
−
−
earphone differential negative output
EARP
46
O
−
−
−
earphone differential positive output
VDDA(vbo)
47
P
−
−
−
voice band output buffer voltage power supply (analog)
VSSA(vbo)
48
G
−
−
−
voice band output buffer ground (analog)
Note
1. O/TS = 3-state output.
1999 May 03
7
Philips Semiconductors
Objective specification
ADO
37 VDDA(vb)
36 Vref
1
ADI 2
35 VSSA(ref)
AFS 3
34 VDDA(ref)
ACLK 4
33 AUXDAC3
RESET 5
32 AUXDAC2
MCLK 6
31 AUXDAC1
PCF50732
VDDD 7
30 AUXADC4
8
QP 23
QN 24
IP 21
IN 22
RXON 20
25 VDDA(bb)
TXON 19
CDO 12
BOEN 18
26 VSSA(bb)
BIEN 16
27 AUXADC1
CDI 11
BDIO 17
CEN 10
BIOCLK 15
28 AUXADC2
AUXST 13
29 AUXADC3
CCLK 9
AMPCTRL 14
VSSD 8
Fig.2 Pin configuration.
1999 May 03
38 AUXMICP
39 AUXMICN
40 MICP
PCF50732
41 MICN
42 VSSA(vb)
43 BUZ
44 AUXSP
45 EARN
46 EARP
handbook, full pagewidth
47 VDDA(vbo)
48 VSSA(vbo)
Baseband and audio interface for GSM
MGR989
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
8
8.2
FUNCTIONAL DESCRIPTION
Baseband and voice band reference voltages
The reference voltage Vref is generated on-chip by a band
gap voltage reference circuit and is available at pin Vref.
This chapter gives a brief overview of the device.
The detailed functional description can be found in the
following chapters:
As Vref is used as reference for most of the internal analog
circuitry, noise must be kept as low as possible by
connecting an external decoupling capacitor at this pin.
Chapter 9 “Baseband CODEC”
Chapter 10 “Voice band CODEC”
Chapter 11 “Auxiliary functions”
The voltage at Vref is buffered to generate the baseband
and voice band reference voltage Vref as well as internal
references for the different functions, such as the auxiliary
and the transmit DACs.
Chapter 12 “Control Serial Interface (CSI)”
Chapter 13 “Voice band Signal Processor (VSP)”.
8.1
PCF50732
General
9
As low power consumption in mobile telephones is a very
important issue, all the circuit parts in the PCF50732 can
be powered-on/off either by means of the external signals
AUXST, TXON or RXON, or by programming the
respective register bits in the Control Serial Interface
(CSI).
BASEBAND CODEC
The baseband CODEC is a complete interface circuit
between the RF part in a mobile communication handset
and the digital signal processor. It consists of three parts:
• The transmit path, which converts a bitstream to
analog quadrature signals for the RF devices
• The receive path, which transforms the quadrature
signals of the IF chip (I/Q) to digital signals
The most important signal for the digital and analog circuit
functions in the PCF50732 is the DAC enable signal
AUXST, which allows to activate AUXDAC1 (AGC) and
AUXDAC2 (AFC), as well as the low-swing master clock
input MCLK. AUXST must be active (HIGH) and VDDA
must be stable (see also Section 18.1) to allow the
master clock to access different circuit parts after a reset
(RESET active). AUXDAC1 and AUXDAC2 are only
activated if their related power-on bit is set. AUXDAC1 is
default off, AUXDAC2 is default on.
• The digital baseband serial interface, which
exchanges baseband data between the PCF50732 and
the DSP. The interface also includes signals to
power-up and power-down the baseband transmit
(TX) and receive (RX) paths.
9.1
Baseband transmit path
The baseband transmit path consists of three parts:
RESET must be active during at least 3 MCLK cycles, with
AUXST active, to ensure a correct initialisation of all the
digital circuitry of the PCF50732. Since RESET is
asynchronous even small spikes of a few nanoseconds
can cause partial resets.
• GMSK modulator: generation of a Gaussian Minimum
Shift Keying (GMSK) signal
• 10-bit DACs: digital-to-analog converters for the
I and Q components of the GMSK signal
For power supply noise interference reduction, a pair of
power supply and ground pins are provided for the:
• Low-pass filters: analog reconstruction low-pass filters
for the output of the DACs.
• Baseband analog: VDDA(bb)/VSSA(bb)
The requirements of the transmit path of a GSM terminal
are given by “GSM recommendation 05.05”:
• Voice band analog: VDDA(vb)/VSSA(vb)
• Phase RMS error <5°
• Voice band output drivers: VDDA(vbo)/VSSA(vbo)
• Phase peak error <20°
• DC reference voltages and currents: VDDA(ref)/VSSA(ref)
• Digital circuitry: VDDD/VSSD.
• Amplitude error < ±1 dB.
All VSS pins are connected internally. VDDD is the digital
supply. VDDA(bb), VDDA(vb), VDDA(vbo), and VDDA(ref) are
analog supplies, and are referred to as VDDA throughout
this document. These analog supplies must be connected
externally.
Nevertheless the performance of the PCF50732 is far
better than these figures indicate; see Section 18.1.
1999 May 03
9
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
9.1.1
The baseband receive section can be switched between
two modes of operation:
GMSK MODULATOR
The input signal of the GMSK modulator is a bitstream
coming from the baseband serial interface, with a
sampling frequency of 270.833 kHz. Typically 148 bits are
modulated during a normal burst, and 88 bits during an
access burst. Using this bitstream, the GMSK modulator
generates digital I and Q components as described in
“GSM recommendation 05.04”.
• ZIF (zero IF) mode for radio sections, which convert the
receive signal down to baseband. In this mode the ADC
is sampled at 6.5 MHz, the decimation filter samples
down by a factor of 24 with a pass band as specified in
Fig.3. The serial interface output BDIO delivers
2 × 12-bit values for I and Q components at
270.833 kHz.
This is done in three steps:
• NZIF (near zero IF) mode for radio sections, which
converts the receive signal down to a centre frequency
of 100 kHz. In this mode the ADC is sampled at 13 MHz,
the decimation filter samples down by a factor of 24 with
a pass band as specified in Fig.3. The serial interface
output BDIO delivers 2 × 12-bit values for I and Q
components at 541.667 kHz.
1. First the incoming bitstream is differentially encoded
by an EXOR operation on the actual bit and the
previous bit
2. The instantaneous phase (ϕ) is calculated using a
gaussian filter with an impulse response of 4 taps
3. A look-up table provides the cosine (I component) and
the sine values (Q component) of the phase (ϕ).
9.2.1
The look-up table also interpolates the signal to a
16 times higher frequency (4.333 MHz).
9.1.2
PCF50732
RECEIVE ADC
The receive ADCs are Σ∆ analog-to-digital converters that
convert differential input signals into1-bit data streams with
a sampling frequency of 6.5 or 13 MHz.
10-BIT DACS
The two 10-bit DACs are working at a sampling rate of
4.3333 MHz. They convert the digital I and Q components
of the GMSK modulator to differential analog
I and Q signals.
9.2.2
9.1.3
• Decimation of the sampling rate (6.5 or 13 MHz) by 24
Digital filtering is required for:
• Suppression of out-of-band noise produced by the
Σ∆ ADC
LOW-PASS FILTER
The analog output signals of the DACs are filtered by
analog reconstruction low-pass filters.
• System level filtering.
The digital filtering is performed by a digital FIR filter with a
group delay for this running average filter of approximately
23 or 11.5 µs respectively. The filter uses twos
complement arithmetic.
These filters remove high frequency components of the
DAC output signals and attenuate components around the
4.3333 MHz sampling frequency. The low-pass filters
have a cut-off frequency of approximately 300 kHz, with
very linear phase behaviour in the pass band.
9.2
Baseband receive path
The baseband receive path consists of two parts:
• Receive ADC: Σ∆ analog-to-digital converters
• Decimation filter: digital decimation filters for I and Q.
1999 May 03
DIGITAL DECIMATION FILTER
10
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
PCF50732
MBL025
20
handbook, full pagewidth
gain
(dB)
0
−20
NZIF
ZIF
−40
−60
−80
−100
0
100
200
300
400
500
f (kHz)
600
3
Fig.3 Transfer functions for the baseband receive filter.
9.3
9.3.1
BIEN0 must be at least 10 quarterbits long to allow settling
of the analog filters. Bits are clocked out of the DSP by the
falling edge and clocked into the PCF50732 by the rising
edge of BIOCLK. After the BIEN1 period has elapsed,
BIEN is set HIGH again and transmission from the DSP
ends. Logic 1s are modulated whenever BIEN is HIGH
and the baseband transmit (BBTX) block is active. Values
for BIEN0 and BIEN1 can be set in the Burst control
register.
Baseband Serial Interface (BSI)
OVERVIEW
The digital part of the baseband consists of a receive
section and a transmit section. The receive section is a
FIR filter that reduces the 6.5 MHz (13 MHz for
NZIF mode) bitstream from the sigma-delta converters
into 2 × 12-bit values at 270.833 kHz (541.667 kHz for
NZIF mode).
Figure 5 shows the timing for the BSI data transmission.
In power-down the de-asserted value of BIOCLK is high-Z
and BIEN is HIGH. Typical connection to the system DSP
is defined in Table 1.
The transmit section converts the 270.833 kHz data
stream from the DSP into a GMSK signal sampled at
4.333 MHz. The 10-bit I and Q signals are then fed into
two 10-bit DACs. The power ramping signal is also
generated by the transmit section with the 10-bit
AUXDAC3 block.
9.3.2
9.3.2.1
Table 1
TRANSMIT PATH BLOCK DESCRIPTION
PCF50732
Transmit serial interface
The power-up of the BSI transmit path is controlled via the
TXON pin. When TXON is pulled HIGH, the transmit path
recovers from power-down. The MCLK/48 = 270.833 kHz
output signal BIOCLK is activated. When the BIEN0 period
has elapsed the output signal BIEN goes LOW and the bits
to be transmitted are clocked out of the DSP.
1999 May 03
Connection of BSI transmit signals to
PCF5087X
11
PCF5087X
PIN
I/O
PIN
I/O
TXON
I
RFSIG[y]
O
BDIO
I/O
SIOXD
I/O
BIEN
O
SOXEN_N
I
BIOCLK
O
SIOXCLK
I
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
9.3.2.2
PCF50732
After TXON goes HIGH and a time equal to RU quarterbit
periods has elapsed, power ramp-up is done.
Power ramping controller
The PCF50732 fully supports all multislot modes which do
not require full duplex operation or more than two
consecutive transmit bursts. In this specification double
burst mode is used for all supported multislot modes while
single burst mode supports the normal GSM modes.
After a time period equal to RD quarterbits has elapsed
power ramp-down is initiated.
The AUXDAC3 output is also shown in Fig.4.
Values for RU (ramp-up) and RD (ramp-down) can be set
in the Burst control register of the control serial interface.
RD must be greater than RU + 32. RU and RD range
from 0 to 4000 QB (quarterbit). The register offers the
possibility to enter codes up to 4095.
The power ramping controller drives the power amplifier
output envelope.
In each transmit (TX) burst one ramp-up and one
ramp-down will be carried out. In multislot mode one
intermediate ramp will be carried out in addition to ramp-up
and ramp-down. Each ramp consists of 16 discrete step
values that are sent to the DAC3. Each step’s duration is
2 quarterbits which translates into 8-bit long ramps.
The DAC3 output is in 3-state whenever it is powered
down. The ramping step values are stored in a 64 × 10-bit
RAM as shown in Table 2.
The GMSK modulator is active for a period of 2 clock
cycles after the ramp-down or for the length of the TXON
burst, whichever is longer.
Multislot (high speed switched data mode) can be selected
by setting the appropriate bit in the Burst control register.
In multislot mode an intermediate ramping step is done.
This intermediate step is started after a time period equal
to RM quarterbits has elapsed. A value for RM
(intermediate ramp) is also set using the Burst control
register. The following conditions must be true:
In order to initialize AUXDAC3 it is necessary to write into
the RAM all 32 (or 48 in multislot mode) DAC3 output
values. Filling the RAM is normally done by writing a
logic 0 to the address sub-register of the Burst control
register, after which 32 or 48 values, depending on
multislot mode, can be written into the data sub-register of
the Burst control register. Writing to the DAC3 RAM is only
possible when the DAC3 is powered off.
RU + 32 < RM and RM + 32 < RD.
Table 2
AUXDAC3 RAM contents
RAM ADDRESS
Total number of CSI-accesses is therefore 33 for a normal
burst and 49 for a double burst.
An autoincrement feature will store these data into the
correct RAM positions.
The value after power-up of DAC3 will always be equal to
the value of RAM location 47.
0 to 15
ramp-up data
16 to 31
intermediate ramp data
32 to 47
ramp-down data
48 to 64
not used
Table 3
AUXDAC3 timing is controlled by the Burst control
register. This contains the following sub-registers:
Power ramping timing characteristics
SYMBOL
• The RU register containing the delay in number of
quarterbit cycles from the assertion of TXON to the start
of the power-up ramping; default value is 0
DATA
VALUE
COMMENTS(1)
t0
12t1
one quarterbit (QB)
tru
RU register
0 to 4000 QB
tim
RM register
RU + 32 to 4000 QB
trd
RD register
RM + 32 to 4000 QB
trup, trim, trdo
32t0
8 bits; 32 QB
• The RM register containing the delay in number of
quarterbit cycles from the assertion of TXON to the start
of the intermediate power ramp; default value is 0. RM
is only used in case of multislot mode
Note
• The RD register containing the delay in number of
quarterbit cycles from the assertion of TXON to the start
of the power-down ramping; default value is 0
1. QB: Quarterbit, usually referred to the time needed for
one quarter of a GSM baseband bit, i.e. a frequency of
1⁄ × 13 MHz.
12
• DAC3 burst RAM address register
• DAC3 burst RAM data register
• Single/double burst mode register: normal mode or
multislot mode selection flag.
1999 May 03
12
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
PCF50732
handbook, full pagewidth
TXON
APE_DAC3(1)
t im
t ru
AUXDAC3
t rd
ADDRESS
AUXDAC3
RAM
0
47
15
15
47
31
15
31
47
31
47
t rup
t rim
t rdo
RU
RM
RD
MGR995
(1) APE_DAC3: Analog Power Enable signal for the AUXDAC3.
Fig.4 Power ramping timing characteristics (multislot mode).
9.3.3
9.3.3.1
Bits are clocked out of the PCF50732 by the falling edge,
and clocked into the DSP by the rising edge of BIOCLK.
In normal bursts 148 I/Q pairs are read from the
PCF50732.
RECEIVER PATH BLOCK DESCRIPTION
Receive serial interface
The baseband serial interface sends the digital signal of
the receive path to a digital signal processor. It also takes
the digital bitstream from the digital signal processor and
transmits it via the baseband CODEC.
When RXON goes LOW, the last pair of I and Q values will
be sampled and transferred to the baseband processor
(both I and Q components). BIOCLK stops after additional
16 BIOCLK cycles. The receive path is powered down
again. In power-down the BIOCLK output is put in 3-state
and the BOEN output is HIGH.
The baseband reception and transmission are active in
bursts. A normal burst has a length of 548 µs. The frame
rate of bursts is 4.615 ms. Using a normal traffic channel,
one burst for each frame is transmitted and two bursts are
received. To save as much power as possible, the transmit
path and the receive path of the PCF50732 are in
power-up mode only during the transmission or reception
bursts respectively.
The output format is 2 × 12-bit I/Q (twos complement).
Transmission occurs MSB first, I followed by Q. The serial
clock signal BIOCLK will run at 6.5 MHz, or 13 MHz in the
NZIF mode. Figure 6 shows the timing of the BSI data
reception.
The power-up of the receive section is controlled via the
RXON pin or RXON bit. When RXON is driven HIGH, the
receive section recovers from power-down and the output
clock BIOCLK is activated. After a settling delay of 52 µs
(ZIF mode, analog circuitry + decimation filter settling
time), BOEN goes LOW to transfer the first 12-bit
I and Q words. The settling time is only 26 µs in NZIF
mode.
1999 May 03
An automatic offset compensation mechanism is provided
in order to achieve the required performance. This
mechanism will short the receive (RX) inputs internally and
measure the resulting offset value. This offset value will be
subtracted from all subsequent I/Q output words.
The offset inherent to the device can thereby be reduced
to a few millivolts. Default value for both I- and Q-offset is
zero.
13
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
Offset compensation measurement can be done on three
channels separately: baseband receive I channel,
baseband receive Q channel and AUXADC channel. All
AUXADC channels use the same offset compensation
value. Starting an offset measurement is done by writing a
logic 1 into the offset trigger register for each channel that
needs calibration. If the value ‘7’ (decimal) is written into
the offset trigger register offsets will be measured for I, Q
and AUXADC channels.
Table 4
Connection of BSI receive signals to the
PCF5087X
PCF50732
Offsets can also be read or written directly. Each offset
measurement is implemented internally as an AUXADC
measurement and takes approximately 100 µs.
Offsets from −256 up to 255 can be compensated.
9.3.4
PCF50732
PCF5087X
PIN
I/O
PIN
I/O
RXON
I
RFSIG[z]
O
BDIO
I/O
SIOXD
I/O
BOEN
O
SIXEN_N
I
BIOCLK
O
SIOXCLK
I
BASEBAND SERIAL INTERFACE (BSI) TIMING CHARACTERISTICS
handbook, full pagewidth
intermediate ramp
t 43
32 QB
ramp-up
t 42
32 QB
t 44
t 40
TXI/Q(1)
data
data
data
data
ramp-down
trail
32 QB
2 BIOCLK
clocks
logic 1s
logic 1s
AUXDAC3
t7
high-Z
BIOCLK
high-Z
BDIO
high-Z
d.c.(2)
d.c.
d.c.
B(0)
B(1)
B(n)
t 39
high-Z
t9
t10
BIEN
t5
TXON
MGR990
t6
(1) TXI/Q = transmit I or Q.
(2) d.c. = don’t care; will be overwritten with logic 1.
Fig.5 Timing of the baseband serial interface transmit path; for the timing values see Table 5
1999 May 03
14
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
PCF50732
t12
handbook, full pagewidth
16t1
high-Z
high-Z
BIOCLK
I11
BDIO
I0
Q11
Q0
t14
t13
BOEN
t15
RXON
MGR991
548 µs
t11
Fig.6 Timing of the baseband serial interface receive path; for the timing values see Table 5.
Table 5
BSI timing characteristics
SYMBOL
PARAMETER
MIN.
TYP.
MAX.
UNIT
Master clock
t1
MCLK cycle time
−
76.9
−
ns
2t1
−
ns
2t1
−
ns
t2
MCLK LOW time
30
1⁄
t3
MCLK HIGH time
30
1⁄
t4
RESET LOW time
3t1
−
−
ns
Baseband Serial Interface (BSI) transmit path (see Fig.5)
t5
BIEN0 value
10
−
511
QB
t6
BIEN1 value
t5
−
4000
QB
t7
BIOCLK cycle time
−
48t1
−
ns
t9
data set-up time
20
−
−
ns
t10
data hold time
20
−
−
ns
t39
BIOCLK active after TXON rising edge
−
−
t1
ns
t40
analog TX and GMSK power-up time
−
−
17.4
QB
t42
ramp-up value
0
−
3940
QB
t43
intermediate ramp value
32 + t42
−
3980
QB
t44
ramp-down value
normal mode
32 + t42
−
4020
QB
double burst mode
32 + t43
−
4020
QB
1999 May 03
15
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
SYMBOL
PCF50732
PARAMETER
MIN.
TYP.
MAX.
UNIT
Baseband Serial Interface (BSI) receive path (see Fig.6)
analog power-up and filter settling time
t11
t12
ZIF mode
−
52
−
µs
NZIF mode
−
26
−
µs
ZIF mode
−
2t1
−
ns
NZIF mode
−
t1
−
ns
BIOCLK cycle time
t13
BOEN LOW after falling clock edge
−
−
15
ns
t14
BIOCLK falling edge to data valid
−
−
15
ns
t15
BOEN HIGH after falling clock edge
−
−
15
ns
Linearity of receiver equipment (to earpiece) at
EARPGA = 0 dB and a volume control (VOLPGA and
EARAMP or AUXAMP) of −12 dB, signal-to-total harmonic
distortion ratio according to “GSM recommendation
II.11.10 V.4.16.1”.
10 VOICE BAND CODEC
The voice band CODEC is a complete analog front-end
circuit. It consists of three parts:
• The receive path, which converts a digital linear PCM
signal to an analog signal for an earpiece, an external
loudspeaker or a buzzer
10.1.1
• The transmit path, which receives an analog signal
from a microphone or an auxiliary input and converts it
into a digital linear PCM signal
RXVOL controls the volume of the voice band receive
path. In conjunction with EARAMP, AUXAMP and
BUZAMP it allows a gain variation from +6 to −30 dB in
64 steps; see Table 25. RXVOL also provides a mute
selection of the three outputs EARP/EARN, AUXSP and
BUZ respectively. At RESET the volume is automatically
set to −12 dB.
• The digital Audio Serial Interface (ASI), which
connects the digital linear PCM signals of the receive
and transmit paths to a digital signal processor.
Various functions and characteristics of the voice band
CODEC can be selected by programming the
corresponding control registers in the Control register
block (see also Tables 11, 22, 23, 24 and 25).
10.1
10.1.2
RXPGA
RXPGA controls the gain of the voice band receive path
within a range of −24 to +12 dB in 64 steps for calibration
purposes.
Voice band receive path
The voice band receive path consists of the following
parts:
10.1.3
• The receive part of the voice band signal processor
RXFILTER
RXFILTER is a digital band-pass filter with a pass band
from 300 to 3400 Hz. It is realized by a programmable
structure (voice band signal processor).
• NOISE SHAPER: 3rd order digital Σ∆ modulator,
generates a bit stream at 1 MHz to drive the EARDAC
• EARDAC: digital-to-analog converter including
low-pass filter for high frequency noise content of noise
shaper
10.1.4
EARDAC
EARDAC is a DAC operating at a sampling frequency of
1 MHz. It converts the bitstream input to a sampled
differential analog signal and low-pass filters the output
signal at the same time.
• EARAMP: amplifier for an earpiece
• AUXAMP: amplifier for an auxiliary loudspeaker
• BUZAMP: amplifier for a buzzer output.
1999 May 03
RXVOL
16
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
10.1.5
Values are specified for a standard electret microphone
with a sensitivity of −64 ±3 dB for high gain or for an
external microphone with an amplifier sensitivity of
−26 ±3 dB (0 dB ≡ 1 V/0.1 Pa = 1 V/µbar; at 1 kHz).
EARAMP
EARAMP is an amplifier, capable of driving a standard
earpiece with a minimum impedance of 8 Ω in
single-ended mode or 16 Ω in differential mode.
10.1.6
10.2.2
AUXAMP
10.2.3
An ‘auxiliary speaker external amplifier control’ output
pin (AMPCTRL) can be used to switch on/off an external
amplifier (hands-free car kit). The status of AMPCTRL is
programmable via the Control Serial Interface; its default
value is on.
The bitstream with a sampling frequency of 1 MHz is
low-pass filtered and down-sampled to 40 kHz by a FIR
filter.
BUZAMP
A digital high-pass filter and a digital low-pass filter (both
IIR filters) process the 14-bit input samples to achieve a
band-pass with a pass band from 300 to 3400 Hz. These
filters run on the on-chip voice band signal processor (see
Fig.7). It’s program is down-loaded into the instruction
memory (IRAM) via the CSI (see Table 26).
Voice band transmit path
The output of the TXFILTER is down-sampled to a
sampling frequency of 8 kHz with a word length of 16 bits.
The voice band transmit path consists of the following
parts:
• MICMUX: microphone input multiplexer
10.2.4
• MICADC: Σ∆ analog-to-digital converter
• TXFILTER: band-pass filter for the digital transmit signal
and down-sampling
10.2.5
• TXPGA/LIM: fine-programmable gain for calibration,
limiter
SIDEPGA
SidePGA loops part of the voice band transmit signal back
into the receive path. There are 64 gain steps from mute to
+6 dB.
• SidePGA: voice band sidetone programmable gain
amplifier.
10.3
Linearity of transmitter equipment, signal-to-total harmonic
distortion ratio according to “GSM recommendation
II.11.10 V.4.16.1”.
Voice band digital circuitry
The voice band digital circuitry is responsible for
converting a 16-bit PCM signal at 8 kHz sample rate to and
from a 1-bit 1 MHz signal. It also contains a band-pass
filter for 300 to 3400 Hz and a sidetone engine. Various
volume settings are calculated inside this block. Figure 7
shows the block diagram of the voice band signal
processor.
MICMUX
MICMUX is used to select between a differential signal at
pins MICP/MICN and a differential signal at pins
AUXMICP/AUXMICN.
1999 May 03
TXPGA
TXPGA adapts the analog signals coming from MICMUX
within a range of −30 to +6 dB. It is designed for calibration
purposes.
• DECIMATOR: decimates the incoming bit stream from
1 MHz to 40 kHz
10.2.1
DECIMATOR AND TXFILTER
The DECIMATOR is a digital filter, which performs a signal
processing to a lower sampling rate at the output
compared to the input.
BUZAMP is an amplifier for connection to an external
buzzer of minimum 8 Ω. It has the same output
characteristics as the AUXAMP and can hence be used as
a second auxiliary output amplifier. It is switched on/off by
a dedicated control bit in the Control register block.
10.2
MICADC
MICADC is a Σ∆ A/D converter which generates a 1 MHz
bitstream.
AUXAMP is an amplifier for connection to an external
loudspeaker amplifier of minimum 8 Ω (hands-free car kit).
10.1.7
PCF50732
17
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
PCF50732
handbook, full pagewidth
VOICE BAND SIGNAL PROCESSOR
ADI
TXPGA/LIM
DECIMATOR
ACLK
TX_BS
(transmit bitstream)
ASI
AFS
RX/TX
FILTER
SidePGA
ADO
1-bit, 1 MHz
16-bit, 8 kHz
RXVOL
NOISE
SHAPER
RXPGA/LIM
RX_BS
(receive bitstream)
MGR992
RRAM
IRAM
Fig.7 Block diagram of the voice band signal processor.
10.3.1
Pin ADO is put in 3-state after the LSB of the transmit
word, independent of the length of the AFS pulse. If the
channel position 0 (see Section 10.3.2.1) is selected, then
the MSB must be output directly after AFS becomes a
logic 1, even if no rising edge on ACLK has been given yet.
VOLUME CONTROL BLOCK
The volume control block contains the RXPGA, SidePGA,
TXPGA and both limiter blocks. The possible settings can
be found in the description of the CSI block. All digital
volume control blocks, i.e. RXPGA, SidePGA, and
TXPGA, will allow settings from +6 to −30 dB and mute in
64 steps. However, not all combinations of settings for
these blocks will be meaningful. The limiter will always clip
signals with overflow to the maximum or minimum
allowable value.
10.3.2
The following modes of operation are programmable:
channel position and ACLK clock mode.
10.3.2.1
Depending on a programmable register value n
(n = 0 to 15) one of 16 channels can be selected (see
Table 22). The ASI can add a delay of 16 × n-bit clocks
between the assertion of AFS and the start of the MSB of
the PCM values. This delay is independently
programmable for transmit and receive mode.
AUDIO SERIAL INTERFACE (ASI) BLOCK
The ASI is the voice band serial interface which provides
the connection for the exchange of PCM data in both
receive and transmit directions, between the baseband
digital signal processor and the PCF50732. The data is
coded in 16-bit linear PCM twos complement words.
10.3.2.2
A frame start is defined by the first falling edge of ACLK
after a rising AFS. This first falling edge is used to clock in
the first data bit on both the baseband and the DSP device.
ACLK clock mode
Single or double clock mode can be selected. Double clock
mode implies two clock pulses per data bit and is used for
communication with IOM2 compatible devices. In double
clock mode data must be output on the first rising edge and
be read on the last falling edge.
Data on pin ADI is clocked in (MSB first) on the falling edge
of the ACLK clock. Data is clocked out (MSB first) on pin
ADO on the rising edge of the ACLK clock.
1999 May 03
Channel position mode
18
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
Table 6
PCF50732
Pin connection of the audio serial interface to the PCF5087X
PCF50732
PCF5087X
PIN
I/O
PIN
I/O
ADI
I
DD
O
ADO
O
DU
I
ACLK
I
DCL
O
AFS
I
FSC
O
handbook, full pagewidth
AFS
word
ADI
t rpdc
word
ADO
MGR993
t tpdc
trpdc: receive path data channel delay.
ttpdc: transmit path data channel delay.
Fig.8 Frame structure of the Audio Serial Interface (ASI).
1999 May 03
19
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
10.3.2.3
PCF50732
Audio Serial Interface (ASI) timing characteristics
t 41
handbook, full pagewidth
AFS
t16
t 42
t17
ACLK
t 40
t 21
LSB
MSB
last slot
last bit
ADO
single
clock
mode
first slot
first bit
t 19
last slot
last bit
t 20
MSB
last slot
last bit
ADI
first slot
second bit
high-Z
t 18
LSB
first slot
second bit
first slot
first bit
last slot
last bit
t 21
MSB
ADO
last slot
last bit
LSB
slot 1
bit 2
first slot
first bit
double
clock
mode
t 19
t 20
LSB
MSB
ADI
last slot
last bit
high-Z
last slot
last bit
first slot
first bit
slot 1
bit 2
last slot
last bit
MGR994
Fig.9 Timing of the Audio Serial Interface (ASI).
Table 7
ASI timing characteristics
SYMBOL
PARAMETER
MIN.
TYP.
MAX.
UNIT
t16
frame sync (AFS) set-up time to falling edge of ACLK
70
−
−
ns
t17
frame sync (AFS) hold time from falling edge of ACLK
40
−
−
ns
t18
ACLK rising edge to data (ADO) valid
−30
−
+30
ns
t19
data (ADI) set-up time to falling edge of ACLK
50
−
−
ns
t20
data (ADI) hold time from falling edge of ACLK
80
−
−
ns
t21
first data valid (ADO) after AFS rising edge
0
−
60
ns
t40
ACLK period
0.5
−
7.8
µs
single clock mode
0.5
−
3.9
µs
t41
AFS period
−
125
−
µs
t42
ACLK LOW before AFS rising edge
40
−
−
ns
double clock mode
1999 May 03
20
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
PCF50732
11 AUXILIARY FUNCTIONS
11.3
The auxiliary functions part consists of three
digital-to-analog converters (DACs) and a 4 input
analog-to-digital converter (ADC) with a 12-bit range.
The DACs are for:
AUXDAC3 is a 10-bit binary coded digital-to-analog
converter designed for power ramping purposes.
AUXDAC3 is default off. The power ramping behaviour is
described in Section 9.3.2.2.
• Automatic Gain Control (AGC): AUXDAC1
Power ramping: AUXDAC3
• Automatic Frequency Control (AFC): AUXDAC2
11.4
• Power ramping: AUXDAC3.
The AUXADC is specified for voltage and temperature
measurements. It contains 4 input channels required for
∆T and ∆V measurements, as well as battery type
recognition:
11.1
Automatic Gain Control (AGC): AUXDAC1
Auxiliary analog-to-digital converter (AUXADC)
The AUXDAC1 is an 8-bit binary coded, guaranteed
monotonic digital-to-analog converter.
• ∆T: battery temperature, ambient temperature
(measured across sensor)
The status of AUXDAC1 is controlled by the signal AUXST
and a power-up bit in the Power control register. The signal
that switches the external VCXO can also be used to
control the AUXST pin of the PCF50732. The AUXDAC1
output is floating in Power-down mode (AUXST = LOW).
The input MCLK is then deactivated.
• ∆V: peak battery voltage, battery voltage during transmit
burst.
Five 12-bit registers are available in which results of
auxiliary analog-to-digital conversions can be stored.
Two registers are dedicated to the input AUXADC1 and
one to each of AUXADC2, AUXADC3 and AUXADC4.
When AUXST goes HIGH, AUXDAC1 is powered-up and
the converted value of the corresponding register in the
control register block is available at the AUXDAC1 output
pin.
The AUXADC1 input can be used for battery voltage
measurement. In the AUXADC1A register the voltage
during a transmit time slot can be stored. The AUXADC1B
register can store the voltage during other time slots. If a
read request to one of these registers is executed by
loading its address into the Read request register, the
actual contents of the addressed register are given to the
control interface and a new measurement is performed in
the next appropriate time slot.
If a write access to the AUXDAC1 register occurs, the DAC
is activated with the new content of the DAC register (see
Table 14 and 15). The AUXDAC1 must be powered-up by
setting the correct bit in the Power control register. At reset
AUXDAC1 is powered-down.
11.2
A multiplexer connects each of the AUXADC inputs to a
channel of the receive ADC depending on read access to
the corresponding register.
Automatic Frequency Control (AFC):
AUXDAC2
The AUXDAC2 is a 12-bit binary coded, guaranteed
monotonic digital-to-analog converter. This DAC is used to
control the frequency of an external master clock VCXO.
Thus an auxiliary analog-to-digital conversion is only
possible, if the baseband receive section is not in use
(RXON is LOW). At each read request to one of the
AUXADC registers, a flag is set in the AUXADC flag
register indicating that an analog-to-digital conversion is to
be performed. When one of the registers AUXADC1B,
AUXADC2, AUXADC3, or AUXADC4 is being read, the
baseband interface verifies that RXON is LOW, indicating
that no receive burst is currently active. The baseband
receive path is then powered up. After the ADC settling
time has elapsed (see POSTAUXADC in Chapter 18), valid
data is available and stored in the corresponding register.
The status of AUXDAC2 is controlled by the signal AUXST
and a power-up bit in the Power control register. The signal
that switches the external VCXO can also be used to
control the AUXST pin of the PCF50732. The AUXDAC2
output is floating in Power-down mode (AUXST = LOW).
When AUXST goes HIGH, AUXDAC2 is powered-up and
the converted value of the corresponding register in the
control register block is available at the AUXDAC2 output
pin.
The default value for AUXDAC2 is 1.1 V which
corresponds to a 800H code in the AUXDAC2 register.
At reset AUXDAC2 is powered on.
1999 May 03
21
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
After conversion the corresponding bit in the AUXADC flag
register is reset (see Table 18). If RXON is activated
during an auxiliary analog-to-digital conversion cycle, the
auxiliary conversion is interrupted and restarted when
RXON returns LOW, indicating no receive burst activity.
PCF50732
The PCF50732 waits for a rising edge of TXON, and
powers up the receive path. After the settling time of the
ADC added to the programmed AUXADC conversion
delay (in 48 MCLK cycles) has elapsed, valid data is
available and stored in the AUXADC1A register.
When register AUXADC1A is read, a battery voltage
measurement during a transmission burst is executed.
handbook, full pagewidth
1440
output code
(LSB)
gain tolerance
offset
at 0 V
0
0
0.2
0.4
0.6
0.8
1.0
1.2
1.4
1.6
1.8
Vin (V)
2.0
MGR996
Fig.10 Typical transfer characteristics of AUXADC (output code as function of differential input voltage).
1999 May 03
22
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
If the device address is equal to the chip address, the
programmed information on CDI (DB11 to DB00) is loaded
into the addressed register (RA3 to RA0) when CEN
returns inactive HIGH.
12 CONTROL SERIAL INTERFACE (CSI)
The Control Serial Interface block is used to set and read
the status bits inside the PCF50732. It is also used to read
data from the auxiliary ADCs and to write data into the
auxiliary DACs. Finally, the block is used to write the power
ramping curve into a 64 × 10-bit static RAM. It should be
noted that only 48 of the 64 addresses can be accessed;
see Table 2.
12.1
PCF50732
The dummy bit in front is needed for compatibility with
older baseband devices.
Reading a register is accomplished by writing the address
of the required register into the read request register.
The next time CEN goes LOW, the requested data will be
shifted out, together with the register and device address.
The serial interface
A 4-line bidirectional serial interface is used to control the
circuit. It allows access to each register of the control
register block (read and/or write). The 4 lines are:
Table 8
Pin connection of the CSI to the PCF5087X
PCF50732
• Data in (CDI)
PCF5087X
• Data out (CDO)
PIN
I/O
PIN
I/O
• Clock (CCLK)
CDI
I
RFDO
O
CDO
O
RFDI
I
CCLK
I
RFCLK
O
CEN
I
RFE_N2
O
• Enable (CEN).
Table 8 lists the normal connections to the PCF5087X.
The data sent to or from the device is loaded in bursts
framed by CEN. Clock edges and data bits are ignored
until CEN goes active (LOW). Each data word consists of
21 bits that comprises a 4-bit device address, a 4-bit
register address, a 12-bit data word and a dummy bit; see
Table 9. The 21 bits are transmitted with MSB first.
Figure 5 shows the valid timing for data transmission on
the control interface.
Table 9
BIT
CONTENT
DESCRIPTION
00 to 03 ADD0 to ADD3 device address; for the
PCF50732 this is ‘1001’
(= 9 decimal)
04 to 07 RA0 to RA3
Data is read in from the CDI pin on the rising edge of the
CCLK clock and output on CDO on the falling edge of the
CCLK clock. Data is written into the registers on the rising
edge of CEN.
1999 May 03
Bit mapping of the 21-bit words
08 to 19 DB00 to DB11
20
23
dummy
register address
data value
don’t care
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
12.2
PCF50732
Control Serial Interface (CSI) timing characteristics
handbook, full pagewidth
CCLK
t 22
t 24
t 27
CEN
t 25
dummy
CDI
t 26
t 38
MSB(#19)
ADD0(#0)
t 23
t 23
dummy
CDO
MSB(#19)
ADD0(#0)
high-Z
t 37
MGR997
Fig.11 Timing diagram of the Control Serial Interface (CSI).
Table 10 CSI timing characteristics
For the timing diagram see Fig.11.
SYMBOL
PARAMETER
MIN.
MAX.
UNIT
t22
CEN set-up time
20
−
ns
t23
CDO data valid after falling clock edge
−
50
ns
t24
CCLK cycle time
100
−
ns
t25
data set-up time to rising edge of CCLK
20
−
ns
t26
data hold time from rising edge of CCLK
30
−
ns
t27
CEN hold time
30
−
ns
t37
CDO 3-state after CEN HIGH
−
30
ns
t38
CEN HIGH time
50
−
ns
1999 May 03
24
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
12.3
PCF50732
Control register block
This section describes the different registers that are implemented in the PCF50732. An overview is given in Table 11.
Tables 12 to 29 describe all the registers of the PCF50732.
Table 11 Control register block overview
ADDRESS
ACCESS
REGISTER NAME
0000
W
0001
R/W
AUXDAC1 (AGC) value register
0010
R/W
AUXDAC2 (AFC) value register
0011
R/W
Burst control register
0100
R/W
0101
R
AUXADC channel 1 register A (AUXADC1A); note 1
0110
R
AUXADC channel 1 register B (AUXADC1B); note 1
Read request register
AUXADC control register
0111
R
AUXADC channel 2 register (AUXADC2); note 1
1000
R
AUXADC channel 3 register (AUXADC3); note 1
1001
R
AUXADC channel 4 register (AUXADC4); note 1
1010
R/W
Voice band control register
1011
R/W
Voice band volume register
1100
R/W
Power control register
1101
R/W
RAM interface register
1110
R/W
Baseband receive control register
1111
R/W
Test mode register; note 2
Notes
1. See description in Section 11.4.
2. Do not use this register.
12.3.1
READ REQUEST REGISTER
Table 12 Read request register
X = don’t care during a read/or write access.
VALUE
ADDRESS
0000
REGISTER NAME
Read request register
11
10
9
8
7
6
5
4
3
2
1
0
X
X
X
X
r3
r2
r1
r0
s3
s2
s1
s0
Table 13 Read request registers value description
VALUE OF
Read request register
1999 May 03
SYMBOL
DESCRIPTION
r3 to r0
Address of the register to be read.
s3 to s0
Subaddress that might be needed. The subaddress bits are right
aligned, meaning that the subaddress always starts with bit ‘s0’ (LSB);
e.g. in case of two subaddress bits, ‘s1’ and ‘s0’ are used.
25
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
12.3.2
PCF50732
AUXDAC1 (AGC) VALUE AND AUXDAC2 (AFC) VALUE REGISTERS
Table 14 Registers overview
X = don’t care during a read/or write access.
VALUE
ADDR.
REGISTER NAME
11
10
9
8
7
6
5
4
3
2
1
0
0001
AUXDAC1 (AGC) value register
X
X
X
X
b7
b6
b5
b4
b3
b2
b1
b0
0010
AUXDAC2 (AFC) value register
b11
b10
b9
b8
b7
b6
b5
b4
b3
b2
b1
b0
Table 15 AUXDAC1 (AGC) value and AUXDAC2 (AFC) value registers value description
VALUE OF
SYMBOL
DESCRIPTION
AUXDAC1 (AGC) value register b7 to b0
input value to the 8-bit AUXDAC1 (fed directly into the DAC); the default
value is 85H
AUXDAC2 (AFC) value register b11 to b0
input value to the 8-bit AUXDAC2 (fed directly into the DAC); the default
value is 800H
12.3.3
BURST CONTROL REGISTER
The Burst control register controls the timing of the transmit burst (TX-burst). The ‘lo’-registers contain the lower 8 bits,
the ‘hi’-registers the upper 4 bits of a 12-bit delay value. Therefore, each register has a programmable range
from 0 to 4095. Not all combinations of values might make sense e.g. ramp-down before ramp-up.
Table 16 Burst control register (address 001 and subaddresses)
X = don’t care during a read/or write access.
SUBADDRESS
FUNCTION
VALUE
11
(s3)
10
(s2)
9
(s1)
8
(s0)
7
6
5
4
3
2
1
0
RU-lo
0
0
0
0
b7
b6
b5
b4
b3
b2
b1
b0
RU-hi
0
0
0
1
X
X
X
X
b11
b10
b9
b8
RM-lo
0
0
1
0
b7
b6
b5
b4
b3
b2
b1
b0
RM-hi
0
0
1
1
X
X
X
X
b11
b10
b9
b8
RD-lo
0
1
0
0
b7
b6
b5
b4
b3
b2
b1
b0
RD-hi
0
1
0
1
X
X
X
X
b11
b10
b9
b8
BIEN0-lo
0
1
1
0
b7
b6
b5
b4
b3
b2
b1
b0
BIEN0-hi
0
1
1
1
X
X
X
X
b11
b10
b9
b8
BIEN1-lo
1
0
0
0
b7
b6
b5
b4
b3
b2
b1
b0
BIEN1-hi
1
0
0
1
X
X
X
X
b11
b10
b9
b8
mode(1)
1
0
1
0
X
X
X
X
X
X
X
b0
DAC3 burst RAM
address(1)
1
0
1
1
X
X
a5
a4
a3
a2
a1
a0
DAC3 burst RAM
data(1)
d7
d6
d5
d4
d3
d2
d1
d0
Single/double burst
1
1
d9(2)
d8(2)
Notes
1. The programming is described in Section 9.3.2.2.
2. The subaddress positions bit 9 (s1) and bit 8 (s0) do not apply to the DAC3 burst RAM data register.
1999 May 03
26
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
PCF50732
Table 17 Burst control registers value description
VALUE OF
DESCRIPTION
RU
Value RU, consisting of RU-lo (least significant byte) and RU-hi (most significant byte), is the delay
measured in quarterbits (1⁄12MCLK) between the rising edge of TXON and the start of the ramp-up on
AUXDAC3. After this delay, the first 16 values of the AUXDAC3 RAM are sent to AUXDAC3. Shifting out
is done at 1⁄24MCLK.
RM
Value RM, consisting of RM-lo (least significant byte) and RM-hi (most significant byte), is the delay
measured in quarterbits between the rising edge of TXON and the start of the intermediate ramp in a
double burst ramp. The RM value is only used in multislot mode. RM must be greater than RU + 32.
RD
Value RD, consisting of RD-lo (least significant byte) and RD-hi (most significant byte), is the delay
measured in quarterbits between the rising edge of TXON and the start of the ramp-down on AUXDAC3.
RD must be greater than RU + 32, or in case of multislot mode, greater than RM + 32.
BIEN0
Value BIEN0, consisting of BIEN0-lo (least significant byte) and BIEN0-hi (most significant byte), is the
delay measured in quarterbits between the rising edge of TXON and the falling edge of BIEN.
BIEN1
Value BIEN1, consisting of BIEN1-lo (least significant byte) and BIEN1-hi (most significant byte), is the
delay measured in quarterbits between the rising edge of TXON and the rising edge of BIEN. BIEN1
must be greater than BIEN0.
12.3.4
AUXADC CONTROL REGISTER
Table 18 AUXADC control register (address 0100 and subaddresses)
X = don’t care during a read/or write access.
SUBADDRESS
FUNCTION
AUXADC conversion delay
value register
VALUE
11
(s2)
10
(s1)
9
(s0)
8
7
6
5
4
3
2
1
0
0
0
0
X
X
b6
b5
b4
b3
b2
b1
b0
X
Qoff
Ioff
auxoff
flag 4
flag 3
flag 2
AUXADC flag register
0
0
1
AUXADC offset value
register
1
0
0
9-bit signed offset compensation value
I channel offset value
register
1
0
1
9-bit signed offset compensation value
Q channel offset value
register
1
1
0
9-bit signed offset compensation value
Offset trigger register
1
1
1
1999 May 03
X
X
27
X
X
X
X
Q-off
flag 1B flag 1A
I-off
Aux
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
PCF50732
Table 19 AUXADC control registers value description
VALUE OF
DESCRIPTION
AUXADC conversion delay
value register
The 7-bit value (b6 to b0) denotes the delay measured in 48MCLK units between the
rising edge of TXON and the conversion on AUXADC1A. The normal power-on
settling time is added to this delay. Default value is 0.
AUXADC flag register
The AUXADC flag register returns the status of the AUXADC converters. If an
auxiliary A/D conversion is pending, the flag of the corresponding AUXADC will be
set. The flag register is read only.
AUXADC offset value register
The offset value registers contain signed 9-bit offset compensation values. These
values are subtracted automatically from all baseband receive (BBRX) and AUXADC
measurements to compensate for offset errors. The compensation values can be
Q channel offset value register
read and written and have a default value of 0. It can also be measured by the device
Offset trigger register
itself.
I channel offset value register
A write to the Offset trigger register will trigger an offset measurement for each of the
channels (Q-off, I-off or AUXADC) selected.
Offset measurements are special cases of AUXADC measurements and are done
sequentially. Each calibration measurement takes approximately 100 µs. The Offset
trigger register is write only.
12.3.5
AUXADC REGISTERS
Table 20 AUXADC registers overview
VALUE
ADDR.
REGISTER NAME
11
0101
AUXADC channel 1 register A (AUXADC1A)
0110
AUXADC channel 1 register B (AUXADC1B)
0111
AUXADC channel 2 register (AUXADC2)
1000
AUXADC channel 3 register (AUXADC3)
1001
AUXADC channel 4 register (AUXADC4)
10
9
8
7
6
5
4
3
2
1
0
b11 b10
b9
b8
b7
b6
b5
b4
b3
b2
b1
b0
Table 21 AUXADC registers value description
VALUE OF
DESCRIPTION
AUXADC1A 12-bit result of the A/D conversion on AUXADC channel 1, measured during a transmission burst
AUXADC1B 12-bit result of the A/D conversion on AUXADC channel 1, measured outside a transmission burst
AUXADC2
12-bit result of the A/D conversion on AUXADC channel 2
AUXADC3
12-bit result of the A/D conversion on AUXADC channel 3
AUXADC4
12-bit result of the A/D conversion on AUXADC channel 4
1999 May 03
28
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
12.3.6
PCF50732
VOICE BAND CONTROL REGISTER
The Voice band control register is used to control the following functionality of the voice band CODEC:
• Analog input source: microphone (MICAMP) or auxiliary (AUXMIC) input
• Analog output device: earphone (EARAMP), auxiliary (AUXAMP) or buzzer (BUZAMP) output; this register allows
individual control of all three output amplifiers
• EARAMP output mode: single-ended (EARP) or differential (EARN/EARP). This selects the input source for the
EARAMP-N amplifier. In single-ended mode EARAMP-N will be at Vref, in differential mode it will carry the output signal
• General purpose output pin: AMPCTRL
• Receive and transmit path delay values
• ASI clock mode
• TX gain boost (MICHI).
Table 22 Voice band control register (address 1010 and subaddresses)
X = don’t care during a read/or write access.
SUBADDRESS
FUNCTION
Select input source
Select output amplifier
11
(s2)
10
(s1)
9
(s0)
0
0
0
0
0
1
VALUE
FUNCTION SETTING
8
7
6
5
4
2
1
don’t care
0
1
0
don’t care
AMPCTRL pin polarity
0
1
1
don’t care
Receive path data channel
1
0
0
Transmit path data channel
1
0
1
ASI clock mode
1
1
0
don’t care
TX gain boost (MICHI)
1
1
1
don’t care
don’t care
29
0
0 MICAMP (default)
don’t care
EARAMP output mode
1999 May 03
3
1 AUXMIC
X
X
X
0 EARAMP-P off
X
X
X
1 EARAMP-P on (default)
X
X
0
X EARAMP-N off
X
X
1
X EARAMP-N on (default)
X
0
X
X AUXAMP off (default)
X
1
X
X AUXAMP on
0
X
X
X BUZAMP off (default)
1
X
X
X BUZAMP on
0 single-ended
1 differential (default)
0 active LOW
1 active HIGH (default)
d
c
b
a
d
c
b
a
4-bit delay value (default = 0)
0 single clock (default)
1 double clock
0 7 dB
1 35 dB (default)
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
12.3.7
PCF50732
VOICE BAND VOLUME REGISTER
Voice band gain settings can be independently programmed for: TXPGA, RXPGA, RXVOL and SidePGA.
Table 23 Voice band volume register (address 1011 and subaddresses)
X = don’t care during a read/or write access.
SUBADDRESS
FUNCTION
11 10
9
(s2) (s1) (s0)
VALUE
8
7
6
5
4
3
2
1
SELECTED
RANGE
0
TXPGA gain
0
0
0
X
X
X
a
b
c
d
e
f
RXPGA gain
0
0
1
X
X
X
a
b
c
d
e
f
RXVOL gain
0
1
0
X
X
X
a
b
c
d
e
f
SidePGA gain
0
1
1
X
X
X
a
b
c
d
e
f
Band gap setting level
1
0
0
X
X
X
a
b
c
X
X
X
Experimental bits
1
0
1
X
X
X dir
pll
dc
−24 to +12 dB
−30 to +6 dB
DEFAULT
SETTING
0 dB
−12 dB
mute
−100 to +75 mV 0 mV offset
vbch hclk bgb −
pll on, all
others off
Table 24 Voice band volume registers value description
VALUE
REMARKS
DESCRIPTION
TXPGA gain
microphone calibration
RXPGA gain
earphone calibration
RXVOL gain
SidePGA gain
customer volume control RXVOL and SidePGA settings use the 6-bit binary fixed point
value ‘a.bcdef’ as a multiplier for each PCM-sample. This results
−
in a control range of +6 to −30 dB (and mute). See note 1b.
Experimental bits
−
TXPGA and RXPGA settings use the 6-bit binary fixed point value
‘ab.cdef’ as a multiplier for each PCM-sample. This results in a
control range of +12 to −24 dB. See note 1a.
• dir: bypass clock buffer
• pll: clock optimizer
• dc: bypass clock capacitor
• vbch: voice band chopping
• hclk: 26 MHz master clock input
• bgb: band gap boost
Band gap setting level
do not use
Note
1. Possible gain settings are listed in Table 25 or can be calculated using the following formulae (‘n’ is an integer that
represents the value that is written into the register; n = 0 to 63):
n
a) RXPGA and TXPGA: gain = 20 × log ------ ; add 6.02 dB to each gain for RXPGA and TXPGA settings.
16
n
b) RXVOL and SidePGA: gain = 20 × log -----32
1999 May 03
30
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
12.3.7.1
PCF50732
Possible gain selections for voice band blocks: RXPGA, TXPGA, RXVOL and SidePGA
Table 25 shows the possible gain selections for the voice band blocks RXPGA, TXPG, RXVOL and SidePGA. It should
be noted that not all possible combinations of these volume settings are meaningful; setting RXPGA, SidePGA and
RXVOL to maximum will result in clipping of the output signal.
Table 25 Gain selections
GAIN (dB)
BINARY
CODE
RXPGA/TXPGA
111111
11.88
GAIN (dB)
RXVOL/SidePGA
BINARY
CODE
RXPGA/TXPGA
RXVOL/SidePGA
5.88
011111
5.72
−0.28
111110
11.74
5.74
011110
5.44
−0.56
111101
11.60
5.60
011101
5.14
−0.86
111100
11.46
5.46
011100
4.84
−1.16
111011
11.31
5.31
011011
4.52
−1.48
111010
11.17
5.17
011010
4.20
−1.80
111001
11.01
5.01
011001
3.86
−2.14
111000
10.86
4.86
011000
3.50
−2.50
110111
10.70
4.70
010111
3.13
−2.87
110110
10.54
4.54
010110
2.75
−3.25
110101
10.38
4.38
010101
2.34
−3.66
110100
10.22
4.22
010100
1.92
−4.08
110011
10.05
4.05
010011
1.47
−4.53
110010
9.88
3.88
010010
1.00
−5.00
110001
9.70
3.70
010001
0.51
−5.49
110000
9.52
3.52
010000
0.00
−6.02
101111
9.34
3.34
001111
−0.58
−6.58
101110
9.15
3.15
001110
−1.18
−7.18
101101
8.96
2.96
001101
−1.82
−7.82
101100
8.77
2.77
001100
−2.52
−8.52
101011
8.57
2.57
001011
−3.28
−9.28
101010
8.36
2.36
001010
−4.10
−10.10
101001
8.15
2.15
001001
−5.02
−11.02
101000
7.94
1.94
001000
−6.04
−12.04
100111
7.72
1.72
000111
−7.20
−13.20
100110
7.49
1.49
000110
−8.54
−14.54
100101
7.26
1.26
000101
−10.12
−16.12
100100
7.02
1.02
000100
−12.06
−18.06
100011
6.78
0.78
000011
−14.56
−20.56
100010
6.53
0.53
000010
−18.08
−24.08
100001
6.27
0.27
000001
−24.10
−30.10
100000
6.00
0.00
000000
1999 May 03
31
off
off
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
12.3.8
PCF50732
POWER CONTROL REGISTER
The Power control register is used to control power-up and power-down of the different sections of the device. Changing
the power status is accomplished by addressing the device as shown in Table 26 and setting bit 0 (= a) according to the
required state:
a = 0 → power-down
a = 1 → power-up.
Setting the baseband RX or TX flag is functionally equivalent to setting RXON or TXON respectively (logical
OR function). The CSI is also accessible when the band gap is powered down. Therefore no reset is required to power-up
after total power-down.
Table 26 Power control register (address 1100 and subaddresses)
SUBADDRESS
FUNCTION
VALUE
11
10
9
8
(s3) (s2) (s1) (s0)
7
6
5
4
3
DEFAULT
2
1
0
VALUE
STATUS
AUXDAC1
0
0
0
1
a
0
off
AUXDAC2
0
0
1
0
a
1
on
AUXDAC3
0
0
1
1
a
0
off
Voice band transmit
0
1
0
0
a
0
off
Voice band receive
0
1
0
1
a
0
off
don’t care
Vref
0
1
1
0
a
1
on
Baseband receive
1
0
0
0
a
0
off
Baseband transmit
1
0
0
1
a
0
off
Complete device
1
1
1
1
a
1
on
12.3.9
Normal operation is to write an address into the VSP
instruction RAM program counter and write low and high
bytes of the 16-bit instructions into their respective
locations. No auto-increment is foreseen, i.e. the address
register must be updated by the user. Writing to the IRAM
is only possible when voice band transmit and receive
sections are both powered off. If this is not the case write
actions are ignored.
RAM INTERFACE REGISTER
The RAM interface register is a general purpose
communication channel between the serial interface CSI
and the voice band signal processor. None of the
processor registers have default values.
The Voice band control register is used to communicate
with the voice band signal processor. Register functions
with subaddress ‘00’ to ‘11’ can be used to program the
Instruction RAM (IRAM) when the voice band processor is
not running, i.e. when voice band receive and transmit
sections are both powered down.
Reading back from the IRAM is not straightforward due to
the need for an extra clock pulse when accessing RAMs;
when reading back the contents of RAM locations 1, 2, 3
and 4 actual output is ‘undefined’ as 1, 2, 3, etc.
The IRAM registers are used to write into the voice band
instruction RAM.
1999 May 03
32
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
PCF50732
Table 27 RAM interface register (address 1101 and subaddresses)
X = don’t care during a read/or write access.
SUBADDRESS
FUNCTION
VALUE
11
(s1)
10
(s0)
9
8
7
6
5
4
3
2
1
0
VSP instruction RAM data low-byte
0
0
X
X
d7
d6
d5
d4
d3
d2
d1
d0
VSP instruction RAM data high-byte
0
1
X
X
d7
d6
d5
d4
d3
d2
d1
d0
VSP instruction RAM program counter
1
0
X
a8
a7
a6
a5
a4
a3
a2
a1
a0
VSP interface register
1
1
x9
x8
x7
x6
x5
x4
x3
x2
x1
x0
12.3.10 BASEBAND RECEIVE CONTROL REGISTER
Normal bandwidth refers to an input signal bandwidth of 100 kHz used for ZIF operation, double bandwidth is 200 kHz
used for NZIF operation. Normal sampling refers to a sampling rate of 1⁄2MCLK, double sampling refers to sampling at
MCLK.
Table 28 Baseband receive control register (address 1110)
VALUE
1
0
OUTPUT
RATE
0
0
271 kHz(1)
0
1
135 kHz
1
0
542 kHz
1
1
271 kHz
FUNCTION
11
10
normal sampling (ZIF)
0
0
double sampling; note 2
0
0
normal sampling (NZIF)
0
0
double sampling
0
0
9
8
7
6
5
4
3
2
Normal bandwidth;
don’t care
Double bandwidth;
don’t care
Notes
1. Default value.
2. Do not use this function.
1999 May 03
33
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
PCF50732
12.3.11 TEST MODE REGISTER
Only test mode 8 (TM8) is available to the end user. It is used to mark baseband-I (BB-I) samples with a logic 0 and
baseband-Q (BB-Q) samples with a logic 1 on the LSB of the 12-bit value.
Table 29 Test mode register (address 1111)
VALUE
TEST
MODE
FUNCTION
11 10
9
8
7
6
5
4
3
2
1
0
NM
normal mode (default)
0
0
0
0
TM1
baseband transmit (BBTX) I digital
0
0
0
1
TM2
baseband receive (BBRX) digital
0
0
1
0
TM3
voice band (VB) loop digital
0
0
1
1
TM4
voice band transmit/receive (VBTX/RX) digital
0
1
0
0
TM5
CSI
0
1
0
1
TM6
baseband (BB) DACs
0
1
1
0
TM7
voice band receive (VBRX) DAC current sources
0
1
1
1
TM8
I/Q marking test
1
0
0
0
TM9
voice band signal processor test mode
1
0
0
1
TM10
VSP signature output mode
1
0
1
0
TM11
MCLK input reflected on BDIO
1
0
1
1
TM12
baseband bitstream output
1
1
0
0
1999 May 03
don’t care
34
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
No buffering is foreseen for these samples, which means
that the VSP program is responsible for proper spacing in
time of the input- and output samples. Failure to ensure
proper spacing will result in heavily distorted signals.
13 VOICE BAND SIGNAL PROCESSOR (VSP)
13.1
Hardware description
The VSP used in the PCF50732 is a 30-bit fixed point VSP
with separate data and instruction areas. The data path
consists of two guard bits, 16 data bits before and 12 data
bits behind the binary point for a total of 30 bits. Twos
complement notation is used inside the data path.
Intermediate results from calculations are stored in a
64 × 30-bit wide data RAM. Data and Programmable Gain
Amplifier (PGA) settings are read in via 7 input ports and
written back into 3 output ports.
Synchronization to the 8 kHz frame-sync signals AFS is
also done under program control. The VSP program must
ensure that noise shaper and FIR filter are properly reset
before actual operation is started.
A VSP-emulator and a VSP-assembler have been written
in order to facilitate program development. The assembler
generates a stream of 16-bit words that need to be loaded
into the instruction RAM. This is done by repeated writes
to the VSP control register. The sequence would be as
follows:
The instruction path uses a 16-bit format with the 4 MSBs
designating the opcode and the trailing 12 bits used to
describe the operand. The VSP has 12 major instructions;
some instructions use two opcodes (operation codes). The
addressing range is 9 bits wide, allowing for a total of
512 instructions, which is more than adequate for the filter
types it is intended to calculate. Some room is available for
Built-In Self Test (BIST). The ALU consists of a 30-bit
subtractor, a 30-bit adder and a 30 × 16-bit ‘modified
booth’-type parallel multiplier.
1. Write address into the VSP instruction RAM program
counter register
2. Write the upper 8 bits into the VSP instruction RAM
data high-byte register
3. Write the lower 8 bits into the VSP instruction RAM
data low-byte register.
This sequence should be repeated until the VSP is fully
programmed. Programming can only be done when the
VSP is not active. The VSP program counter will be set to
location 0 and operation starts after enabling voice band
transmit or voice band receive. See also the CSI
description in Chapter 12.
The VSP’s accumulator has built-in overrange checking
and will limit values to their minimum (in case of underflow)
or maximum (in case of overflow) value.
The VSP engine is designed to operate at 4 MIPS on a
8 kHz PCM signal.
All instructions take one clock-cycle to complete. It should
be noted that since the noise shaper operates at a sample
rate of 32 kHz and the voice band filter operates at a
sample rate of 40 kHz it is necessary to transfer 4 samples
to the receive output and to read 5 samples from transmit
input for each frame.
1999 May 03
PCF50732
35
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
PCF50732
INPUT PORTS
handbook, full pagewidth
(from ADI) (from FIR)
RAM/ROM
512 × 30-BIT
CTE in
(9.0)
or
(0.12)
PC
RX in
TX in
(16.0)
CSI in
(16.0)
TXPGA
RXPGA RXVOL SidePGA
(2.4)
(12.0)
(2.4)
(1.5)
(1.5)
(1)
INPUT SELECTOR
(6.0)
(18.12)
(18.12)
FLAGS
ALU
(2.0)
RAM
64 × 30-BIT
(6.0)
INDEX
(18.12)
AFS
ACCUMULATOR
(18.12)
OUTPUT REGISTER
(16.0)
RX out
(16.0)
TX out
(to NOISE SHAPER)
(12.0)
CSI out
(to ADO)
OUTPUT PORTS
The program ROM and program counter are not shown.
(1) (x.y) designates a x + y bits wide data stream with x bits
before and y bits after the binary point.
Fig.12 Voice band Signal Processor (VSP) block diagram.
1999 May 03
36
MGR998
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
13.2
PCF50732
VSP assembler language
The stack for return addresses is only one entry deep which means that nesting of subroutines is not possible.
Table 30 VSP instruction set
X = don’t care during a read/or write access. For the description of the bit symbols see notes 1 to 8.
MNEMONIC
LDA
INSTRUCTION
Load accumulator
I3 I2 I1
I0
D11 D10 D9 D8 D7 D6 D5 D4 D3 D2 D1 D0
0
m3
c11
c10
c9
m3
m2
m1
m0 d8 d7 d6 d5 d4 d3 d2 d1 d0
0
0
c8
c7
c6
c5
c4
c3
c2
c1
c0
STO
Store accumulator
0
0
1
0
m2
m1
m0
X
X
X
d5 d4 d3 d2 d1 d0
RTN
Return from subroutine
0
0
1
1
X
X
X
X
X
X
X
X
X
X
X
X
ADD
Add to accumulator
0
1
0
m3
c11
c10
c9
c8
c7
c6
c5
c4
c3
c2
c1
c0
SUB
Subtract from
accumulator
0
1
1
Multiply with accumulator
1
MUL
JMFS
0
0
m3
m2
m1
m0 d8 d7 d6 d5 d4 d3 d2 d1 d0
m3
c11
c10
c9
m3
m2
m1
m0 d8 d7 d6 d5 d4 d3 d2 d1 d0
c8
c8
c7
c7
c6
c6
c5
c5
c4
c4
c3
c3
c2
c2
c1
c1
c0
m3
c11
c10
c9
m3
m2
m1
m0 d8 d7 d6 d5 d4 d3 d2 d1 d0
c0
Jump if flag set
1
0
1
0
f2
f1
f0
a8 a7 a6 a5 a4 a3 a2 a1 a0
JMFC
Jump if flag clear
1
0
1
1
f2
f1
f0
a8 a7 a6 a5 a4 a3 a2 a1 a0
JSFS
Jump subroutine if flag set 1
1
0
0
f2
f1
f0
a8 a7 a6 a5 a4 a3 a2 a1 a0
JSFC
Jump subroutine if flag
clear
1
1
0
1
f2
f1
f0
a8 a7 a6 a5 a4 a3 a2 a1 a0
STF
Set/clear flag
1
1
1
0
f2
f1
f0
X
X
X
X
X
X
X
X
d0
IDX
Index operations
1
1
1
1
im2
X
X
X
i5
i4
i3
i2
i1
i0
im1 im0
Notes
1. c11 to c0 denotes a 12-bit twos complement coefficient between −1 and +1.
2. m3 to m0 denotes a 4-bit instruction mode descriptor.
3. f2 to f0 denotes a 3-bit flag descriptor.
4. a8 to a0 denotes a 9-bit address.
5. i5 to i0 denotes a 6-bit index register value.
6. a8 to a0 denotes a 9-bit address.
7. X is a don’t care bit.
8. im2 to im0 denotes a 3-bit instruction mode descriptor for the IDX operator.
1999 May 03
37
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
PCF50732
Table 31 Mode descriptions
m2
m1
m0
0
0
0
0
register
R(d5 to d0)
register 0 to 63
r
0
0
0
1
register indexed
R((d5 to d0) + index) register 0 to 63
i
0
0
1
0
port
P(d2 to d0)
ports 0 to 7
p
0
0
1
1
small integer
d8 to d0
−256 to +255; note 1
s
0
1
0
0
index
index
0 to 63; note 1
i
1
MODE NAME
OPERAND
RANGE
ASSEMBLER
SHORT HAND
m3
bits 11 to 0 form a 12-bit twos complement coefficient between −1 and +1
c
Note
1. Value range in increments of 1.
Table 32 Index mode descriptions
im2
im1
im0
NAME
OPERAND
0
0
0
store
index = d5 to d0
0
0
1
increment
index = (d5 to d0) + index
1
0
0
accu
index = accu
Table 33 Flag descriptions
f2
f1
f0
NAME
DESCRIPTION
REMARKS
0
0
0
ALW
always set
0
0
1
INZ
set if index not zero used to implement loops
0
1
0
EQ0
set if accu is all 0
0
1
1
EQ1
set if accu is all 1
1
0
0
SYNC
PCM sync signal
1
0
1
A
user flag A
1
1
0
B
user flag B
1
1
1
C
user flag C
TYPE
flag is clear in VSP test mode; used to initiate BIST
system
used to sync VSP to external PCM signal
user
used to reset noise shaper and FIR filter
Table 34 Port descriptions
P2
P1
P0
NAME
0
0
0
Receive (RX)
0
0
1
0
1
0
0
1
1
1
DIRECTION
RANGE
read/write
−32768 to +32767 (16 bits)
Transmit (TX)
read/write
−32768 to +32767 (16 bits)
CSI
read/write
−2048 to +2047 (12 bits)
1
ZERO
read
fixed 0
0
0
TXPGA
read
0 to 63 (−24 to +12 dB)
0
1
RXPGA
read
0 to 63 (−24 to +12 dB)
1
1
0
RXVOL
read
0 to 63 (−20 to +6 dB)
1
1
1
SidePGA
read
0 to 63 (−20 to +6 dB)
1999 May 03
38
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
13.3
• f.l. = a 3-bit flag descriptor
Descriptions of the VSP instruction set
13.3.1
PCF50732
• addr = a 9-bit address
CONVENTIONS
• stack = a one entry deep return address stack
In the descriptions of the VSP instruction set:
• PC = a 9-bit program counter
• A = the 30-bit accumulator
• o.a. = the 9-bit old address
• I = the 6-bit index register
• s.i. = small integer
• r.a. = a 6-bit register address
• X = don’t care during a read/or write access.
• p.n. = a 3-bit port number (address)
• coeff = a 12-bit coefficient
13.3.2
LDA INSTRUCTION
The LDA (Load accumulator) instruction is used to load data into the VSP’s accumulator. Flags affected are
EQ0 and EQ1.
Table 35 LDA instruction
15 14 13 12 11 10 9 8 7 6 5 4 3
2
1
0
OPERATION
ASSEMBLER
NAME
0
0
0
1
coeff → A
LDA c <coeff> load coefficient
0
0
0
0
0
0
0 X X X
register address
R(r.a.) → A
LDA r <r.a.>
0
0
0
0
0
0
1 X X X
register address
R(r.a. + I) → A LDA i <r.a.>
coefficient
0
0
0
0
0
1
0 X X X X X X port number P(p.n.) → A
0
0
0
0
0
1
1
0
0
0
0
1
0
0 X X X X X X
13.3.3
small integer
X
X
X
load register
load register indexed
LDA p <p.n.>
load port
s.i. → A
LDA s <s.i.>
load integer
I→A
LDA x
load index
STO INSTRUCTION
The STO (Store accumulator) instruction is used to store data into register RAM or output ports. No flags are affected.
Table 36 STO instruction
15 14 13 12 11 10 9 8 7 6 5 4 3
2
1
0
OPERATION
ASSEMBLER
0
0
1
0
0
0
0 X X X
register address
A → R(r.a.)
0
0
1
0
0
0
1 X X X
register address
A → R(r.a. + I) STO i <r.a.>
0
0
1
0
0
1
0 X X X X X X port number A → P(p.n.)
1999 May 03
39
STO r <r.a.>
STO p <p.n.>
NAME
store register
store register indexed
store port
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
13.3.4
PCF50732
ADD INSTRUCTION
The ADD (Add to accumulator) instruction is used to add data to the VSP’s accumulator. Flags affected are
EQ0 and EQ1.
Table 37 ADD instruction
15 14 13 12 11 10 9 8 7 6 5 4 3
2
1
0
OPERATION
NAME
A + coeff → A
ADD c <coeff> add coefficient
register address
A + R(r.a.) → A
ADD r <r.a.>
add register
register address
A + R(r.a. + I) → A ADD i <r.a.>
add register
indexed
0
1
0
1
0
1
0
0
0
0
0 X X X
0
1
0
0
0
0
1 X X X
0
1
0
0
0
1
0 X X X X X X port number A + P(p.n.) → A
0
1
0
0
0
1
1
0
1
0
0
1
0
0 X X X X X X
13.3.5
ASSEMBLER
coefficient
small integer
X
X
X
ADD p <p.n.>
add port
A + s.i. → A
ADD s <s.i.>
add integer
A+I→A
ADD x
add index
SUB INSTRUCTION
The SUB (Subtract from accumulator) instruction is used to subtract data from the VSP’s accumulator. Flags affected
are EQ0 and EQ1.
Table 38 SUB instruction
15 14 13 12 11 10 9 8 7 6 5 4 3
2
1
0
OPERATION
NAME
A − coeff → A
SUB c <coeff> subtract
coefficient
register address
A − R(r.a.) → A
SUB r <r.a.>
subtract register
register address
A − R(r.a. + I) → A SUB i <r.a.>
subtract register
indexed
0
1
1
1
0
1
1
0
0
0
0 X X X
0
1
1
0
0
0
1 X X X
0
1
1
0
0
1
0 X X X X X X port number A − P(p.n.) → A
0
1
1
0
0
1
1
0
1
1
0
1
0
0 X X X X X X
13.3.6
ASSEMBLER
coefficient
small integer
X
X
X
SUB p <p.n.>
subtract port
A − s.i. → A
SUB s <s.i.>
subtract integer
A−I→A
SUB x
subtract index
MUL INSTRUCTION
The MUL (Multiply with accumulator) instruction is used to multiply data with the VSP’s accumulator. Flags affected are
EQ0 and EQ1. The second operand of the multiplication is restricted to 16-bit; e.g. R(r.a.).
Table 39 MUL instruction
15 14 13 12 11 10 9 8 7 6 5 4 3
2
1
0
OPERATION
NAME
A × coeff → A
MUL c <coeff> multiply
coefficient
register address
A × R(r.a.) → A
MUL r <r.a.>
multiply register
register address
A × R(r.a. + I) → A MUL i <r.a.>
multiply register
indexed
1
0
0
1
1
0
0
0
0
0
0 X X X
1
0
0
0
0
0
1 X X X
1
0
0
0
0
1
0 X X X X X X port number A × P(p.n.) → A
1
0
0
0
0
1
1
1
0
0
0
1
0
0 X X X X X X
1999 May 03
ASSEMBLER
coefficient
small integer
X
X
X
40
MUL p <p.n.>
multiply port
A × s.i. → A
MUL s <s.i.>
multiply integer
A×I→A
MUL x
multiply index
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
13.3.7
PCF50732
JMFS INSTRUCTION
The JMFS (Jump if flag set) is used for conditional jumps. The jump is carried out when the flag is set, otherwise the PC
is simply incremented.
Table 40 JMFS instruction
15 14 13 12 11 10 9 8 7 6 5 4 3 2 1 0
1
0
1
13.3.8
0
flag
OPERATION
<addr> → PC
address
ASSEMBLER
JMFS <f.l.> <addr>
JMFC INSTRUCTION
The JMFC (Jump if flag clear) is used for conditional jumps. The jump is carried out when the flag is clear, otherwise the
PC is incremented.
Table 41 JMFC instruction
15
14
13
12
1
0
1
1
13.3.9
11
10
9
8
7
6
flag
5
4
3
2
1
0
OPERATION
<addr> → PC
address
ASSEMBLER
JMFC <f.l.> <addr>
JSFS INSTRUCTION
The JSFS (Jump subroutine if flag set) is used for conditional call to a subroutine. The jump is carried out when the flag
is set, otherwise the PC is incremented. Note that the return stack is just one entry deep, so nesting of subroutines is not
allowed.
Table 42 JSFS instruction
15
14
13
12
1
1
1
0
11
10
9
8
7
6
flag
5
4
3
2
1
0
OPERATION
<o.a> → stack
address
ASSEMBLER
JSFS <f.l.> <addr>
<addr> → PC
13.3.10 JSFC INSTRUCTION
The JSFC (Jump subroutine if flag clear) is used for conditional jumps to a subroutine. The jump is carried out when the
flag is clear, otherwise the PC is incremented. It should be noted that the return stack is just one entry deep, so nesting
of subroutines is not allowed.
Table 43 JSFC instruction
15
14
13
12
1
1
1
1
11
10
9
8
7
6
flag
5
4
3
2
1
0
OPERATION
<o.a> → stack
address
ASSEMBLER
JSFC <f.l.> <addr>
<addr> → PC
13.3.11 RTN INSTRUCTION
The RTN (Return from subroutine) is used to return from a subroutine.
Table 44 RTN instruction
15
14
13
12
11
10
9
8
7
6
5
4
3
2
1
0
0
0
1
1
X
X
X
X
X
X
X
X
X
X
X
X
1999 May 03
41
OPERATION
stack → PC
ASSEMBLER
RTN
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
PCF50732
13.3.12 STF INSTRUCTION
The STF (Set/clear flag) instruction is used to set or clear the user flags A, B or C. System flags cannot be set or reset
under program control.
Table 45 STF instruction
15
14
13
12
1
1
0
0
11
10
9
flag
8
7
6
5
4
3
2
1
0
OPERATION
ASSEMBLER
X
X
X
X
X
X
X
X
value
<value> → <f.l.>
STF <f.l.> <value>
13.3.13 IDX INSTRUCTION
The IDX (Index operations) instruction is used to store and increment/decrement index values. It should be noted that
additions to the index register is done in modulo 64. A ‘decrement index register by one’ could therefore be programmed
as ‘IDX + 63’. The ‘IDX A’ instruction loads the 6 bits to the left of the binary point into the index register, i.e. it stores the
integer part modulo 64 into I.
Table 46 IDX instruction
15
14
13
12
11
10
9
8
7
6
1
1
0
1
0
0
0
X
X
X
value
<value> → I
IDX = <value>
1
1
0
1
0
0
1
X
X
X
value
I + <value> → I
IDX + <value>
1
1
0
1
1
0
0
X
X
X
13.4
5
X
4
X
3
X
2
X
1
X
0
OPERATION
X A→I
ASSEMBLER
IDX A
The assembler/emulator
A 2-pass assembler and an emulator was made to assist with the development of VSP programs. The software programs
are written in ‘C’ and currently run under NT, HPUX and LINUX operating systems. The assembler reads assembler
source files and produces a log file, sets of VHDL or Verilog stimuli and an output file containing CSI instructions that,
when loaded, will load the executable into the VSP RAM.
Requirements for the assembler source code are:
• One instruction or pseudo instruction (see Table 47) per line
• No empty lines
• A maximum of 512 instructions
• Operation always starts at instruction 0.
Table 47 Assembler pseudo instructions
MNEMONIC
INSTRUCTION
DEFINITION
. label
{<.>< ><label>}
Defines a location inside the source code. Is usually used as
an argument to JMF/JSF instructions.
define
{<define>< ><label> < ><value>
Defines a variable and assigns a value to it. These variables
can then be referenced in the assembler instructions.
include
{<include>< ><file name>}
Reads in another source code file and then continues with the
current file.
{<-->< ><comment>
Defines a comment; the rest of the line is skipped.
--
1999 May 03
42
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
PCF50732
14 LIMITING VALUES
In accordance with Absolute Maximum Rating System (IEC 134).
SYMBOL
PARAMETER
MIN.
MAX.
UNIT
VDD
supply voltage
−0.5
+3.3
V
IDD
supply current
−
30
mA
II1
DC current into any pin; except EARP/EARN, AUXSP and BUZ
−10
+10
mA
II2
DC current into pins EARP/EARN, AUXSP and BUZ
−100
+100
mA
VI
input voltages on all inputs
−0.5
VDD + 0.5 V
Ptot
total power dissipation
−
800
mW
Tamb
operating ambient temperature
−40
+85
°C
Tstg
storage temperature
−65
+150
°C
15 THERMAL CHARACTERISTICS
SYMBOL
Rth(j-a)
PARAMETER
CONDITIONS
thermal resistance from junction to ambient
VALUE
UNIT
80
K/W
in free air
16 DC CHARACTERISTICS
Tamb = −40 to +85 °C; VSS = 0 V (ground pins must be interconnected externally); VDDA ≥ VDDD;
VDDA(bb) = VDDA(vb) = VDDA(vbo) = VDDA(ref) = VDDA = 2.5 to 2.75 V (supply pins must be interconnected externally);
all voltages with respect to VSS unless otherwise specified.
SYMBOL
PARAMETER
Istb(tot)
total standby current
Pav
average power consumption
CONDITIONS
MIN.
TYP.
MAX.
UNIT
−
10
−
µA
VDDD = 1.5 V;
−
VDDA = 2.7 V; without load
on audio outputs EARP,
EARN, AUXSP and BUZ
15
−
mW
1.5
2.75
V
0.3VDDD
V
Digital power supply: VDDD
VDDD
digital supply voltage
1.0
Digital inputs: CCLK, CEN, CDI, TXON, RXON, AUXST, ADI, AFS, ACLK and RESET
−
VIL
LOW-level input voltage
VIH
HIGH-level input voltage
0.7VDDD
−
VDDD
V
ILI
input leakage current
−
±1
−
µA
0.0
Digital outputs: BIEN, BOEN, ADO and AMPCTRL
VOL
LOW-level output voltage
Isink = 1.5 mA
−
−
0.2VDDD
V
VOH
HIGH-level output voltage
Isource = 1.5 mA
0.7VDDD
−
−
V
Digital output: BIOCLK
VOL
LOW-level output voltage
Isink = 1.5 mA
−
−
0.2VDDD
V
VOH
HIGH-level output voltage
Isource = 1.5 mA
0.7VDDD
−
−
V
1999 May 03
43
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
SYMBOL
PARAMETER
PCF50732
CONDITIONS
MIN.
TYP.
MAX.
UNIT
Digital bidirectional pins: CDO and BDIO
VIL
LOW-level input voltage
0.0
−
0.3VDDD
V
VIH
HIGH-level input voltage
0.7VDDD
−
VDDD
V
ILI
input leakage current
−
±1
−
µA
VOL
LOW-level output voltage
Isink = 1.5 mA
−
−
0.2VDDD
V
VOH
HIGH-level output voltage
Isource = 1.5 mA
0.7VDDD
−
−
V
−
±1
−
µA
2.5
2.7
2.75
V
VDDD = 1.5 V;
VDDA = 2.7 V;
RXON active
−
3.5
−
mA
no external load
−
1.25
−
V
−
0.1
−
µA
1.175
1.25
1.325
V
−
0.5Vref
−
V
−
0.5Vref
−
V
−
Vref
−
V
−
Vref
−
V
−
Vref
−
V
Low-swing clock input: MCLK
ILI
input leakage current
Analog power supplies: VDDA(bb), VDDA(vb), VDDA(vbo) and VDDA(ref)
VDDA
analog supply voltage
IDDA
analog supply current
Analog reference pin: Vref
Vref
DC reference level
II(ref)
input source/sink current
Analog output pins: IP, IN, QP and QN
Vbias(TXIQ)
DC bias level
Analog input pins: MICP and MICN
Vref(MIC)
DC input reference level
Analog input pins: AUXMICP and AUXMICN
Vref(AUXMIC)
DC input reference level
Analog output pins: EARP and EARN
Vbias(EAR)
DC bias level
Analog output pin: AUXSP
Vbias(AUX)
DC bias level
Analog output pin: BUZ
Vbias(BUZ)
1999 May 03
DC bias level
44
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
PCF50732
17 AC CHARACTERISTICS
VDDD = 1.0 to 2.75 V; VDDA = 2.5 to 2.75 V; Tamb = −40 to +85 °C; unless otherwise specified.
SYMBOL
fclk
PARAMETER
CONDITIONS
MIN.
−
master clock frequency
TYP.
13.0
MAX.
UNIT
−
MHz
Digital input pins: CCLK, CEN, CDI, TXON, RXON, AUXST, ADI, AFS, ACLK and RESET
Ci
input capacitance
−
5.0
−
pF
Digital output pins: BIOCLK, BIEN, BOEN, ADO and AMPCTRL
tdLHO
output rise time
output load = 10 pF
−
10
−
ns
tdHLO
output fall delay
output load = 10 pF
−
10
−
ns
Digital bidirectional pins: CDO and BDIO
Ci
input capacitance
−
5.0
−
pF
tdLHO
output rise time
output load = 20 pF
−
10
−
ns
tdHLO
output fall delay
output load = 20 pF
−
10
−
ns
note 1
0.1
−
0.5VDDD
V
40
−
60
%
Low-swing clock input: MCLK
VMCLK
input amplitude
δMCLK
duty cycle
Analog output pins: IP, IN, QP and QN
tst(TXIQ)
output settling time
output load = 10 pF // 10 kΩ,
to 1 LSB, for 0.8 to 2.2 V
−
9.6
−
µs
Ro(TXIQ)
output resistance
f < 100 kHz
−
105
−
Ω
differential
200
−
−
kΩ
−
5
−
pF
−
1
−
MΩ
200
220
320
kΩ
200
220
−
kΩ
f = 1 kHz
0
−
1
Ω
f = 1 kHz
0
−
1
Ω
f = 1 kHz
0
−
1
Ω
Analog input pins: IP, IN, QP and QN
Ri(RXIQ)
input resistance
Ci(RXIQ)
input capacitance
Analog input pins: AUXADC1, AUXADC2, AUXADC3 and AUXADC4
Ri(AUXADC)
input resistance
Analog input pins: MICP and MICN
Ri(eq)(MIC)
equivalent input resistance
differential
Analog input pin: AUXMICP and AUXMICN
Ri(eq)(AUXMIC)
equivalent input resistance
Analog output pins: EARP and EARN
Ro(EARAMP)
output resistance
Analog output pin: AUXSP
Ro(AUXAMP)
output resistance
Analog output pin: BUZ
Ro(BUZ)
output resistance
Note
1. Input MCLK is internally AC coupled; the signal must not go below VSS or above VDDD.
1999 May 03
45
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
PCF50732
18 FUNCTIONAL CHARACTERISTICS
18.1 Baseband transmit (BSI to TXI/Q)
VDDA = 2.5 to 2.75 V; Tamb = −40 to +85 °C.
SYMBOL
PARAMETER
CONDITIONS
MIN.
TYP.
MAX.
UNIT
RESTXIQ
resolution of TX DACs
−
10
−
bit
S/NTXIQ
signal-to-noise TX DACs
−
55
−
dB
FSINTXIQ
input sampling frequency
−
270.833 −
kHz
VO(TXIQ)(p-p)
output signal amplitude (peak-to-peak
value)
0.9
1.0
1.1
V
VDC(TXIQ)
output DC level
1.15
1.25
1.35
V
AMATTXIQ
output amplitude matching between
I and Q TX paths
note 1
−1.75
−
+1.75
%
−0.15
−
+0.15
dB
VOFSTXIQ
differential DC offset voltage between
IP/IN or QP/QN
note 1
−4.5
−
+4.5
mV
FRESPTXIQ
frequency response of random output
signal
f = 0 to 100 kHz
−3
−
−
dB
f = 200 kHz
−
−
−30
dB
f = 250 kHz
−
−
−33
dB
f = 400 kHz
−
−
−60
dB
f = 600 kHz
−
−
−70
dB
f = 1200 kHz
−
−
−70
dB
f > 1800 kHz
−
−
−70
dB
note 1
MPEITXIQ
maximum phase effect instance
note 2
−
22
−
µs
AGDTXIQ
absolute group delay
note 1
−
10
−
µs
GDLTXIQ
group delay linearity
−
100
−
ns
GDMATTXIQ
measured at full-scale;
10
kHz < f < 100 kHz;
group delay matching of I and Q TX paths
load: 10 pF // 10 kΩ
−
−
40
ns
PMATTXIQ
phase matching of I and Q TX paths
note 1
−
0.5
−
deg
PTERMSTXIQ
RMS phase trajectory error
random input pattern;
notes 1 and 3
−
0.5
0.8
deg
−
1.5
3.0
deg
PTEPEAKTXIQ peak phase trajectory error
Notes
1. Measured at full-scale; load: 10 pF // 10 kΩ; f = 67 kHz.
2. Not tested. Defined between the rising edge of BIOCLK which latches a data bit at BDIO to its corresponding
maximum phase change on the analog outputs ITX and QTX.
3. Not tested.
1999 May 03
46
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
PCF50732
18.2 Baseband receive (RXI/Q to BSI)
VDDA = 2.5 to 2.75 V; Tamb = −40 to +85 °C; all values valid for ZIF and NZIF modes.
SYMBOL
PARAMETER
CONDITIONS
MIN.
TYP.
MAX. UNIT
−
12
−
bit
−
66
−
dB
1.0
1.25
1.5
V
(IP − IN); (QP − QN)
−1.5
−
1.5
V
Baseband receive control register = 0X
−
6.5
−
MHz
Baseband receive control register = 1X
−
13
−
MHz
FSOUTRXIQ output sample rate
Baseband receive control register = 00 or 11
−
270.833 −
kHz
Baseband receive control register = 10
−
541.667 −
kHz
FRESPRXIQ frequency response
Baseband receive control register = 0X; note 1
f = 0 to 70 kHz; VIDM(RXIQ) = 150 mV (p-p)
−0.8
0
+0.3
dB
f = 90 kHz; VIDM(RXIQ) = 150 mV (p-p)
−
−3.5
−
dB
f = 100 kHz; VIDM(RXIQ) = 150 mV (p-p)
−
−5.5
−
dB
f = 200 kHz; VIDM(RXIQ) = 150 mV (p-p)
−
−
−35
dB
f > 220 kHz; VIDM(RXIQ) = 150 mV (p-p)
−
−
−45
dB
f = 0 to 140 kHz; VIDM(RXIQ) = 150 mV (p-p)
−0.8
0
+0.3
dB
f = 180 kHz; VIDM(RXIQ) = 150 mV (p-p)
−
−3.5
−
dB
f = 200 kHz; VIDM(RXIQ) = 150 mV (p-p)
−
−5.5
−
dB
f = 400 kHz; VIDM(RXIQ) = 150 mV (p-p)
−
−
−35
dB
f > 440 kHz; VIDM(RXIQ) = 150 mV (p-p)
−
−
−45
dB
RESRXIQ
resolution
I and Q word length at BSI
S/NRXIQ
signal to noise ratio
VICM(RXIQ)
input common mode
voltage
(IP + IN)/2; (QP + QN)/2; referred to VSS
VIDM(RXIQ)
input differential
voltage
FSINRXIQ
input sampling
frequency
Baseband receive control register = 1X;
note 1 and 2
DYNRXIQ
SINADRXIQ
dynamic signal range
ZIF mode
f = 20 Hz to 135 kHz
60
68
−
dB
NZIF mode
f = 20 Hz to 270 kHz
60
68
−
dB
f = 20.0 kHz; VIDM(RXIQ) = 2 V (p-p)
40
−
−
dB
f = 67.7 kHz; VIDM(RXIQ) = 2 V (p-p)
−
65
−
dB
f = 20 kHz; VIDM(RXIQ) = 150 mV (p-p)
−
40
−
dB
signal to noise and
distortion ratio
f = 67.7 kHz; VIDM(RXIQ) = 150 mV (p-p)
−
40
−
dB
OPC
output code in BDIO
for maximum input amplitude
−
±1440
−
LSB
PSRRRXIQ
power supply ripple
rejection
applying a 100 mV (p-p)/217 Hz sine wave on
top of the analog power supply
−
70
−
dB
GERRRXIQ
gain error
referenced to maximum amplitude
−6
−
+6
%
−0.5
−
+0.5
dB
−3
−
+3
%
GMATRXIQ
gain matching error
at maximum input level
GDMATRXIQ group delay matching measured at full-scale; 10 kHz < f < 100 kHz;
of I and Q RX paths
output load = 10 pF // 10 kΩ
1999 May 03
47
−0.25 −
+0.25 dB
−
5
−
ns
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
SYMBOL
PARAMETER
TYP.
MAX. UNIT
−40
−
+40
mV
after compensation
−5
−
+5
mV
ZIF mode
−
52
−
µs
NZIF mode
−
26
−
µs
ZIF mode
−
23
−
µs
NZIF mode
−
11.5
−
µs
offset error
POSTRXIQ
power-on settling
time
including decimation filter
filter group delay
Notes
1. Reference level is full-scale input at 67 kHz.
2. This will not be tested.
1999 May 03
MIN.
before compensation
OFFSRXIQ
FGDRXIQ
CONDITIONS
PCF50732
48
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
PCF50732
18.3 Voice band transmit (microphone to ASI)
VDDA = 2.5 to 2.75 V; Tamb = −40 to +85 °C.
SYMBOL
PARAMETER
CONDITIONS
MIN. TYP. MAX.
RESMICADC
resolution of ADC
−
13
FSINMICADC
internal sampling
frequency
−
1000 −
kHz
GRANTXPGA
calibration gain range
−24
0
+12
dB
GSTPTXPGA
calibration gain step
size
see Table 25
−
64
−
steps
GTOLVBTX
gain tolerance of coder
at TXPGA = 0 dB
−1.5 −
+1.0
dB
FRESPVBTX
digital filter frequency
response of
implemented standard
VSP software (version:
vb5_all)
f < 100 Hz
−
−
−20
dB
100 Hz < f < 200 Hz
−
−
−10
dB
f = 300 Hz to 3.3 kHz
−1
−
+1
dB
f = 3.3 to 3.4 kHz
−1.5 −
0
dB
f ≥ 4 kHz
−
−
−20
dB
FREJVBTX
out-of-band rejection
−
UNIT
bit
f = 4.6 kHz
40
45
−
dB
f = 6 to 30 kHz
45
50
−
dB
TXPGA = 0 dB, MICHI = 1
−
−35
−
dBm
TXPGA = 0 dB, MICHI = 0
−
−7
−
dBm
−
−
−75
dBm0p(2)
Microphone/auxiliary signal path
VIN(rms)
NIDLE
nominal input level
(RMS value)
idle noise level
(pin ADO)
psophometrically
weighted(1);
Tamb = 25 °C
THD
total harmonic distortion f = 1 kHz; PGA = −4 dB; ADO = +2 dBm0
−
−
1
%
SINAD
signal-to-noise and
distortion
ADO = 3 dBm0
30
−
−
dB
ADO = 0 dBm0
40
−
−
dB
ADO = −10 dBm0
45
−
−
dB
ADO = −20 dBm0
45
−
−
dB
ADO = −30 dBm0
40
−
−
dB
ADO = −40 dBm0
30
−
−
dB
ADO = −45 dBm0
25
−
−
dB
applying a 100 mV (p-p)/217 Hz sine wave
on top of the analog power supply
−
−
2
LSB
PSCTVBTX
power supply crosstalk
Audio Serial Interface (ASI)
FASOUT
PCM output bit rate
128
−
2048 kbits/s
FSYNCAFS
PCM frame
synchronization
frequency at pin AFS
−
8
−
kHz
Notes
1. Psophometrical weighting: a frequency weighting curve described in “ITU recommendation O.41”.
2. The unit dBm0p: 0 dBm0p is generally defined as −3.14 dBFS, where dBFS denotes dB full scale, i.e. a signal with
an amplitude covering the complete range of digital values. The suffix ‘p’ refers to psophometrical weighting.
1999 May 03
49
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
PCF50732
18.4 Voice band receive (ASI to earphone)
VDDA = 2.5 to 2.75 V; Tamb = −40 to +85 °C
SYMBOL
PARAMETER
CONDITIONS
MIN.
TYP.
MAX.
UNIT
RESEARDAC
resolution of DAC
−
13
−
bit
FSINEARDAC
internal sampling
frequency
−
1000
−
kHz
GRANVOL
gain step range
−30
−12
+6
dB
GSTPVOL
gain step size
−
64
−
steps
GRANPGA
calibration PGA range
−24
−
+12
dB
GSTPPGA
gain step size
−
64
−
steps
GTOLVBRX
gain tolerance of
decoder
−1
−
+1
dB
40
−
−
dB
f = 0 to 100 Hz
−
−
−20
dB
f = 300 to 3300 Hz
−1.0
−
+1.0
dB
f = 3300 to 3400 Hz
−2.0
−
+1.0
dB
f = 4000 Hz
−
−
−18
dB
f = 4600 Hz
38
−
−
dB
f = 28.6 kHz
40
−
−
dB
digital steps; see Table 25
digital steps; see Table 25
GMUTEVBRX mute attenuation of
decoder
FRESPVBRX
FREJVBRX
digital filter frequency
response of
implemented standard
VSP software (version:
vb5_all)
out-of-band rejection
Audio Serial Interface (ASI)
FASIN
PCM input bit rate
128
−
2048
kbits/s
FSYNCAFS
PCM frame
synchronization
frequency at pin AFS
−
8
−
kHz
Earphone output: EARP and EARN
Vref(EAR)
DC reference level
−
Vref
−
V
Vo(EAR)(p-p)
output voltage
(peak-to-peak value)
load: 16 Ω differential
−
2
−
V
load: 8 Ω single-ended
−
1.5
−
V
Io(EAR)peak
output source/sink
current
load: 8 Ω single-ended
−
100
−
mA
GAINEARVOL
nominal gain from ASI
to EARP/EARN
GRANVOL = −12 dB; load 32 Ω
differential
−13
−12
−11
dB
single-ended
−19
−18
−17
dB
+5
−
+41
dB
−
−
1
%
−
−
−72
dBmp(2)
GRANSIDVOL total sidetone gain
(from MICP/MICN to
EARP/EARN)
THDEAR
IDLNEAR
1999 May 03
total harmonic distortion GRANEARVOL = −12 dB
idle noise at
EARP/EARN
weighted(1);
psophometrically
GRANEARPGA = 0 dB
50
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
SYMBOL
SINADEAR
PSRREAR
PARAMETER
signal-to-noise and
distortion ratio from ASI
to earphone
power supply ripple
rejection at
EARP/EARN
PCF50732
CONDITIONS
psophometrically
MIN.
TYP.
MAX.
UNIT
weighted(1)
at 3 dBm0 input signal level
30
−
−
dB
at 0 dBm0 input signal level
35
−
−
dB
at −10 dBm output signal level 45
−
−
dB
at −20 dBm output signal level 42
−
−
dB
at −30 dBm output signal level 40
−
−
dB
at −40 dBm output signal level 30
−
−
dB
at −45 dBm output signal level 25
−
−
dB
−
−
dB
applying a 100 mV (p-p)/217 Hz
sine wave on top of the analog
power supply
70
−
Vref
−
V
load: 16 Ω with 47 µF in series
to ground
−
Vref ±1
−
V
load: 8 Ω with 100 µF in series
to ground
−
Vref ±0.77
−
V
Auxiliary output: AUXSP
Vref(AUXSP)
DC reference level
Vo(AUXSP)
output voltage
Io(AUXSP)peak
output source/sink
current
load: 16 Ω with 47 µF in series to −
ground
62.5
−
mA
GAINAUXSP
nominal gain from ASI
to AUXSP
load: 16 Ω with 47 µF in series
to ground; GRANVOL = −12 dB
−19
−18
−17
dB
−
Vref
−
V
load: 8 Ω with 100 µF in series
to ground
−
Vref − 0.77 −
V
−
100
−
mA
load: 8 Ω with 100 µF in series
to ground; GRANVOL = −12 dB
−19
−18
−17
dB
Buzzer output: BUZ
Vref(BUZ)
DC reference level
Vo(BUZ)
output voltage
Io(BUZ)peak
output source/sink
current
GAINBUZ
nominal gain from ASI
to BUZ
Notes
1. Psophometrical weighting: a frequency weighting curve described in “ITU recommendation O.41”.
2. The unit dBmp: 0 dBmp refers to a voltage of a signal of 1 mW across a 600 Ω load. The suffix ‘p’ refers to
psophometrical weighting.
1999 May 03
51
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
PCF50732
18.5 Auxiliary digital-to-analog converters
VDDA = 2.5 to 2.75 V; Tamb = −40 to +85 °C.
SYMBOL
PARAMETER
CONDITIONS
MIN.
TYP.
MAX.
UNIT
AUXDAC1
RESDAC1
resolution
−
8
−
bit
VOMINDAC1
minimum output voltage
register value: 000H
0
−
0.15
V
VOMAXDAC1
maximum output voltage
register value: 0FFH
2.1
2.2
2.3
V
VDEFDAC1
output voltage after reset
register value: 085H
−
1.147
−
V
MONDAC1
monotonicity range
−
8
−
bit
−5.0
−
+5.0
LSB
−1.0
−
+1.0
LSB
−80
−
+80
mV
load: 50 pF // 2 kΩ, to VSS; −
see Fig.13a
−
40
−
µs
8
−
µs
−
12
−
bit
INLDAC1
integral
non-linearity(1)
non-linearity(2)
DNLDAC1
differential
OFFSDAC1
offset error
FSSTDAC1
full-scale settling time
LSBSTDAC1
one LSB settling time
AUXDAC2
RESDAC2
resolution
VOMINDAC2
minimum output voltage
register value: 000H
0
−
0.15
V
VOMAXDAC2
maximum output voltage
register value: FFFH
2.1
2.2
2.32
V
VDEFDAC2
output voltage after reset
register value: 800H
−
1.1
−
V
MONDAC2
monotonicity range
−
12
−
bit
INLDAC2
integral non-linearity(1)
−
±10
−
LSB
DNLDAC2
differential non-linearity(2)
−1.0
−
+2.0
LSB
OFFSDAC2
offset error
−25
−
+25
mV
FSSTDAC2
full-scale settling time
40
−
µs
one LSB settling time
load: 50 pF // 10 kΩ, to
VSS; see Fig.13b
−
LSBSTDAC2
−
8
−
µs
POSTDAC2
power-on settling time
see Section 18.1
−
−
4
ms
−
10
−
bit
0
−
0.15
V
AUXDAC3
RESDAC3
resolution
VOMINDAC3
minimum output voltage
register value: 000H
register value: 3FFH
VOMAXDAC3
maximum output voltage
2.1
2.2
2.3
V
MONDAC3
monotonicity range
−
10
−
bit
INLDAC3
integral non-linearity(1)
−5.0
−
+5.0
LSB
−1.0
−
+1.0
LSB
−40
−
+40
mV
10
15
µs
non-linearity(2)
DNLDAC3
differential
OFFSDAC3
offset error
FSSTDAC3
full-scale settling time
LSBSTDAC3
one LSB settling time
SSCDAC3
output source/sink current
load: 50 pF // 1 kΩ, to VSS; 1
see Fig.13c
−
−
2.5
−
µs
−
2.5
mA
Notes
1. INL: the difference of the output to the best fit line. INL(i) = [V(i) − (a + i × b)]/1 LSB; INL = (INL(i)(max) − INL(i)(min))/2.
2. DNL is the difference between individual code width and average code width (1 LSB); maximum and minimum
specified. DNL(i) = [(V(i + 1) − V(i) − 1 LSB)/1 LSB]; DNL(min) > −1 is equivalent to monotonicity V(i + 1) > V(i).
1999 May 03
52
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
PCF50732
18.6 Auxiliary analog-to-digital converters: AUXADC1, AUXADC2, AUXADC3 and AUXADC4
VDDA = 2.5 to 2.75 V; Tamb = −40 to +85 °C.
SYMBOL
PARAMETER
CONDITIONS
MIN.
TYP.
MAX.
UNIT
−
1440
−
input voltage
0.0
−
2.0
V
Vin for output code 0
−20
−
20
mV
−
2.0
−
V
input resistance
−
1.0
−
MΩ
integral non-linearity
−
2.5
−
mV
DNLAUXADC
differential non-linearity
−
2.5
−
mV
GERRAUXADC
gain error
−0.5
−
+ 0.5
OFFSAUXADC
offset error after compensation
−3
−
3
LSB
POSTAUXADC
power-on settling time
−
170
−
µs
RESAUXADC
resolution
coded in 12 bits
VINAUXADC
VINAUXADCMIN
VINAUXADCMAX
Vin for output code +1820
Ri(AUXADC)
INLAUXADC
after offset compensation
Vi = Vref
LSB
dB
18.7 Typical total current consumption
The typical total current consumption values for the chip in different modes; Tamb = 25 °C.
TOTAL CURRENT (mA)
ACTIVITY
REMARKS
NOTE 1
NOTE 2
3.96
4.04
Baseband
transmit
receive
baseband transmit + references + MCLK + BSI
5.14
5.41
baseband receive + references + MCLK + BSI
4.79
4.94
voice band transmit and receive + references
+ 13 MHz + auxiliary DAC2; note 3
baseband transmit
7.32
7.51
voice band transmit and receive + baseband transmit
+ references + 13 MHz + CSI + auxiliary DACs 2 and 3
baseband receive
8.52
8.91
voice band transmit and receive + baseband receive
+ references + 13 MHz + auxiliary DAC 2
Auxiliary ADC function
2.75
2.86
auxiliary ADC + CSI + references + 13 MHz + auxiliary
DAC2
Auxiliary DAC1
2.35
2.49
auxiliary DACs 1 and 2 + references + 13 MHz
Auxiliary DAC2
1.55
1.59
auxiliary DAC2 + references + 13 MHz
Auxiliary DAC3
4.35
4.56
auxiliary DACs 3 and 2 + CSI + baseband transmit
+ references + 13 MHz
Idle with MCLK running
0.23
0.24
references + 13 MHz clock
Idle no MCLK; references on
0.18
0.19
references; see Section 19.1.1 “Possibility 1”
Idle
0.01
0.01
all blocks in power-down, no 13 MHz clock
Voice band transmit and receive
Voice band transmit and receive
Notes
1. VDDD = 2.3 V; VDDA = 2.65 V; external interface current is not included.
2. VDDD = 2.6 V; VDDA = 2.65 V; external interface current is not included.
3. For a signal at the earpiece differential output of amplitude ‘A’ across a load resistance of ‘R’, the current ‘I’ must be
4 A
added, where: I = --- ⋅ ---- .
π R
1999 May 03
53
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
18.8
PCF50732
Typical output loads
Figure 13 illustrates the typical loads for the outputs: AUXDAC1, AUXDAC2, AUXDAC3, EARP, EARN, AUXSP and
BUZ.
handbook, halfpage
handbook, halfpage
AUXDAC1
50
pF
AUXDAC2
50
pF
2
kΩ
VSSA
VSSA
MBL023
MBL024
a. AUXDAC1.
b. AUXDAC2.
handbook, halfpage
handbook, halfpage
10
kΩ
AUXDAC3
50
pF
EARP
or
AUXSP
1
kΩ
800 µH
100 pF
16 Ω
VSSA
EARN
MBH602
MBL020
c. AUXDAC3.
ndbook, halfpage
AUXSP
or
BUZ
d. EARP/EARN or AUXSP.
8Ω
handbook, halfpage
AUXSP
or
BUZ
16 Ω
47 µF
100 µF
VSS
VSS
MGS172
MBL021
e. AUXSP or BUZ; R = 8 Ω.
f. AUXSP or BUZ; R = 16 Ω.
Fig.13 Typical output loads.
1999 May 03
54
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
PCF50732
19 APPLICATION INFORMATION
handbook, full pagewidth
G14
BUS
RFCLK
RFDO
G11
RFDI
G13
RFE_N1
F13
RFE_N2
F11
VDDD
68 nF
VDDA
VDDA(vbo)
68 nF
68 nF
CLOCK
DATA
AUXST
RFSIG[x]
7
13
CCLK
CDI
CEN
CDO
47
25 34 37
9
11
21
10
22
12
23
PCF5087X
H13
J13
J11
H14
24
BIOCLK
SIOXCLK
SOXEN_N
BIEN
BDIO
SIOXD
SIXEN_N
BOEN
15
16
27
17
28
TXON
RFSIG[z]
RXON
19
31
32
20
33
PCF50732
EXTERNAL
IOM2
B11
A11
D11
B10
FSC
AFS
DCL
ACLK
DU
ADO
DD
ADI
AMPCTRL
L7
CKI
MCLK
30
3
4
38
1
39
18
IP
IA
IN
IB
QP
QA
QN
QB
7
OM5178
8
9
10
AUXDAC1
13 MHz ON
AUXDAC2
VCXO
AUXDAC3
PA-CONTROL
CIRCUITRY
AUXADC1
CHARGER
BATTERY VOLTAGE
BATTERY TEMPERATURE
AMBIENT TEMPERATURE
BATTERY TYPE
AUXADC2
AUXADC3
AUXADC4
AUXMICP
microphone
supply
AUXMICN
2
microphone
supply
14
41
6
40
K14 K12
RSTO_N
16
13 MHz
18
29
RFSIG[y]
EN
17
46
MICP
MICN
EARP
RST_N
RESET
system
reset
Vref
68
nF
5
45
36
44
8
26 35 42 48
43
EARN
AUXSP
BUZ
MGS173
(1) 10 nF can be used instead of 100 nF for high-pass filtering.
Fig.14 Application diagram.
1999 May 03
55
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
19.1
A down-counter increases the band gap output drive
capability for 32768 MCLK cycles which equals
approximately 2.5 ms. After that time the voltage at Vref
has reached ±0.5 mV of its final value. The timing diagram
illustrates the situation (see Fig.15). Other points to note
for this possibility:
Wake-up procedure from Sleep mode
Apart from being the status control signal of AUXDAC1,
AUXDAC2 and the MCLK input, AUXST also starts a
down-counter at each rising edge which controls the
output drive capability of pin Vref. This is important for the
following considerations. For current consumption
reduction during Sleep mode there are two possibilities as
shown in Section 19.1.1 and 19.1.2.
19.1.1
• As long as VDDD is not switched off, all registers keep
their values.
• As long as VDDA(bb) is not stable, the internal master
clock is not running, because the first stage of the clock
generator is supplied by VDDA.
POSSIBILITY 1
Program every block into power-down via CSI except for
the band gap, then pull AUXST LOW to switch off the clock
internally. This results in a IDD(total) = 60 µA (typical). Since
the band gap hasn’t been programmed into power-down,
the only active reference is Vref. After a rising edge of
AUXST, POSTDAC is in the order of 1.5 ms.
19.1.2
• All digital signals MUST remain stable for tMCLK after
AUXST has gone HIGH. This is necessary to avoid any
timing violations in the digital part of the PCF50732
caused by an unstable MCLK clock input.
• The previously mentioned 2.5 ms for tBG are only valid
for CVref = 68 nF ±10% or less. The maximum of value
68 nF is highly recommended for good noise and power
supply rejection figures.
POSSIBILITY 2
If AUXST is also used to switch off the analog power
supply, all references are shut down. The power-up time in
this case is measured from the point where the MCLK
clock input has valid levels or VDDA has settled to its final
value (the latter of the two signals sets the reference
point).
handbook, full pagewidth
PCF50732
POSTDAC
t MCLK
(4 ms)
t BG
t VDD
(2.5 ms)
VDDA
Vref
MCLK
AUXST
AUXDAC1/
AUXDAC2
MGR999
tVDD: settling time until VDDA(bb) has reached 95% of its final value. It is assumed that tMCLK > tVDD; otherwise tBG and POSTDAC are related to tVDD.
tMCLK: settling time until MCLK clock has reached at least 100 mV (peak-to-peak) level and a frequency of 13 MHz ±10 kHz.
tBG: settling time until voltage at Vref has reached ±0.5 mV of its final value for CVref = 68 nF ±10%.
POSTDAC: settling time until AUXDAC1 and AUXDAC2 has reached the previously programmed value ±2 LSBs.
Fig.15 Possible timing of wake-up sequence.
1999 May 03
56
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
19.2
PCF50732
Microphone input connection and test set-up
microphone
supply
handbook, halfpage
2 kΩ
handbook, halfpage
MICP
MICP
100 nF
MICN
100 nF
100 nF (1)
MICN
100 nF (1)
2 kΩ
MGS171
MBL022
(1) 10 nF can be used instead of 100 nF for high-pass filtering.
a. Microphone input connection.
b. Microphone input test set-up.
Fig.16 Microphone input connection and test set-up.
1999 May 03
57
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
PCF50732
20 PACKAGE OUTLINE
LQFP48: plastic low profile quad flat package; 48 leads; body 7 x 7 x 1.4 mm
SOT313-2
c
y
X
36
25
A
37
24
ZE
e
E HE
A A2
(A 3)
A1
w M
pin 1 index
θ
bp
Lp
L
13
48
detail X
12
1
ZD
e
v M A
w M
bp
D
B
HD
v M B
0
2.5
5 mm
scale
DIMENSIONS (mm are the original dimensions)
UNIT
A
max.
A1
A2
A3
bp
c
D (1)
E (1)
e
HD
HE
L
Lp
v
w
y
mm
1.60
0.20
0.05
1.45
1.35
0.25
0.27
0.17
0.18
0.12
7.1
6.9
7.1
6.9
0.5
9.15
8.85
9.15
8.85
1.0
0.75
0.45
0.2
0.12
0.1
Z D (1) Z E (1)
θ
0.95
0.55
7
0o
0.95
0.55
o
Note
1. Plastic or metal protrusions of 0.25 mm maximum per side are not included.
OUTLINE
VERSION
REFERENCES
IEC
JEDEC
EIAJ
ISSUE DATE
94-12-19
97-08-01
SOT313-2
1999 May 03
EUROPEAN
PROJECTION
58
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
If wave soldering is used the following conditions must be
observed for optimal results:
21 SOLDERING
21.1
Introduction to soldering surface mount
packages
• Use a double-wave soldering method comprising a
turbulent wave with high upward pressure followed by a
smooth laminar wave.
This text gives a very brief insight to a complex technology.
A more in-depth account of soldering ICs can be found in
our “Data Handbook IC26; Integrated Circuit Packages”
(document order number 9398 652 90011).
• For packages with leads on two sides and a pitch (e):
– larger than or equal to 1.27 mm, the footprint
longitudinal axis is preferred to be parallel to the
transport direction of the printed-circuit board;
There is no soldering method that is ideal for all surface
mount IC packages. Wave soldering is not always suitable
for surface mount ICs, or for printed-circuit boards with
high population densities. In these situations reflow
soldering is often used.
21.2
PCF50732
– smaller than 1.27 mm, the footprint longitudinal axis
must be parallel to the transport direction of the
printed-circuit board.
The footprint must incorporate solder thieves at the
downstream end.
Reflow soldering
Reflow soldering requires solder paste (a suspension of
fine solder particles, flux and binding agent) to be applied
to the printed-circuit board by screen printing, stencilling or
pressure-syringe dispensing before package placement.
• For packages with leads on four sides, the footprint must
be placed at a 45° angle to the transport direction of the
printed-circuit board. The footprint must incorporate
solder thieves downstream and at the side corners.
Several methods exist for reflowing; for example,
infrared/convection heating in a conveyor type oven.
Throughput times (preheating, soldering and cooling) vary
between 100 and 200 seconds depending on heating
method.
During placement and before soldering, the package must
be fixed with a droplet of adhesive. The adhesive can be
applied by screen printing, pin transfer or syringe
dispensing. The package can be soldered after the
adhesive is cured.
Typical dwell time is 4 seconds at 250 °C.
A mildly-activated flux will eliminate the need for removal
of corrosive residues in most applications.
Typical reflow peak temperatures range from
215 to 250 °C. The top-surface temperature of the
packages should preferable be kept below 230 °C.
21.3
21.4
Wave soldering
Fix the component by first soldering two
diagonally-opposite end leads. Use a low voltage (24 V or
less) soldering iron applied to the flat part of the lead.
Contact time must be limited to 10 seconds at up to
300 °C.
Conventional single wave soldering is not recommended
for surface mount devices (SMDs) or printed-circuit boards
with a high component density, as solder bridging and
non-wetting can present major problems.
To overcome these problems the double-wave soldering
method was specifically developed.
1999 May 03
Manual soldering
When using a dedicated tool, all other leads can be
soldered in one operation within 2 to 5 seconds between
270 and 320 °C.
59
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
21.5
PCF50732
Suitability of surface mount IC packages for wave and reflow soldering methods
SOLDERING METHOD
PACKAGE
REFLOW(1)
WAVE
BGA, SQFP
not suitable
HLQFP, HSQFP, HSOP, HTSSOP, SMS not
PLCC(3),
SO, SOJ
suitable
suitable(2)
suitable
suitable
suitable
LQFP, QFP, TQFP
not recommended(3)(4)
suitable
SSOP, TSSOP, VSO
not recommended(5)
suitable
Notes
1. All surface mount (SMD) packages are moisture sensitive. Depending upon the moisture content, the maximum
temperature (with respect to time) and body size of the package, there is a risk that internal or external package
cracks may occur due to vaporization of the moisture in them (the so called popcorn effect). For details, refer to the
Drypack information in the “Data Handbook IC26; Integrated Circuit Packages; Section: Packing Methods”.
2. These packages are not suitable for wave soldering as a solder joint between the printed-circuit board and heatsink
(at bottom version) can not be achieved, and as solder may stick to the heatsink (on top version).
3. If wave soldering is considered, then the package must be placed at a 45° angle to the solder wave direction.
The package footprint must incorporate solder thieves downstream and at the side corners.
4. Wave soldering is only suitable for LQFP, TQFP and QFP packages with a pitch (e) equal to or larger than 0.8 mm;
it is definitely not suitable for packages with a pitch (e) equal to or smaller than 0.65 mm.
5. Wave soldering is only suitable for SSOP and TSSOP packages with a pitch (e) equal to or larger than 0.65 mm; it is
definitely not suitable for packages with a pitch (e) equal to or smaller than 0.5 mm.
22 DEFINITIONS
Data sheet status
Objective specification
This data sheet contains target or goal specifications for product development.
Preliminary specification
This data sheet contains preliminary data; supplementary data may be published later.
Product specification
This data sheet contains final product specifications.
Limiting values
Limiting values given are in accordance with the Absolute Maximum Rating System (IEC 134). Stress above one or
more of the limiting values may cause permanent damage to the device. These are stress ratings only and operation
of the device at these or at any other conditions above those given in the Characteristics sections of the specification
is not implied. Exposure to limiting values for extended periods may affect device reliability.
Application information
Where application information is given, it is advisory and does not form part of the specification.
23 LIFE SUPPORT APPLICATIONS
These products are not designed for use in life support appliances, devices, or systems where malfunction of these
products can reasonably be expected to result in personal injury. Philips customers using or selling these products for
use in such applications do so at their own risk and agree to fully indemnify Philips for any damages resulting from such
improper use or sale.
1999 May 03
60
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
NOTES
1999 May 03
61
PCF50732
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
NOTES
1999 May 03
62
PCF50732
Philips Semiconductors
Objective specification
Baseband and audio interface for GSM
NOTES
1999 May 03
63
PCF50732
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Internet: http://www.semiconductors.philips.com
© Philips Electronics N.V. 1999
SCA63
All rights are reserved. Reproduction in whole or in part is prohibited without the prior written consent of the copyright owner.
The information presented in this document does not form part of any quotation or contract, is believed to be accurate and reliable and may be changed
without notice. No liability will be accepted by the publisher for any consequence of its use. Publication thereof does not convey nor imply any license
under patent- or other industrial or intellectual property rights.
Printed in The Netherlands
465008/00/01/pp64
Date of release: 1999 May 03
Document order number:
9397 750 04998