Philips Semiconductors Product specification Electronic ballast controller circuit NE5565 DESCRIPTION PIN CONFIGURATION The Electronic Ballast controller chip has been designed in a bipolar process. It is housed in a 20-lead dual-in-line plastic package. The control chip contains the equivalent of two (2) switched mode power supply control circuits. The first SMPS controller is a DC-to-DC converter operating in the discontinuous current conduction mode. It is used as a PFC in the ballast system to provide a DC voltage step-up function, good AC power factor, low AC current harmonic distortion, and circuit protection against some types of AC voltage transients. The PFC uses pulse width modulation to control the power transfer with an external MOS power transistor. The second SMPS circuit is a half-bridge oscillator circuit. It converts the DC output voltage of the PFC into a high frequency AC voltage for operating lamps. Power transfer in this circuit is controlled by changing the switch frequency. The half-bridge controller circuit is capable of driving two external high voltage MOS power transistors and it has circuits to regulate the lamp current, limit the peak lamp voltage, and protect the power switches during fault conditions. This electronic ballast controller circuit has the capability of being used in a dimming application. N Package CT 1 20 DCOUT CP 2 19 DC DMAX 3 18 OV RT 4 17 PF RXCX 5 16 VREF VLAMP 6 15 IPRIM CRECT 7 14 OUTH LI2 8 13 VCC LI 9 12 OUTP CSI 10 11 GND SL00524 Figure 1. Pin Configuration • Selectable variable frequency modes • Programmable pre-hit and ignition • Lamp over-voltage protection • PFC over-voltage protection for preventing over-shooting due to FEATURES: • Complete PFC correction and dimming ballast control on one IC • Low line current distortion PFC load removal ORDERING INFORMATION DESCRIPTION TEMPERATURE RANGE ORDER CODE DWG # 0 to +85°C NE5565N SOT146-1 20-Pin Plastic Dual-In-Line Package (DIP) BLOCK DIAGRAM VLAMP RXCX 6 RT 5 4 VCC CRECT LI2 7 8 LI 9 CSI 10 GND 11 OUTP 12 VCC 13 3 DMAX 2 CP 1 CT 20 DCOUT 14 OUTH 15 IPRIM 16 VREF 17 18 PF OV 19 DC SL00525 Figure 2. Block Diagram 1996 May 21 1 853-1835 16843 Philips Semiconductors Product specification Electronic ballast controller circuit NE5565 AC LINE FLUORESCENT LAMPS HALF-BRIDGE SQUARE WAVE OSCILLATOR POWER FACTOR CORRECTION CIRCUIT AC FILTER DC SUPPLY 13 17 VCC PF RXCX 5 12 10 11 OUTP CSI GND VREF RT 16 4 DMAX 19 18 DC CP 3 14 OUTH OV DCOUT CT 2 1 20 6 VLAMP CRECT 15 IPRIM LI 7 LI2 9 8 R5 RT RX R4 R1 R2 CX C1 CT CP C2 C3 R3 DIMMING INPUT SL00526 Figure 3. Typical Application: 2-Lamps Dimming Ballast above the upper trip point, both PFC and half-bridge oscillator circuits become operational. When the VCC falls below the lower trip point of 10V, both PFC and half-bridge circuits are disabled. Once the half-bridge oscillator turns off, it is not allowed to turn back on until VCC exceeds the upper trip point and a minimum time delay, set by external components at the DMAX pin, has passed. Voltage Regulator The VREF output provides a regulated output voltage of 7.42V at the VREF pin. This voltage is used as a reference as well as the power supply of the control logic. It is based on a trimmed band gap voltage reference circuit. The nominal VCC voltage for the control chip is 12.7V. The VREF circuit requires a minimum of 9.3V before it can produce regulated output. The VREF output voltage has an absolute accuracy of ±3.5% over the temperature range of 0°C to 85°C. Start up Ckt The Low Half-bridge Voltage Lock-out Circuit senses the DC output voltage of the PFC SMPS clrcuit. It is used to inhibit the lamp ignition sequence or frequency sweep of the half-bridge oscillator until the PFC output voltage has reached a pre-determined value. This value is set by external components. The PFC voltage is sensed by the over voltage input pin, OV. When this input exceeds 5/7 of VREF the frequency sweep is allowed to occur, thus beginning the lamp ignition sequence. Lamp Voltage Regulator Limits the maximum open circuit voltage across the lamp load during the pre-heat, ignition and lamp removal conditions. During steady state operation, the lamp voltage is governed by the arc voltage of the lamps, not by the control circuit. The lamp voltage comparator is used to sense when the voltage at the VLAMP pin exceeds VREF. At the time this occurs, the lamp voltage has reached its maximum allowed open circuit value and the circuit responds by producing a rapid frequency increase which reduces the voltage at the Vlamp pin. The RxCx time constant sets the frequency sweep time of the start up circuit. The frequency sweep range has a rate of 2:1. The Over Voltage Protection Circuit prevents the PFC DC output voltage from exceeding a pre-determined value. When the voltage at the OV pin is greater than VREF the PFC buffer gate drive output OUTP is turned off. This prevents any further increase in PFC DC output voltage. The over voltage circuit only protects against an over voltage or over shoot generated by the PFC itself. This may occur during turn on when the SMPS is not loaded and the circuit is under damped. Transient voltages from the AC line are not suppressed by this circuit. Low Supply Lock-out Protection Senses the DC power supply voltage at the VCC pin to determine when the PFC and half-bridge control circuits should turn on or off. This protection circuit uses a Schmitt trigger with a voltage reference to determine the upper and lower trip points of the power supply voltage. As the power supply voltage rises from 0V to a value just below the upper trip point of 11V, both the PFC and the half-bridge control circuits are held in the off state. Once the VCC voltage rises 1996 May 21 Capacitive Load Protection Prevents failure of the half-bridge power transistors during lamp removal. It does this by limiting the operation of the half-bridge oscillator to frequencies above the resonant frequency of an 2 Philips Semiconductors Product specification Electronic ballast controller circuit NE5565 external LC network driven by the bridge. At frequencies above resonance the primary voltage of the half-bridge LC load network leads the primary current in phase. The protection logic senses the LC network current phase relative to the half-bridge gate drive voltage to determine if a resonant condition exists. The Iprim input voltage represents the primary current signal from the external LC network. If the voltage at Iprim is more positive than -100mV when the gate drive signal is high, then a fault condition exists and the half-bridge oscillator frequency is swept high. triggers the over current protection circuit this turns off the OUTP output and forces the external capacitor connected to DMAX to discharge when an over current condition occurs in the PFC input circuit. An over current condition is usually produced during the turn on transient of the SMPS or when the AC line voltage has a power interruption. Power Factor Amplifier Senses the phase and amplitude of a peak rectified AC line voltage in order to modulate the duty cycle of the PFC power switch. This is done to improve the sinusoidal wave shape of the AC line current. The power factor input is provided by the PF input pin. The voltage at this pin is 1V when the AC line voltage reaches its peak and 0V when the AC voltage is at its 0V crossing. Half-Bridge Oscillator Is a triangle wave generator used to produce a square wave signal for driving the half-bridge buffer circuit. The triangle wave appears on the Ct capacitor output pin. The oscillator frequency is governed by the value of the resistor connected to the Rt input and the value of the Ct capacitor. DC Error Amplifier Provides negative feedback control of the PFC DC output voltage. The DC pin senses the DC output voltage of the PFC through an external resistor voltage divider and filter network. The reference voltage for the DC error amplifier is VREF. The output of the amplifier is available at the DC out pin and an external capacitor is connected to this pin in order to remove switching frequency noise before its signal is applied to the pulse width modulator in the PWM oscillator circuit. Output Buffer Drive Convert the low level logic signals from the half-bridge oscillator and pulse width modulator into a 10V drive signal for the power switches. The OUTH half-bridge buffer/drive circuit will drive an external level shift scheme which will then be used to operate the half-bridge power switches. The OUTP output may directly drive a power MOSFET switch or an external level shift/power MOSFET combination. Lamp Current Rectifier Pulse Width Modulator Is used to provide negative feedback control of the average lamp current. An external lamp current transformer and load resistor are used to convert the lamp current signal into a voltage. This voltage is applied to the lamp current input pins, Li1 and Li2. The full wave rectified output is provided at CRECT pin. External resistors and a capacitor determine the gain and time constant of the circuit. A differential error amplifier compares the voltage of CRECT to an internal reference of 2/7 VREF and adjusts the half-bridge oscillator frequency so that the error voltage is minimized. This forces the average lamp current to be a constant. Generates a ramp voltage used to control the duty cycle of the PFC SMPS. The frequency of the pulse width modulator is set by the half-bridge oscillator. The ramp voltage appears at the CP output. It is synchronized to the half-bridge oscillator so that the beginning of the ramp occurs at the valley of the Ct triangle waveform. When the ramp voltage at CP exceeds the voltage at the DC out pin in the DC amplifier, the capacitor connected to CP is discharged. The period of the PFC gate drive pulse correspond to the CP ramp time. The maximum duty cycle, soft start function, and half-bridge off time are all controlled by the external capacitor and resistors connected to the DMAX pin. Dimming Dimming input should be an extra current put into charging C3 in addition to the current from Pin 7. This creates the same condition as higher voltage differential across Pins 8 and 9, hence, the IC reacts as if there is too much power applied to the lamps. Over Current Protection An over current is sensed by an external resistor connected to the current sense input pin, CSl. A voltage of minus 500mV at CSl 1996 May 21 3 Philips Semiconductors Product specification Electronic ballast controller circuit NE5565 PIN DESCRIPTIONS/ABSOLUTE MAXIMUM RATINGS Pin # 1 2 3 4 5 6 7 8 9 10 11 12 13 14 15 16 17 18 19 20 Name Ct CP DMAX Rt RxCx VLAMP CRECT Li2 Li1 CSl GND OUTP VCC OUTH IPRIM VREF PF OV DC DCOUT Function Half-Bridge oscillator capacitor PWM Capacitor for power factor correction circuit Max Duty Cycle, soft start, and time delay R/C input Resistor for setting the half-bridge frequency Start resistor and capacitor input for setting frequency sweep time Lamp voltage regulator input Lamp current rectifier capacitor input/dimming control input Lamp current differential inputs Current sense input for over-current protection Ground Gate drive output for the PFC Positive power supply voltage Gate drive output for the half-bridge DMOS Primary current sense input Regulated output voltage and reference Power factor input 0ver-voltage comparator input DC error amplifier input DC error amplifier output for connecting to external filter capacitor Rating 7 7 7 ±0.7V or 500µA 7 14 7 Units V V V V/µA V V V ±1V to Li1, 7V or VREF -0.7V to GND V +0.5 V / -2V 0 14 14 14 +1V / -1.5 V or ±500µA VCC 7 14 12 7 V V V V V V/µA V V V V V DC ELECTRICAL CHARACTERISTICS VCC = +12.7V, TA = 25°C; unless otherwise stated. SYMBOL PARAMETER TEST CONDITIONS LIMITS UNITS MIN TYP MAX -403 -690 -941 µA -1 µA 7.79 V 6.6 V DC Error Amplifier DC input clamp current DC = 0V DC bias current DC = VREF DC error amp reference 7.05 DC output HIGH voltage DC = 7V 7.42 5.4 Power Factor Amplifier PF input current -14 µA 65 100 135 µA/V -8 µA 1.51 1.59 1.67 V -8 µA PF = 1V PF transconductance Start-up Circuit RxCx input current RxCx = 0.5V RxCx threshold OV input current OV = 5V OV threshold 7.05 7.42 7.79 V HB lockout threshold 4.93 5.3 5.67 V -160 -200 -240 µA Oscillator Rt voltage .7 Ct HIGH current RxCx=0V Rt=100µA Ct LOW current RxCx=6.5V Rt=100µA V -80 -100 -120 µA Ct HIGH threshold 4.14 4.6 5.06 V Ct LOW threshold 2.23 2.48 2.73 V PWM CP HIGH threshold CP-to-DMAX threshold CP-to-DC output threshold 1996 May 21 4 3.66 4.07 4.48 V DMAX = 4V 2.97 3.3 3.63 V DC = 4V 2.97 3.3 3.63 V Philips Semiconductors Product specification Electronic ballast controller circuit NE5565 DC ELECTRICAL CHARACTERISTICS (continued) SYMBOL PARAMETER TEST CONDITIONS LIMITS MIN TYP MAX UNITS PWM (cont.) DMAX input current -1 µA 1.17 V 9 18 mA 9.3 14 V ±3.5 % -5 mA DMAX = 0.5V DMAX threshold 0.95 1.06 Power Supply ISUPPLY static VCC Supply voltage VREF Reference voltage VCC = 12.7V TRIMMED VALUE VREF tolerance 7.42 0 to 85°C VREF load current IREF short circuit current VREF = 0V V -30 mA Buffer IPC = 40mA OUTP / OUTH LOW OUTP / OUTH HIGH 3 IPC = -40mA 10.2 IPC = -250mA PULSE 8.1 V Magnetizing ±40 mA Gate capacitance current ±250 mA OUTP / OUTH peak triangle wave current OUTP / OUTH pulse current 1 IPC = 250mA PULSE Low supply upper trip point 10.45 11.0 11.55 V Low supply lower trip point 9.5 10.0 10.5 V -8 µA 7.05 7.42 7.79 V -60 -100 -140 µA -60 -100 -140 mV -60 -100 -140 µA -400 -500 -650 mV -120 -200 -280 µA 150 mV V Lamp Voltage Regulator VLAMP input current VLAMP = 6.5V VLAMP threshold Load Protection IPRIM input current IPRIM = 0V IPRlM negative threshold Over-current Protection CSI input current CSI = -1V CSI threshold Rectifier (RLi = RLi2 = 4k, R3 = 20k; VRLi = Voltage input to RLi1; VRLi2 = 0V, Input to RLi2) Li input current VRLi1 = VRLi2 = 0V CRECT output offset VRLi1 = VRLi2 = 0V CRECT HIGH output VRLi1 = ±0.5V 4.42 4.66 4.9 CRECT gain VRECT/VRLi1 8.86 9.33 9.80 2.01 2.12 2.23 CRECT error amp reference 1996 May 21 5 V Philips Semiconductors Product specification Electronic ballast controller circuit NE5565 DIP20: plastic dual in-line package; 20 leads (300 mil) 1996 May 21 6 SOT146-1