Features • • • • • • • • • • Low-voltage Operation 3V to 6.5V Attenuator Gain Range Between Transmit and Receive: 52 dB Four-point Signal Sensing for Improved Sensitivity Monitoring System for Background Noise Level Adjustable Microphone Amplifier Gain Mute Function Chip Disable for Active/Standby Operation On-board Filter Dial Tone Detector Compatible with U4083B Speaker Amplifier Low-voltage Voice-switched IC for Hands-free Operation Benefits • Fast Channel Switching Allows Quasi-duplex Operation • Proper Operation in Noisy Surroundings 1. Description The low-voltage voice-switched speakerphone circuit, U4082B, incorporates a wide range of functions. The versatility of the device is further enhanced by giving access to internal circuit points. The block diagram (see Figure 1-1) shows amplifiers, level detectors, transmit and receive attenuators operating in complementary functions, background noise monitors, chip disable, dial tone detector and mute function. Due to low-voltage operation, the device can be operated either by a low supply or via a telephone line requiring 5.5 mA typically. Stand-alone operation is enabled by a coupling transformer (Tip and Ring) or in conjunction with a handset speech network, as shown in Figure 1-2 on page 2. Figure 1-1. Block Diagram 11 MIC MICO 10 17 TLI2 + 12 MUTE 9 8 TO TI 7 HTI VS HTO- - T Attenuator VB 6 - + 5 HTO+ + VB VB 27 CPR AGC 16 CPT U4082B Background Noise Monitor Background Noise Monitor 23 TLI1 Level Detectors 18 TLO2 19 RLO2 25 RLO1 24 TLO1 Dial Tone Detector + - 4 VS U4082B 28 GND 3 CD Level Detectors Attenuator Control VB Filter 400Ω R Attenuator 15 VB 14 CT 20 RLI2 RECO 22 +1 21 RI 13 VCI 26 RLI1 1 PD 2 FI Rev. 4743D–CORD–03/06 2 VS 1N4733 5.1V 6 1 kΩ 0.02 µF 7 18 C PT 16 3 CD 3 GND 28 VS 4 RL O 2 19 TL O 2 U4083B 1 1000 µF 12 VB VB 4 270 pF 10 + - + - 14 120 kΩ 15 400 Ω 5 8 200 pF 110 kΩ 5.1 kΩ 0.05 µF 10 kΩ + - 6 VB 9.1 kΩ Volume Control 20 kΩ VB 0.1 µF 10 kΩ 56 kΩ +1 Filter FO 1 0.05 µF RLI1 2 6 + - FI 2 TLO 1 24 RLO 1 25 TLI1 23 C PR 27 H TO + 5 Balancing Network U4082B Level Detector Background Noise Monitor H TO - 51 kΩ V CI 13 VB H TI 7 0.1 µF RI 2 1 0.1 µF REC O 2 2 R Attenuator VB + Dial Tone Detector Attenuator Control AGC VS - TO 8 10 kΩ T Attenuator TI 9 0.1 µF RLI2 20 Level Detector 5 µF CT 5.1 kΩ 1 7 T L I2 0.1 µF Background Noise Monitor + MICO 180 kΩ M IC 1 1 220 µF 5.1 kΩ MUTE VB 2 µF 2 µF 47 µF 100 kΩ 20 µF 620 Ω 0.2 µF 100 kΩ 220 kΩ 4700 pF 2 µF 2 µF VB 0.05 µF 47 µF 5.1 kΩ 0.1 µF 300 Ω 820 Ω 4700 pF 0.01 µF VS Hook Switch Ring Tip Figure 1-2. Block Diagram with External Circuit U4082B 4743D–CORD–03/06 U4082B 2. Pin Configuration Figure 2-1. Table 2-1. Pinning SO28 FO 1 28 GND FI 2 27 CPR CD 3 26 RLI1 VS 4 25 RLO1 HTO+ 5 24 TLO1 HTO- 6 23 TLI1 HTI 7 22 RECO TO 8 21 RI TI 9 20 RLI2 MICO 10 19 RLO2 MIC 11 18 TLO2 MUTE 12 17 TLI2 VCI 13 16 CPT CT 14 15 VB Pin Description Pin Symbol 1 FO Filter output. Output impedance is less than 50Ω Function 2 FI Filter input. Input impedance is greater than 1 MΩ 3 CD Chip disable. A logic low (< 0.8V) sets normal operation. A logic high (> 2V) disables the IC to conserve power. Input impedance is nominally 90 kΩ 4 VS Supply voltage 2.8V to 6.5V, approximately 5 mA. AGC circuit reduces the receive attenuator gain at 25 dB, receive mode at 2.8V 5 HTO+ Output of the second hybrid amplifier (Hybrid output). Gain is internally set at –1 to provide a differential output, (in conjunction with HTO–) to the hybrid transformer 6 HTO– Output of the first hybrid amplifier. Hybrid output. Gain is set by external resistors 7 HTI Input and summing node for the first hybrid amplifier. DC level is approximately VB 8 TO Transmit attenuator output. DC level is approximately VB Transmit attenuator input. Maximum signal level is 350 mVrms. Input impedance is approximately 10 kΩ 9 TI 10 MICO Microphone amplifier output. Gain is set by external resistors 11 MIC Microphone amplifier input. Bias voltage is approximately VB 12 MUTE 13 VCI Volume control input. When VCI = VB, the receive attenuator is at maximum gain when in receive mode. When VCI = 0.3 VB, the receive gain is down 35 dB. It does not affect the transmit mode 14 CT Response time. An RC at this pin sets the response time for the circuit to switch modes Mute input. A logic low (< 0.8V) sets normal operation. A logic high (> 2V) mutes the microphone amplifier without affecting the rest of the circuit. Input impedance is nominally 90 kΩ 3 4743D–CORD–03/06 Table 2-1. Pin Description (Continued) Pin Symbol Function 15 VB 16 CPT An RC at this pin sets the time constant for the transmit background monitor 17 TLI2 Transmit level detector input on the microphone/speaker side 18 TLO2 Transmit level detector output on the microphone/speaker side, and input to the transmit background monitor 19 RLO2 Receive level detector output on the microphone/speaker side 20 RLI2 Receive level detector input on the microphone/speaker side 21 RI 22 RECO 23 TLI1 Transmit level detector input on the line side 24 TLO1 Transmit level detector output on the line side 25 RLO1 Receive level detector output on the line side and input to the receive background monitor 26 RLI1 Receive level detector input on the line side 27 CPR An RC at this pin sets the time constant for the receive background monitor 28 GND Ground Output voltage ≈ VS/2. It is a system AC ground and biases the volume control. A filter cap is required Input receive attenuator and dial tone detector. Maximum input level is 350 mVrms. Input impedance is approximately 10 kΩ Receive attenuator output. DC level is approximately VB 3. Introduction 3.1 General The fundamental difference between the operation of a speakerphone and a handset is that of half duplex versus full duplex. The handset is full duplex since conversation can occur in both directions (transmit and receive) simultaneously. A speakerphone has higher gain levels in both paths, and attempting to converse in full-duplex mode results in oscillatory problems due to the loop that exists within the system. The loop is formed by the receive and transmit paths, the hybrid and the acoustic coupling (speaker to microphone). The only practical and economical solution used to date is to design the speakerphone to operate in half-duplex mode. That is, only one person speaks at a time, while the other listens. To achieve this, a circuit is required which can detect who is talking, switch on the appropriate path (transmit or receive), and switch off (attenuate) the other path. In this way, the loop gain is maintained less than unity. When the talkers exchange functions, the circuit must quickly detect this, and switch the circuit appropriately. By providing speech-level detectors, the circuit operates in a “hands-free” mode, eliminating the need for a “push-to-talk” switch. The handset has the same loop as the speakerphone. Oscillations do not occur because the gains are considerably lower and the coupling from the earpiece to the mouthpiece is almost nonexistent (the receiver is normally held against a person's ear). The U4082B provides the necessary level detectors, attenuators, and switching control for a properly operating speakerphone. The detection sensitivity and timing are externally controllable. Additionally, the U4082B provides background noise monitors (which make the circuit insensitive to room and line noise), hybrid amplifiers for interfacing to Tip and Ring, the microphone amplifier, and other associated functions. 4 U4082B 4743D–CORD–03/06 U4082B 3.2 Transmit and Receive Attenuators TI, TO and RI, RECO The attenuators are functionally complementary; that is, when one is at maximum gain (+6.0 dB), the other is at maximum attenuation (–46 dB), and vice versa. Neither is ever fully on or off. The sum of their gains remains constant (within a nominal error band of ±0.1 dB) at a typical value of –40 dB (see Figure 7-1 on page 17). Their purpose is to control the transmit and receive paths to provide the half-duplex operation required in a speakerphone. The non-inverting attenuators have a –3.0 dB (from maximum gain) frequency of approximately 100 kHz. The input impedance of each attenuator (TI and RI) is nominally 10 kΩ (see Figure 3-1). To prevent distortion, the input signal should be limited to 350 mVrms. The maximum recommended input signal is independent of the volume control setting. The diode clamp on the inputs limits the input swing, and thus the maximum negative output swing. This results in a specific VRECO and VTOL definition as given in the table “Electrical Characteristics” on page 14. The output impedance is less than 10Ω until the output current limit (typically 2.5 mA) is reached. Figure 3-1. Attenuator Input Stage VB 11 kΩ to Attenuator Input RI 21 TI 9 5 kΩ 95 kΩ The attenuators are controlled by the single output of the control block, which is measurable at pin CT (pin 14). When pin CT is at +240 mV with respect to VB, the circuit is in receive mode (receive attenuator is at +6.0 dB). When pin CT is at –240 mV with respect to VB, the circuit is in transmit mode (transmit attenuator is at +6.0 dB). The circuit is in an idle mode when the C T voltage is equal to VB causing the attenuators' gain to be halfway between their fully on and fully off positions (–20 dB each). Monitoring the CT voltage (with respect to VB) is the most direct method of monitoring the circuit's mode. The attenuator control has seven inputs: two from the comparators operated by the level detectors, two from the background noise monitors, volume control, dial-tone detector, and AGC. They are described in the sections that follow. 3.3 Level Detectors There are four level detectors, two on the receive side and two on the transmit side. As shown in Figure 3-2 on page 6, the terms in parentheses form one system, and the other terms form the second system. Each level detector is a high-gain amplifier with back-to-back diodes in the feedback path, resulting in nonlinear gain which permits operation over a wide dynamic range of speech levels. Refer to the graphs of Figures 7-2, 7-3 and 7-4 on page 18 for their DC and AC transfer characteristics. The sensitivity of each level detector is determined by the external resistor and capacitor at each input (TLI1, TLI2, RLI1, and RLI2). Each output charges an external capacitor through a diode and limiting resistor, thus providing a DC representation of the input AC signal level. The outputs have a quick rise time (determined by the capacitor and an internal 350Ω resistor) and a slow decay time set by an internal current source and the capacitor. The capacitors on the four outputs should have the same value (±10%) to prevent timing problems. As can be seen in Figure 1-2 on page 2, on the receive side, one level detector (RLI1) is located at the receive input, receiving the same signal as at Tip and Ring, and the other (RLI2) is at the 5 4743D–CORD–03/06 output of the speaker amplifier. On the transmit side, one level detector (TLI2) is at the output of the microphone amplifier, while the other (TLI1) is at the hybrid output. The outputs RLO1 and TLO1 feed a comparator, whose output is fed to the attenuator control block. Likewise, outputs RLO2 and TLO2 feed a second comparator which also goes to the attenuator control block. The truth table for the effects of the level detectors is given in the section “Attenuator Control Block” on page 8. 3.4 Background Noise Monitors This circuit distinguishes speech (which consists of bursts) from background noise (a relatively constant signal level). There are two background noise monitors, one for the receive path and the other for the transmit path. The receive background noise monitor is operated by the RLI1-RLO1 level detector, while the transmit background noise monitor is operated by the TLI2-TLO2 level detector (Figure 3-2). They monitor the background noise by storing a DC voltage representative of the respective noise levels in capacitors at CPR and CPT. The voltages at these pins have slow rise times (determined by the external RC), but fast decay times. If the signal at RLI1 (or TLI2) changes slowly, the voltage at CPR (or CPT) will remain more positive than the voltage at the non-inverting input of the monitor's output comparator. When speech is present, the voltage on the non-inverting input of the comparator will rise more quickly than the voltage at the inverting input (due to the burst characteristic of speech), causing its output to change. This output is sensed by the attenuator control block. Figure 3-2. Level Detectors Level detector (TLI2) RLI1 Background noise monitor 4 µA (17) 26 + 5.1 kΩ VB + - 350Ω (TLO2) RLO1 0.1 µF + (18)25 2 µF Signal input + (CPT) CPR VS (16) 100 kΩ 27 47 µF 56 kΩ 33 kΩ 36 mV 15 VB VB + (RLI2) TLI1 (20) 23 Level detector 4 µA 0.1 µF C4 (C3) C2 (C1) 350Ω 24 TLO1 (RLO2) (19) 2 µF 5.1 kΩ + Comparator To attenuator control block Signal input The 36 mV offset at the comparator's input keeps the comparator from changing state unless the speech level exceeds the background noise by approximately 4.0 dB. The time constant of the external RC (approximately 4.7s) determines the response time to background noise variations. 6 U4082B 4743D–CORD–03/06 U4082B 3.5 Volume Control The volume control input at VCI (pin 13) is sensed as a voltage with respect to VB. It affects the attenuators in receive mode only and has no effect during idle or transmit mode. In receive mode, the attenuator receive gain, GR, is +6.0 dB, and attenuator transmit gain GT is –46 dB under the condition that VCI = V B . When VCI < V B , the attenuator receive gain is reduced (Figure 7-5 on page 19), whereas the attenuator transmit gain is increased; their sum, however, remains constant. Voltage deviation at VCI changes the voltage at CT, which in turn controls the attenuators (see section “Attenuator Control Block” on page 8). The volume control setting does not affect the maximum attenuator input signal at which noticeable distortion occurs. The bias current at VCI is typically –60 nA. It does not vary significantly with the VCI voltage or supply voltage VS. 3.6 Dial Tone Detector The dial tone detector is a comparator with one side connected to the receive input (RI) and the other to VB with a 15 mV offset (see Figure 3-3). If the circuit is in idle mode, and the incoming signal is greater than 15 mV (10 mVrms), the comparator's output will change, disabling the receive idle mode. The receive attenuator will then be at a setting determined mainly by the volume control. This circuit prevents the dial tone (which would be considered as continuous noise) from fading away as the circuit would have the tendency to switch to idle mode. By disabling the receive idle mode, the dial tone remains at the normally-expected full level. Figure 3-3. Dial Tone Detector To R attenuator RI - 21 + C4 To attenuator control 15 mV VB 3.7 AGC The AGC circuit affects the circuit only in receive mode, and only when the supply voltage is less than 3.5V. As VS < 3.5V, the gain of the receive attenuator is reduced as seen in Figure 7-6 on page 19. The transmit path attenuation changes such that the sum of the transmit and receive gains remains constant. The purpose of this feature is to reduce the power (and current) used by the speaker when a line-powered speakerphone is connected to a long line where the available power is limited. By reducing the speaker power, the voltage sag at VS is controlled, preventing possible erratic operation. 7 4743D–CORD–03/06 3.8 Attenuator Control Block The attenuator control block has seven inputs: • The output of the comparator operated by RLO2 and TLO2 (microphone/speaker side) – designated C1 • The output of the comparator operated by RLO1 and TLO1 (Tip/Ring side) – designated C2 • The output of the transmit background noise monitor – designated C3 • The output of the receive background noise monitor – designated C4 • The volume control • The dial tone detector • The AGC circuit The single output of the control block controls the two attenuators. The effect of C1 to C4 is as follows: Table 3-1. Mode Selection Table Inputs Note: 3.9 C1 C2 C3 C4 Output Mode T T 1 X Transmit T R Y Y Fast Idle R T Y Y Fast Idle R R X 1 Receive T T 0 X Slow Idle T R 0 0 Slow Idle R T 0 0 Slow Idle R R X 0 Slow Idle X = Do not care; Y = C3 and C4 are not both 0. Term Definitions • “Transmit” means the transmit attenuator is fully on (+6.0 dB), and the receive attenuator is at maximum attenuation (–46 dB). • “Receive” means both attenuators are controlled by the volume control. At maximum volume, the receive attenuator is fully on (+6.0 dB), and the transmit attenuator is at maximum attenuation (–46 dB). • “Fast Idle” means both transmit and receive speech are present in approximately equal levels. The attenuators are quickly switched (30 ms) to idle mode until one speech level dominates the other. • “Slow Idle” means speech has ceased in both transmit and receive paths. The attenuators are then slowly switched (1s) to idle mode. • Switching to full transmit or receive mode from any other mode is at the fast rate (≈ 30 ms). 8 U4082B 4743D–CORD–03/06 U4082B 3.10 Summary of the Truth Table • The circuit will switch to transmit if - both transmit level detectors sense higher signal levels relative to the respective receive level detectors (TLI1 versus RLI1, TLI2 versus RLI2), and - the transmit background noise monitor indicates the presence of speech. • The circuit will switch to receive if - both receive level detectors sense higher signal levels relative to the respective transmit level detectors, and - the receive background noise monitor indicates the presence of speech. • The circuit will switch to fast idle mode if the level detectors disagree on the relative strengths of the signal levels, and at least one of the background noise monitors indicates speech. For example, referring to the block diagram (Figure 1-2 on page 2), if there is a sufficient signal at the microphone amp output (TLI2) to override the speaker signal (RLI2) and there is sufficient signal at the receive input (RLI1) to override the signal at the hybrid output (TLI1), and either or both background monitors indicate speech, then the circuit will be in fast idle mode. Two conditions that can cause fast idle mode: - when both talkers are attempting to gain control of the system by talking at the same time, and - when one talker is in a very noisy environment, forcing the other talker to continually override that noise level. In general, fast idle mode will occur infrequently. • The circuit will switch to slow idle mode when - both talkers are quiet (no speech present), or - when one talker's speech level is continuously overridden by noise at the other speaker's location. The time required to switch the circuit between transmit, receive, fast idle and slow idle is determined in part by the components at pin 14 (see the section on switching times for a more complete explanation of the switching time components). A diagram of the CT circuitry is shown in Figure 3-4, and operates as follows: Figure 3-4. CT Attenuator Control Block Circuit VB 15 RT 14 CT CT 2 kΩ I1 I2 60 µA + Attenuator control To attenuators 4 C1 to C4 Volume control Dial tone detector AGC 9 4743D–CORD–03/06 – RT is typically 120 kΩ, and CT is typically 5.0 µF. – To switch to receive mode, I1 is turned on (I2 is off), charging the external capacitor to +240 mV above VB. (An internal clamp prevents further charging of the capacitor.) – To switch to transmit mode, I2 is turned on (I1 is off), bringing down the voltage on the capacitor to –240 mV with respect to VB. – To switch to idle mode quickly (fast idle), the current sources are turned off, and the internal 2 kΩ resistor is switched on, discharging the capacitor to VB with a time constant of 2 kΩ × CT. – To switch to idle mode slowly (slow idle), the current sources are turned off, the switch at the 2 kΩ resistor is open, and the capacitor discharges to VB through the external resistor, RT, with a time constant of = RT × CT. 3.11 Microphone Amplifier The microphone amplifier (pins 10, 11) has the non-inverting input internally connected to VB, while the inverting input and the output are pinned out. Unlike most operational amplifiers, this amplifier has an all-NPN output stage which maximizes phase margin and gain bandwidth. This feature ensures stability at gains less than unity, as well as with a wide range of reactive loads. The open loop gain is typically 80 dB (f < 100 Hz), and the gain-bandwidth is typically 1.0 MHz (see Figure 7-7 on page 19). The maximum peak-to-peak output swing is typically (VS – 1V) with an output impedance of < 10Ω until current limiting is reached (typically 1.5 mA). Input bias current at MIC is typically –40 nA. Figure 3-5. Microphone Amplifier and Mute RMF RMI VS VB 11 MIC From microphone 12 MUTE + - 10 MICO VS 90 kΩ 75 kΩ 10 U4082B 4743D–CORD–03/06 U4082B 3.12 Hybrid Amplifiers The two hybrid amplifiers (at HTO+, HTO–, and HTI), in conjunction with an external transformer, provide the two-to-four-wire converter for interfacing to the telephone line. The gain of the first amplifier (HTI to HTO–) is set by external resistors (gain = –RHF / RHI in Figure 1-2 on page 2), and its output drives the second amplifier, the gain of which is internally set at –1.0. Unlike most operational amplifiers, these amplifiers have an all-NPN output stage, which maximizes phase margin and gain bandwidth. This feature ensures stability at gains less than unity, as well as with a wide range of reactive loads. The open-loop gain of the first amplifier is typically 80 dB, and the gain bandwidth of each amplifier is approximately 1.0 MHz (see Figure 7-6 on page 19). The maximum output swing (peak to peak) of each amplifier is typically 1.2V less than VS with an output impedance of < 10Ω until current limiting is reached (typically 8.0 mA). The output current capability is guaranteed to be a minimum of 5.0 mA. The bias current at HTI is typically –30 nA. The connections to the coupling transformer are shown in Figure 1-1 on page 1. Balancing the network is necessary to match the line impedance. 3.13 Filter The operation of the filter circuit is determined by the external components. The circuit within the U4082B from pins FI to FO is a buffer with a high input impedance (> 1 MΩ) and a low output impedance (< 50Ω). The configuration of the external components determines whether the circuit is a high-pass filter (as shown in Figure 1-2 on page 2), a low-pass filter, or a band-pass filter. As a high-pass filter, with the components shown in Figure 3-6 on page 12, the filter will keep out the 60Hz (and 120Hz) hum which can be picked up by the external telephone lines. As a low-pass filter (Figure 3-7 on page 12), it can be used to roll off the high-end frequencies in the receive circuit, which aids in protecting against acoustic feedback problems. With an appropriate choice of an input coupling capacitor to the low-pass filter, a band-pass filter is formed. 11 4743D–CORD–03/06 Figure 3-6. High-pass Filter VB VS 56 kΩ R1 300 kΩ 220 kΩ C1 R2 4700 pF FO FI C2 4700 pF 1 2 260 µA 305Hz 50 0 -3.0 fN = 1 2π 1 C2 R1R2 for C1 = C2 -30 Figure 3-7. fN Low-pass Filter VB 220 kΩ C1 R1 VI 13 kΩ 0.01 µF R2 FI 13 kΩ 2 0.001 µF +1 1 FO C2 4.0 20 kHz 0 -3.0 fN = 1 1 2π C 1C2R2 for R1 = R2 -30 12 fN U4082B 4743D–CORD–03/06 U4082B 3.14 Power Supply, VB, and Chip Disable The power supply voltage at pin 4 (VS) is between 3.5V and 6.5V for normal operation, but reduced operation is possible down to 2.8V (see Figure 7-6 on page 19 and section “AGC” on page 7). The power supply current is shown in Figure 7-9 on page 20 for both power-up and power-down mode. The output voltage at VB (pin 15) is approximately (VS – 0.7) / 2, and provides the AC ground for the system. The output impedance at VB is approximately 400Ω (see Figure 7-10 on page 20), and in conjunction with the external capacitor at VB, forms a low-pass filter for power supply rejection. Figure 7-11 on page 21 gives an indication of the amount of rejection with different capacitors. The capacitor value depends on whether the circuit is powered by the telephone line or a power supply. Since VB biases the microphone and hybrid amplifiers, the amount of supply rejection at their outputs is directly related to the rejection at VB, as well as their respective gains. Figure 8-1 on page 22 depicts this graphically. The chip disable (CD, pin 3) permits powering down the IC to conserve power and/or for muting purposes. With CD < 0.8V, normal operation is in effect. With 2.0V < CD < VS, the IC is in power-down mode. In power-down mode, the microphone and the hybrid amplifiers are disabled, and their outputs reach the high-impedance state. Additionally, the bias is removed from the level detectors. The bias is not removed from the filter (pins 1 and 2), the attenuators (pins 8, 9, 21 and 22), or from pins 13, 14, and 15 (the attenuators are disabled, however, and will not pass a signal). The input impedance at CD is typically 90 kΩ, has a threshold of approximately 1.5V, and the voltage at this pin must be kept within the range of ground and VS (see Figure 7-8 on page 20). If CD is not used, the pin should be grounded. 4. Absolute Maximum Ratings Stresses beyond those listed under “Absolute Maximum Ratings” may cause permanent damage to the device. This is a stress rating only and functional operation of the device at these or any other conditions beyond those indicated in the operational sections of this specification is not implied. Exposure to absolute maximum rating conditions for extended periods may affect device reliability. Reference point pin 28, Tamb = 25° C, unless otherwise specified. Parameters Supply voltage, pin 4 Symbol Value Unit VS –1.0 to +7.0 V –1.0 to (VS + 1.0) –1.0 to (VS + 0.5) –0.5 to (VS + 0.5) V –55 to +150 °C Voltages Pin 3, 12 Pin 13 Pin 2, 9, 21 Storage temperature range Tstg Tj 125 °C Ambient temperature range Tamb –20 to +60 °C Power dissipation Tamb = 60° C, SO28 Ptot 520 mW RthJA 120 K/W Junction temperature Maximum thermal resistance Junction ambient, SO28 13 4743D–CORD–03/06 5. Recommended Operating Conditions Parameters Test Conditions Supply voltage Pin 4 CD input MUTE input Pin 3 Pin 12 Output current Pin 15 Volume control input Pin 13 Attenuator input signal voltage Pins 9, 21 Symbol Min. Max. Unit VS 3.5 6.5 V 0 VS V IB - 500 µA VCI 0.3 × VB VB V 0 350 mVrms 0 40 dB 0 0 0 ±2.0 ±1.0 ±5.0 mA Tamb –20 +60 °C Symbol Min. Typ. Max. Unit 5.5 600.0 8.0 800.0 mA µA Microphone amplifier, hybrid amplifier gain Load current At RECO, TO; pins 8, 22 At MICO; pin 10 At HTO–, HTO+; pins 6, 5 Ambient temperature range Typ. 6. Electrical Characteristics Tamb = +25°C, VS = 5.0 V, CD ≤0.8 V, unless otherwise specified Parameters Test Conditions Power Supply Supply current VS = 6.5V, CD = 0.8V VS = 6.5V, CD = 2.0V CD input resistance VS = VCD = 6.5V RCD 50.0 CD input voltage High Low VCDH VCDL 2.0 0.0 Output voltage VS = 3.5V VS = 5.0V VB 1.8 Output resistance IVB = 1 mA ROVB 400.0 Ω Power supply rejection ratio CVB = 220 µF, f = 1 kHz PSRR 54.0 dB IS 90.0 kΩ VS 0.8 1.3 2.1 2.4 V V Attenuators Receive attenuator gain f = 1.0 kHz, VCI = VB R mode, RI = 150 mVrms (VS = 5.0V) (VS = 3.5V) Gain change AGC gain change Idle mode RI = 150 mVrms GR +4.0 VS = 3.5V versus VS = 5.0V ∆GR1 –0.5 –VS = 2.8V versus VS = 5.0V ∆GR2 Range R to T mode +6.0 +8.0 0.0 +0.5 –25.0 –15.0 GRI –22.0 –20.0 –17.0 ∆GR3 49.0 52.0 54.0 VCR 27.0 dB dB Volume control range R Mode, 0.3 VB < VCI < VB 35.0 dB RECO DC voltage R mode VRECO VB V RECO DC voltage R to T mode ∆VRECO ±10 RECO high voltage IO = –1 mA, RI = VB + 1.5V VRECOH RECO low voltage IO = 1 mA, RI = VB – 1V, output measured with respect to VB VRECOL RI input resistance RI < 350 mVrms 14 RRI ±150.0 3.7 7.0 mV V –1.5 –1.0 V 10.0 14.0 kΩ U4082B 4743D–CORD–03/06 U4082B 6. Electrical Characteristics (Continued) Tamb = +25°C, VS = 5.0 V, CD ≤0.8 V, unless otherwise specified Parameters Test Conditions Symbol Min. Typ. Max. Transmit attenuator gain f = 1 kHz T mode, TI = 150 mVrms Idle mode, TI = 150 mVrms Range T to R mode GT GTI GTI +4.0 –22.0 49.0 +6.0 –20.0 52.0 +8.0 –17.0 54.0 TO DC voltage T Mode VTO VB TO DC voltage T to R Mode VTO ±100 TO high voltage IO = –1.0 mA, TI = VB + 1.5V VTOH TO low voltage IO = + 1.0 mA TI = VB – 1.0V output measured with respect to VB VTOL TI input resistance TI < 350 mVrms RTI Gain tracking GR + GT, at T, Idle, R GTR CT voltage Pin 14 – VB R mode, VCI = VB Idle mode T mode VCT CT source current R mode ICTR –85.0 –60.0 –40.0 µA CT sink current T mode ICTT +40.0 +60.0 +85.0 µA dB V ±150.0 3.7 7.0 Unit mV V –1.5 –1.0 10.0 14.0 ±0.1 V kΩ dB Attenuator Control +240.0 0.0 –240.0 mV CT slow idle current ICTS 0.0 CT fast idle internal resistance RFI VCI input current IVCI Dial tone detector threshold VDT 10.0 15.0 20.0 mV MICO VOS –50.0 0.0 +50.0 mV GVOLM 70.0 80.0 dB 1.0 MHz 1.5 2.0 µA 3.6 –60.0 kΩ nA Microphone Amplifier VMUTE < 0.8V, GVCL = 31 dB Output offset VMICO – VB Feedback R = 180 kΩ Open loop gain f < 100Hz Gain bandwidth GBWM Output high voltage IO= –1.0 mA, VS = 5.0V VMICOH Output low voltage IO = +1.0 mA VMICOL Input bias current (MIC) Muting (∆ gain) MUTE input resistance VS = VMUTE = 6.5V MUTE input high MUTE input low V 200.0 IBM f = 1 kHz, VMUTE = 2.0V 300Hz < f < 10 kHz Distortion 3.7 G G –55.0 RMUTE 50.0 VMUTEH 2.0 VMUTEL 0.0 –40.0 nA –68.0 dB dB 90.0 kΩ VS 0.8 0.15 300Hz < f < 10 kHz THDM HTO– Offset VHTO – VB, Feedback R = 51 kΩ HVOS –20.0 HTO to HTO+ Offset Feedback R = 51 kΩ HBVOS Open loop gain HTI to HTO–, f < 100Hz GVOLH mV V V % Hybrid Amplifiers Gain bandwidth GB 0.0 +20.0 mV –30.0 0.0 +30.0 mV 60.0 80.0 dB 1.0 MHz 15 4743D–CORD–03/06 6. Electrical Characteristics (Continued) Tamb = +25°C, VS = 5.0 V, CD ≤0.8 V, unless otherwise specified Parameters Test Conditions Closed loop gain HTO– to HTO+ Input bias current at HTI Symbol Min. Typ. Max. Unit GVCLH –0.35 0.0 +0.35 dB –30.0 IBH HTO high voltage IO = –5.0 mA VHT H HTO low voltage IO = +5.0 mA VHT L HTO+ high voltage IO = –5.0 mA VHT H HTO+ low voltage IO = +5.0 mA VHT L Distortion 300 Hz < f < 10 kHz (see Figure 6-1) nA 3.7 V 250.0 3.7 mV V 450.0 d 0.3 mV % Level Detectors and Background Noise Monitors Transmit receive switching threshold Current ratio from T to R at RLI1 + RLI2 to 20 mA at TLI1 + TLI2 to switch ITH Source current RLO1, RLO2, TLO1, TLO2 ILSO –2.0 mA Sink current RLO1, RLO2, TLO1, TLO2 ILSK 4.0 µA CPR, CPT output resistance IO = 1.2 mA CPR, CPT leakage current 0.8 1.0 1.2 RCP 35 Ω ICPLK –0.2 µA Filter VFO – VB, 220 kΩ from VB to FI FOVOS –200.0 FO sink current IFO 150.0 FI bias current IFI –50.0 Voltage offset at FO –90 0.0 mV 260 400.0 µA nA System Distortion R Mode From FI to RECO, FO connected to RI dR 0.5 3.0 % T Mode From MIC to HTO–/HTO+, includes T attenuator dT 0.8 3.0 % Figure 6-1. Hybrid Amplifier Distortion Test 6 HTO- 51 kΩ 10 kΩ VI 7 0.1 µF - HTI R 1200Ω R Amplifier + VB - 5 + HTO+ Analyzer VB 16 U4082B 4743D–CORD–03/06 U4082B 7. Temperature Characteristics Parameters Typical Value at 25° C Typical Change –20° C to +60° C Supply current, CD = 0.8 VIS 5.0 mA –0.3%/° C Supply current, CD = 2.0 VIS 400.0 µA –0.4%/° C VB output voltage, VS = 5.0V VO 2.1V +0.8%/° C Attenuator gain (maximum gain) +6.0 dB 0.0008 dB/° C Attenuator gain (maximum attenuation) –46.0 dB 0.004 dB/° C Attenuator input resistance (at TI, RI) 10.0 kΩ +0.6%/° C Dial tone detector threshold 15.0 mV +20.0 mV/° C CT source, sink current ±60.0 µA –0.15%/° C 0.0 mV ±4.0 mV/° C Microphone, hybrid amplifier offset 1.0 ±0.02%/° C Sink current at RLO1, RLO2, TLO1, TLO2 Transmit receive switching threshold 4.0 µA –10.0 nA/° C Closed loop gain (HTO– to HTO+) 0.0 dB 0.001%/° C Figure 7-1. Attenuator Gain versus VCT (Pin 14) 10 0 -10 G (dB) T attenuator R attenuator -20 -30 -40 -50 -320 -160 0 160 VCT - VB (mV) 320 17 4743D–CORD–03/06 Figure 7-2. Level Detector DC Transfer Characteristics 500 ∆VO (mV) 400 300 200 100 0 -20 0 Figure 7-3. -40 -60 II (µA) -80 -100 Level Detector AC Transfer Characteristics 300 R = 5.1 kΩ C = 0.1 µF 250 ∆VO (mV) ↓ ← R = 10 kΩ 200 C = 0.047 µF or 0.1 µF 150 f = 1 kHz 100 50 0 0 20 4 60 80 100 Vi (mVrms) Figure 7-4. Level Detector AC Transfer Characteristics versus Frequency 20 ∆VO (mV at 1 kHz) 10 Vi= 10 mV 0 i -10 Vi= 40 mV -20 -30 -40 100 1000 10000 f (Hz) 18 U4082B 4743D–CORD–03/06 U4082B Figure 7-5. Receive Attenuator versus Volume Control 10 0 ∆G (dB) -10 Receive mode -20 -30 ← Minimum recommended level -40 0.1 0.3 0.5 0.7 0.9 1.2 VCI/VB Figure 7-6. Receive Attenuation Gain versus VS 10 ∆G (dB) 0 -10 -20 -30 -40 2.8 3 3.2 3.4 3.6 VS (V) 120 120 100 100 Microphone amp. phase 80 80 Hybrid amp. phase 60 60 Gain 40 40 20 20 0 0.1 Phase (degrees) Microphone and 1st-hybrid Amplifier Open-loop Gain and Phase versus Frequency GVOL (dB) Figure 7-7. 0 1 10 f (kHz) 100 1000 19 4743D–CORD–03/06 Figure 7-8. Input Characteristics at CD, MUTE 120 100 ← Valid for 0 ≤ CD, MUTE ≤ VS → II (µA) 80 60 40 20 0 2 0 4 6 6.5 8 Input Voltage (V) Figure 7-9. Supply Current versus Supply Voltage 10 8 CD ≤ 0.8V IS (mA) 6 4 2 2V ≤ CD ≤ VS 0 2 0 4 6 8 VS (V) Figure 7-10. VB Output Characteristics 3.0 2.5 VS = 6V VB (V) 2.0 1.5 VS = 3.5V 1.0 0.5 0 0 20 0.5 1.0 1.5 2.0 -IB (mA) (Load Current) 2.5 U4082B 4743D–CORD–03/06 U4082B Figure 7-11. VB Power Supply Rejection versus Frequency Characteristics and VB Capacitor 80 CVB = 1000 µF PSRR (dB) 500 µF 60 200 µF 100 µF 50 µF 40 20 0.3 1 2 3 f (kHz) 8. Design Guidelines 8.1 Switching Time The switching time of the U4082B circuit is determined primarily by CT (pin 14, refer to Figure 3-3 on page 7), and secondarily by the capacitors at the level detector outputs (RLO1, RLO2, TLO1, TLO2). For more information, please refer to Figure 1-2 on page 2. The time to switch from idle to receive or transmit mode is determined by the capacitor at CT, together with the internal current sources. The switching time is: ∆MinimalV × C 240Minimal × 5 ∆MinimalT = ------------------------------------------T- = ----------------------------------------- = 20.0 ms I 60 where ∆V = 240 mV CT = 5 µF I = 60 µA If the circuit switches directly from receive to transmit mode (or vice versa), the total switching time would be 40 ms. The switching time depends upon the mode selection. If the circuit is going to “fast idle”, the time constant is determined by the CT capacitor, and the internal 2 kΩ resistor. With CT = 5 µF, the time constant is approximately 10 ms, giving a switching time to idle of approximately 30 ms (for 95% change). Fast idle is an infrequent mode, however, occurring when both speakers are talking and competing for control of the circuit. The switching time from idle back to either transmit or receive mode is described above. By switching to “slow idle” the time constant is determined by the CT capacitor and RT, the external resistor (see Figure 3-4 on page 9). With CT = 5.0 µF and RT = 120 kΩ, the time constant is approximately 600 ms, giving a switching time of approximately 1.8 seconds (for 95% change). The switching period to slow idle begins when both speakers have stopped talking. The switching time back to the original mode will depend on how soon that speaker begins speaking again. The sooner the speaking starts during the 1.8s period, the quicker the switching time since a smaller voltage excursion is required. The switching time is determined by the internal current source as described above. 21 4743D–CORD–03/06 The above switching times occur, however, after the level detectors have detected the appropriate signal levels, since their outputs operate the attenuator control block. Referring to Figure 3-2 on page 6, the rise time of the level detectors' outputs to new speech is quick by comparison (approximately 1 ms), determined by the internal 350Ω resistor and the external capacitor (typically 2 µF). The output's decay time is determined by the external capacitor and an internal 4 µA current source, giving a decay rate of 60 ms for a 120 mV excursion at RLO or TLO. Total response time of the circuit is not constant since it depends on the relative strength of the signals at the different level detectors and the timing of the signals with respect to each other. The capacitors at the four outputs (RLO1, RLO2, TLO1, TLO2) must be of equal value (±10%) to prevent problems in timing and level response. The rise time of the level detector's outputs is not significant since it is so short. The decay time, however, provides a significant part of the “hold time” necessary to hold the circuit during the normal pauses in speech. The components at the inputs of the level detectors (RLI1, RLI2, TLI1, TLI2) do not affect the switching time but rather affect the relative signal levels required to switch the circuit and the frequency response of the detectors. 8.2 Design Equations The following definitions are used at 1 kHz with reference to Figure 1-2 on page 2 and Figure 8-3 on page 23 where coupling capacitors are omitted for the sake of simplicity: • GMA is the gain of the microphone amplifier measured from the microphone output to TI (typically 35V/V, or 31 dB) • GT is the gain of the transmit attenuator, measured from TI to TO • GHA is the gain of hybrid amplifiers, measured from TO to the HTO–/HTO+ differential output (typically 10.2V/V, or 20.1 dB) • GHT is the gain from HTO–/HTO+ to Tip/Ring for transmit signals, and includes the balance network (measured at 0.4V/V, or –8 dB) Figure 8-1. VB Power Supply Rejection of the Microphone and Hybrid Amplifiers 100 HTO-, CVB = 1000 µF 80 PSRR (dB) = 220 µF 60 MICO, CVB = 1000 µF 40 20 = 220 µF 0 0.3 22 1 f (kHz) 2 3 U4082B 4743D–CORD–03/06 U4082B Figure 8-2. Typical Output Swing versus VS 6 MICO VOPP (V) 5 HTO -, HTO + 4 3 TO, RO TO 2 FO RO 1 0 3 4 5 6 VS (V) Figure 8-3. Basic Clock Diagram for Design Purposes MIC amp. TI MICO T attenuator TO Hybrid amp. HTO-/HTO+ R2 R1 I1 TLI2 GHIT TLI1 + Acoustic coupling Comparator C1 Comparator Attenuator control + Tip GST C2 + - Hybrid Ring + RLI1 RLI2 I3 I2 R3 I4 R4 R attenuator RECO SAO RI GHR FI FO Speaker amp. Filter • GST is the side tone gain, measured from HTO–/HTO+ to the filter input (measured at 0.18 V/V, or –15 dB) • GHR is the gain from Tip/Ring to the filter input for receive signals (measured at 0.833V/V or –1.6 dB) • GFO is the gain of the filter stage, measured from the input of the filter to RI, typically 0 dB • GR is the gain of the receive attenuator measured from RI to RECO • GSA is the gain of the speaker amplifier, measured from RECO to the differential output of the U4083B (typically 22V/V or 26.8 dB) • GAC is the acoustic coupling, measured from the speaker differential voltage to the microphone output voltage 23 4743D–CORD–03/06 8.2.1 Transmit Gain The transmit gain, from the microphone output (VM) to Tip and Ring, is determined by the output characteristics of the microphone, and the desired transmit level. For example, a typical electret microphone will produce approximately 0.35 mVrms under normal speech conditions. To achieve 100 mVrms at Tip/Ring, an overall gain of 285V/V is necessary. The gain of the transmit attenuator is fixed at 2.0 (+6.0 dB), and the gain through the hybrid of Figure 1-2 on page 2 (GHT) is nominally 0.4 (–8.0 dB). Therefore, a gain of 357V/V is required of the microphone and hybrid amplifiers. It is desirable to have the majority of that gain in the microphone amplifier for three reasons: 1. The low-level signals from the microphone should be amplified as soon as possible to minimize signal/noise problems; 2. to provide a reasonable signal level to the TLI2 level detector; 3. and to minimize any gain applied to broadband noise generated within the attenuator. However, to cover the normal voice band, the microphone amplifier's gain should not exceed 48 dB (Figure 7-7 on page 19). For the circuit in Figure 8-3 on page 23, the gain of the microphone amplifier was set at 35V/V (31 dB), and the differential gain of the hybrid amplifiers was set at 10.2V/V (20.1 dB). 8.2.2 Receive Gain The overall receive gain depends on the incoming signal level and the desired output power at the speaker. Nominal receive levels (independent of the peaks) at Tip/Ring can be 35 mVrms (–27 dBm), although on long lines that level can be down to 8.0 mVrms (-40 dBm). The speaker power is: dBm/10 10 × 0.6 P SPK = -------------------------------------RS (1) where RS is the speaker impedance, and the dBm term is the incoming signal level increased by the gain of the receive path. Experience has shown that approximately 30 dB gain is a satisfactory amount for the majority of applications. Using the above numbers and equation 1, it would appear that the resulting power to the speaker is extremely low. However, equation 1 does not consider the peaks in normal speech which can be 10 to 15 times the rms value. Considering the peaks, the overall average power approaches 20 to 30 mW on long lines, and much more on short lines. Referring to Figure 1-2 on page 2, the gain from Tip/Ring to the filter input was measured at 0.833V/V (–1.6 dB), the filter's gain is unity, and the receive attenuator's gain is 2.0V/V (+6.0 dB) at maximum volume. The speaker amplifier's gain is set at 22V/V (26.8 dB) which puts the overall gain at approximately 31.2 dB. 8.2.3 Loop Gain The total loop gain (of Figure 8-3 on page 23) must add up to less than 0 dB to obtain a stable circuit. This can be expressed as: GMA + GT + GHA + GST + GFO + GR + GSA + GAC < 0 (2) Using the typical numbers mentioned above, and knowing that GT + GR = –40 dB, the required acoustic coupling can be determined: GAC < –[31 + 20.1 + (–15) + 0 + (–40) + 26.8] = –22.9 dB( 3 ) 24 U4082B 4743D–CORD–03/06 U4082B An acoustic loss of at least 23 dB is necessary to prevent instability and oscillations, commonly referred to as “singing”. However, the following equations show that greater acoustic loss is necessary to obtain proper level detection and switching. 8.2.4 Switching Thresholds To switch comparator C1, currents I1 and I3 need to be determined. Referring to Figure 8-3 on page 23, with a receive signal VL applied to Tip/Ring, a current I3 will flow through R3 into RLI2 according to the following equation: G SA VL I 3 = ------- × G HR × G FO × G R × ----------R3 2 (4) where the terms in the brackets are the V/V gain terms. The speaker amplifier gain is divided by two since GSA is the differential gain of the amplifier, and V3 is obtained from one side of that output. The current I1, coming from the microphone circuit, is defined by: V M × G MA I 1 = -------------------------R1 (5) where VM is the microphone voltage. Since the switching threshold occurs when I1 = I3, combining the above two equations yields: R 1 [ G HR × G FO × G R × G SA ] V M = V L × ------- × --------------------------------------------------------------------G MA × 2 R3 (6) This is the general equation defining the microphone voltage necessary to switch comparator C1 when a receive signal VL is present. The highest VM occurs when the receive attenuator is at maximum gain (+6.0 dB). Using the typical numbers for equation 6 yields: VM = 0.52 × VL (7) To switch comparator C2, currents I2 and I4 need to be determined. With sound applied to the microphone, a voltage VM is created by the microphone, resulting in a current I2 into TLI1: G HA VM I 2 = -------- × G MA × G T × ----------R2 2 (8) Since GHA is the differential gain of the hybrid amplifiers, it is divided by two to obtain the voltage V2 applied to R2. Comparator C2 switches when I4 = I2. I4 is defined by: V I 4 = ------L- [ G HR × G FO ] R4 (9) Setting I4 = I2, and combining the above equations results in: R 4 [ G MA × G T × G HA ] V L = V M × ------- × -------------------------------------------------G HR × G FO × 2 R2 (10) 25 4743D–CORD–03/06 This equation defines the line voltage at Tip/Ring necessary to switch comparator C2 in the presence of a microphone voltage. The highest VL occurs when the circuit is in transmit mode (GT = +6.0 dB). Using the typical numbers for equation 10 yields: VL = 840 × VM (or VM = 0.0019 × VL) (11) At idle, where the gain of the two attenuators is –20 dB (0.1V/V), equations 6 and 10 yield the same result: VM = 0.024 × VL (12) Equations 7, 11, and 12 define the thresholds for switching, and are represented in Figure 8-4 The "M" terms are the slopes of the lines (0.52, 0.024, and 0.0019) which are the coefficients of the three equations. The MR line represents the receive to transmit threshold, in that it defines the microphone signal level necessary to switch to transmit in the presence of a given receive signal level. The MT line represents the transmit to receive threshold. The MI line represents the idle condition, and defines the threshold level on one side (transmit or receive) necessary to overcome noise on the other. Figure 8-4. Switching Thresholds MR VM MI MT VL Some comments on the graph (see Figure 8-4): • Acoustic coupling and side tone coupling were not included in equations 7 and 12. Those couplings will affect the actual performance of the final speakerphone due to their interaction with speech at the microphone and the receive signal coming in at Tip/Ring. The effects of those couplings are difficult to predict due to their associated phase shifts and frequency response. In some cases the coupling signal will add, and other times subtract from the incoming signal. The physical design of the speakerphone enclosure, as well as the specific phone line to which it is connected, will affect the acoustic and side tone couplings, respectively. • The MR line helps define the maximum acoustic coupling allowed in a system, which can be found from the following equation: R1 G AC(MAX) = -----------------------------------2 × R 3 × G MA 26 (13) U4082B 4743D–CORD–03/06 U4082B Equation 13 is independent of the volume control setting. Conversely, the acoustic coupling of a designed system helps determine the minimum slope of that line. Using the component values of Figure 1-2 on page 2 in equation 13 yields a GAC(MAX) of –37 dB. Experience has shown, however, that an acoustic coupling loss of 40 dB is desirable. • The MT line helps define the maximum side tone coupling (GST) allowed in the system. GST can be found using the following equation: R4 G ST = ----------------------------------2 × R 2 × G FO (14) Using the component values of Figure 1-2 on page 2 in equation 14 yields a maximum side tone of 0 dB. Experience has shown, however, that a minimum of 6.0 dB loss is preferable. The above equations can be used to determine the resistor values for the level detector inputs. Equation 6 can be used to determine the R1-R3 ratio, and equation 10 can be used to determine the R1-R2 ratio. In Figure 8-3 on page 23, R1-R4 each represent the combined impedance of the resistor and coupling capacitor at each level detector input. The magnitude of each RC's impedance should be kept within the range of 2.0 kΩ to 15 kΩ in the voice band (due to the typical signal levels present) to obtain the best performance from the level detectors. The specific R and C at each location will determine the frequency response of that level detector. 9. Application Information 9.1 Dial Tone Detector The threshold for the dial tone detector is internally set at 15 mV (10 mVrms) below VB (see Figure 3-3 on page 7). That threshold can be reduced by connecting a resistor from RI to ground. The resistor value is calculated from: VB R = 10 k -------–1 ∆V where VB is the voltage at pin 15, and ∆V is the amount of threshold reduction. By connecting a resistor from VS to RI, the threshold can be increased. The resistor value is calculated from: VS – VB -–1 R = 10 k ------------------∆V where ∆V is the amount of the threshold increase. 9.2 Background Noise Monitors For testing or circuit analysis purposes, the transmit or receive attenuators can be set to the “on” position by disabling the background noise monitors and applying a signal so as to activate the level detectors. Grounding the CPR pin will disable the receive background noise monitor, thereby indicating the “presence of speech” to the attenuator control block. Grounding CPT does the same for the transmit path. Additionally, the receive background noise monitor is automatically disabled by the dial tone detector whenever the receive signal exceeds the detector's threshold. 27 4743D–CORD–03/06 9.3 Transmit/Receive Detection Priority Although the U4082B was designed to have idle mode such that the attenuators are halfway between their full on and full off positions, idle mode can be biased towards the transmit or the receive side. With this done, gaining control of the circuit from idle will be easier for that side towards which it is biased since that path will have less attenuation at idle. By connecting a resistor from CT (pin 14) to ground, the circuit will be biased towards the transmit side. The resistor value is calculated from: VB R = R T -------–1 ∆V where RT = 120 kΩ (typ.) connected between pin 14 and 15. ∆V= VB – V14 (see Figure 7-1 on page 17). By connecting a resistor from CT (pin 14) to VS, the circuit will be biased towards the receive side. The resistor value is calculated from: VS – VB -–1 R = R T ------------------∆V Switching time will be somewhat affected in each case due to the different voltage excursions required to get to transmit and receive from idle. For practical considerations, the ∆V shift should not exceed 100 mV. 28 U4082B 4743D–CORD–03/06 U4082B 10. Ordering Information Extended Type Number Package Remarks U4082B-MFLG SO28 Tube, Pb-free U4082B-MFLG3G SO28 Taped and reeled, Pb-free 11. Package Information Package SO28 Dimensions in mm 9.15 8.65 18.05 17.80 7.5 7.3 2.35 1.27 28 0.25 0.25 0.10 0.4 10.50 10.20 16.51 15 technical drawings according to DIN specifications 1 14 29 4743D–CORD–03/06 Atmel Corporation 2325 Orchard Parkway San Jose, CA 95131, USA Tel: 1(408) 441-0311 Fax: 1(408) 487-2600 Regional Headquarters Europe Atmel Sarl Route des Arsenaux 41 Case Postale 80 CH-1705 Fribourg Switzerland Tel: (41) 26-426-5555 Fax: (41) 26-426-5500 Asia Room 1219 Chinachem Golden Plaza 77 Mody Road Tsimshatsui East Kowloon Hong Kong Tel: (852) 2721-9778 Fax: (852) 2722-1369 Japan 9F, Tonetsu Shinkawa Bldg. 1-24-8 Shinkawa Chuo-ku, Tokyo 104-0033 Japan Tel: (81) 3-3523-3551 Fax: (81) 3-3523-7581 Atmel Operations Memory 2325 Orchard Parkway San Jose, CA 95131, USA Tel: 1(408) 441-0311 Fax: 1(408) 436-4314 RF/Automotive Theresienstrasse 2 Postfach 3535 74025 Heilbronn, Germany Tel: (49) 71-31-67-0 Fax: (49) 71-31-67-2340 Microcontrollers 2325 Orchard Parkway San Jose, CA 95131, USA Tel: 1(408) 441-0311 Fax: 1(408) 436-4314 La Chantrerie BP 70602 44306 Nantes Cedex 3, France Tel: (33) 2-40-18-18-18 Fax: (33) 2-40-18-19-60 ASIC/ASSP/Smart Cards 1150 East Cheyenne Mtn. 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Unless specifically provided otherwise, Atmel products are not suitable for, and shall not be used in, automotive applications. Atmel’s products are not intended, authorized, or warranted for use as components in applications intended to support or sustain life. © Atmel Corporation 2006. All rights reserved. Atmel ®, logo and combinations thereof, Everywhere You Are ® and others, are registered trademarks or trademarks of Atmel Corporation or its subsidiaries. Other terms and product names may be trademarks of others. Printed on recycled paper. 4743D–CORD–03/06