AD AD8628AUJZ-R2 Zero-drift, single-supply, rail-to-rail input/output operational amplifier Datasheet

Zero-Drift, Single-Supply, Rail-to-Rail
Input/Output Operational Amplifier
AD8628/AD8629/AD8630
Lowest auto-zero amplifier noise
Low offset voltage: 1 μV
Input offset drift: 0.002 μV/°C
Rail-to-rail input and output swing
5 V single-supply operation
High gain, CMRR, and PSRR: 120 dB
Very low input bias current: 100 pA max
Low supply current: 1.0 mA
Overload recovery time: 10 μs
No external components required
PIN CONFIGURATIONS
OUT 1
V– 2
AD8628
5
V+
4
–IN
TOP VIEW
(Not to Scale)
+IN 3
02735-001
FEATURES
Figure 1. 5-Lead TSOT (UJ-5)
and 5-Lead SOT-23 (RT-5)
NC 1
–IN 2
AD8628
8
NC
7
V+
Automotive sensors
Pressure and position sensors
Strain gage amplifiers
Medical instrumentation
Thermocouple amplifiers
Precision current sensing
Photodiode amplifier
NC = NO CONNECT
Figure 2. 8-Lead SOIC_N (R-8)
OUT A 1
–IN A 2
AD8629
8
V+
7
OUT B
+IN A 3
6 –IN B
TOP VIEW
V– 4 (Not to Scale) 5 +IN B
02735-063
APPLICATIONS
6 OUT
TOP VIEW
V– 4 (Not to Scale) 5 NC
02735-002
+IN 3
OUT A 1
–IN A 2
AD8629
+IN A 3
TOP VIEW
(Not to Scale)
V– 4
8
V+
7
OUT B
6
–IN B
5
+IN B
02735-064
Figure 3. 8-Lead SOIC_N (R-8)
OUT A
1
14
OUT D
–IN A
2
13
–IN D
+IN A
3
AD8630
12
+IN D
V+
4
TOP VIEW
(Not to Scale)
11
V–
+IN B
5
10
+IN C
–IN B
6
9
–IN C
OUT B
7
8
OUT C
02735-066
Figure 4. 8-Lead MSOP (RM-8)
Figure 5. 14-Lead SOIC_N (R-14)
OUT A 1
14 OUT D
–IN A 2
+IN A 3
13 –IN D
AD8630
12 +IN D
TOP VIEW
11 V–
(Not to Scale)
+IN B 5
10 +IN C
–IN B 6
9
–IN C
OUT B 7
8
OUT C
02735-065
V+ 4
Figure 6. 14-Lead TSSOP (RU-14)
Rev. E
Information furnished by Analog Devices is believed to be accurate and reliable.
However, no responsibility is assumed by Analog Devices for its use, nor for any
infringements of patents or other rights of third parties that may result from its use.
Specifications subject to change without notice. No license is granted by implication
or otherwise under any patent or patent rights of Analog Devices. Trademarks and
registered trademarks are the property of their respective owners.
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 781.329.4700
www.analog.com
Fax: 781.461.3113
© 2005 Analog Devices, Inc. All rights reserved.
AD8628/AD8629/AD8630
TABLE OF CONTENTS
General Description ......................................................................... 3
Specifications..................................................................................... 4
Electrical Characteristics—Vs = 5.0 V............................................. 4
Electrical Characteristics—Vs = 2.7 V............................................. 5
Absolute Maximum Ratings............................................................ 6
ESD Caution.................................................................................. 6
Typical Performance Characteristics ............................................. 7
Functional Description .................................................................. 15
1/f Noise....................................................................................... 15
Peak-to-Peak Noise .................................................................... 16
Total Integrated Input-Referred Noise
for First-Order Filter.................................................................. 16
Input Overvoltage Protection ................................................... 17
Output Phase Reversal............................................................... 17
Overload Recovery Time .......................................................... 17
Infrared Sensors.......................................................................... 18
Precision Current Shunt Sensor ............................................... 19
Output Amplifier for High Precision DACs........................... 19
Outline Dimensions ....................................................................... 20
Ordering Guide .......................................................................... 22
Noise Behavior with First-Order Low-Pass Filter.................. 16
REVISION HISTORY
5/05—Rev. D to Rev. E
Changes to Ordering Guide .......................................................... 22
1/05—Rev. C to Rev. D
Added AD8630 ...................................................................Universal
Added Figure 5 and Figure 6........................................................... 1
Changes to Caption in Figure 8 and Figure 9 ............................... 7
Changes to Caption in Figure 14 .................................................... 8
Changes to Figure 17........................................................................ 8
Changes to Figure 23 and Figure 24............................................... 9
Changes to Figure 25 and Figure 26............................................. 10
Changes to Figure 31...................................................................... 11
Changes to Figure 40, Figure 41, Figure 42................................. 12
Changes to Figure 43 and Figure 44............................................. 13
Changes to Figure 51...................................................................... 15
Updated Outline Dimensions ....................................................... 20
Changes to Ordering Guide .......................................................... 22
10/03—Rev. A to Rev. B
Changes to General Description .....................................................1
Changes to Absolute Maximum Ratings........................................4
Changes to Ordering Guide .............................................................4
Added TSOT-23 Package .............................................................. 15
6/03—Rev. 0 to Rev. A
Changes to Specifications.................................................................3
Changes to Ordering Guide .............................................................4
Change to Functional Description............................................... 10
Updated Outline Dimensions....................................................... 15
10/02—Revision 0: Initial Version
10/04—Rev. B to Rev. C
Updated Formatting ...........................................................Universal
Added AD8629 ...................................................................Universal
Added SOIC and MSOP Pin Configurations ............................... 1
Added Figure 48.............................................................................. 13
Changes to Figure 62...................................................................... 17
Added MSOP Package ................................................................... 19
Changes to Ordering Guide .......................................................... 22
Rev. E | Page 2 of 24
AD8628/AD8629/AD8630
GENERAL DESCRIPTION
This amplifier has ultralow offset, drift, and bias current. The
AD8628/AD8629/AD8630 are wide bandwidth auto-zero
amplifiers featuring rail-to-rail input and output swings and low
noise. Operation is fully specified from 2.7 V to 5 V single
supply (±1.35 V to ±2.5 V dual supply).
The AD8628/AD8629/AD8630 provide benefits previously
found only in expensive auto-zeroing or chopper-stabilized
amplifiers. Using Analog Devices’ topology, these zero-drift
amplifiers combine low cost with high accuracy and low noise.
No external capacitor is required. In addition, the AD8628/
AD8629/AD8630 greatly reduce the digital switching noise
found in most chopper-stabilized amplifiers.
With an offset voltage of only 1 μV, drift of less than
0.005 μV/°C, and noise of only 0.5 μV p-p (0 Hz to 10 Hz), the
AD8628/AD8629/AD8630 are suited for applications in which
error sources cannot be tolerated. Position and pressure sensors,
medical equipment, and strain gage amplifiers benefit greatly
from nearly zero drift over their operating temperature range.
Many systems can take advantage of the rail-to-rail input and
output swings provided by the AD8628/AD8629/AD8630 to
reduce input biasing complexity and maximize SNR.
The AD8628/AD8629/AD8630 are specified for the extended
industrial temperature range (−40°C to +125°C). The AD8628
is available in tiny TSOT-23, SOT-23, and the 8-lead narrow
SOIC plastic packages. The AD8629 is available in the standard
8-lead narrow SOIC and MSOP plastic packages. The AD8630
quad amplifier is available in 14-lead narrow SOIC and TSSOP
plastic packages.
Rev. E | Page 3 of 24
AD8628/AD8629/AD8630
SPECIFICATIONS
ELECTRICAL CHARACTERISTICS—VS = 5.0 V
VS = 5.0 V, VCM = 2.5 V, TA = 25°C, unless otherwise noted.
Table 1.
Parameter
INPUT CHARACTERISTICS
Offset Voltage
Symbol
Conditions
Min
VOS
Typ
Max
Unit
1
5
10
100
300
1.5
200
250
5
μV
μV
pA
pA
nA
pA
pA
V
dB
dB
dB
dB
μV/°C
−40°C ≤ TA ≤ +125°C
Input Bias Current
(AD8630)
IB
Input Offset Current
IOS
30
100
−40°C ≤ TA ≤ +125°C
50
−40°C ≤ TA ≤ +125°C
Input Voltage Range
Common-Mode Rejection Ratio
CMRR
Large Signal Voltage Gain 1
AVO
Offset Voltage Drift
OUTPUT CHARACTERISTICS
Output Voltage High
∆VOS/∆T
VOH
Output Voltage Low
VOL
Short-Circuit Limit
ISC
VCM = 0 V to 5 V
−40°C ≤ TA ≤ +125°C
RL = 10 kΩ, VO = 0.3 V to 4.7 V
−40°C ≤ TA ≤ +125°C
−40°C ≤ TA ≤ +125°C
RL = 100 kΩ to ground
−40°C ≤ TA ≤ +125°C
RL = 10 kΩ to ground
−40°C ≤ TA ≤ +125°C
RL = 100 kΩ to V+
−40°C ≤ TA ≤ +125°C
RL = 10 kΩ to V+
−40°C ≤ TA ≤ +125°C
0
120
115
125
120
4.99
4.99
4.95
4.95
±25
−40°C ≤ TA ≤ +125°C
Output Current
IO
−40°C ≤ TA ≤ +125°C
POWER SUPPLY
Power Supply Rejection Ratio
Supply Current/Amplifier
INPUT CAPACITANCE
Differential
Common-Mode
DYNAMIC PERFORMANCE
Slew Rate
Overload Recovery Time
Gain Bandwidth Product
NOISE PERFORMANCE
Voltage Noise
Voltage Noise Density
Current Noise Density
1
PSRR
ISY
VS = 2.7 V to 5.5 V
−40°C ≤ TA ≤ +125°C
VO = 0 V
−40°C ≤ TA ≤ +125°C
CIN
SR
4.996
4.995
4.98
4.97
1
2
10
15
±50
±40
±30
±15
130
0.85
1.0
0.02
5
5
20
20
1.1
1.2
V
V
V
V
mV
mV
mV
mV
mA
mA
mA
mA
dB
mA
mA
1.5
8.0
pF
pF
RL = 10 kΩ
1.0
0.05
2.5
V/μs
ms
MHz
0.1 Hz to 10 Hz
0.1 Hz to 1.0 Hz
f = 1 kHz
f = 10 Hz
0.5
0.16
22
5
μV p-p
μV p-p
nV/√Hz
fA/√Hz
GBP
en p-p
en p-p
en
in
115
140
130
145
135
0.002
Gain testing is highly dependent on test bandwidth.
Rev. E | Page 4 of 24
AD8628/AD8629/AD8630
ELECTRICAL CHARACTERISTICS—VS = 2.7 V
VS = 2.7 V, VCM = 1.35 V, VO = 1.4 V, TA = 25°C, unless otherwise noted.
Table 2.
Parameter
INPUT CHARACTERISTICS
Offset Voltage
Symbol
Conditions
Min
VOS
Typ
Max
Unit
1
5
10
100
300
1.5
200
250
2.7
μV
μV
pA
pA
nA
pA
pA
V
dB
dB
dB
dB
μV/°C
−40°C ≤ TA ≤ +125°C
Input Bias Current
(AD8630)
IB
Input Offset Current
IOS
30
100
1.0
50
−40°C ≤ TA ≤ +125°C
−40°C ≤ TA ≤ +125°C
Input Voltage Range
Common-Mode Rejection Ratio
CMRR
Large Signal Voltage Gain 1
AVO
Offset Voltage Drift
OUTPUT CHARACTERISTICS
Output Voltage High
∆VOS/∆T
VOH
Output Voltage Low
VOL
Short-Circuit Limit
ISC
VCM = 0 V to 2.7 V
−40°C ≤ TA ≤ +125°C
RL = 10 kΩ, VO = 0.3 V to 2.4 V
−40°C ≤ TA ≤ +125°C
−40°C ≤ TA ≤ +125°C
RL = 100 kΩ to ground
−40°C ≤ TA ≤ +125°C
RL = 10 kΩ to ground
−40°C ≤ TA ≤ +125°C
RL = 100 kΩ to V+
−40°C ≤ TA ≤ +125°C
RL = 10 kΩ to V+
−40°C ≤ TA ≤ +125°C
0
115
110
110
105
2.68
2.68
2.67
2.67
±10
−40°C ≤ TA ≤ +125°C
Output Current
IO
−40°C ≤ TA ≤ +125°C
POWER SUPPLY
Power Supply Rejection Ratio
Supply Current/Amplifier
INPUT CAPACITANCE
Differential
Common-Mode
DYNAMIC PERFORMANCE
Slew Rate
Overload Recovery Time
Gain Bandwidth Product
NOISE PERFORMANCE
Voltage Noise
Voltage Noise Density
Current Noise Density
1
PSRR
ISY
VS = 2.7 V to 5.5 V
−40°C ≤ TA ≤ +125°C
VO = 0 V
−40°C ≤ TA ≤ +125°C
CIN
SR
2.695
2.695
2.68
2.675
1
2
10
15
±15
±10
±10
±5
130
0.75
0.9
0.02
5
5
20
20
1.0
1.2
V
V
V
V
mV
mV
mV
mV
mA
mA
mA
mA
dB
mA
mA
1.5
8.0
pF
pF
RL = 10 kΩ
1
0.05
2
V/μs
ms
MHz
0.1 Hz to 10 Hz
f = 1 kHz
f = 10 Hz
0.5
22
5
μV p-p
nV/√Hz
fA/√Hz
GBP
en p-p
en
in
115
130
120
140
130
0.002
Gain testing is highly dependent on test bandwidth.
Rev. E | Page 5 of 24
AD8628/AD8629/AD8630
ABSOLUTE MAXIMUM RATINGS
Table 3.
Parameters
Supply Voltage
Input Voltage
Differential Input Voltage 1
Output Short-Circuit Duration to GND
Storage Temperature Range
R, RM, RU, RT, UJ Packages
Operating Temperature Range
Junction Temperature Range
R, RM, RU, RT, UJ Packages
Lead Temperature Range
(Soldering, 60 sec)
1
Ratings
6V
GND − 0.3 V to VS− + 0.3 V
±5.0 V
Indefinite
Stresses above those listed under Absolute Maximum Ratings
may cause permanent damage to the device. This is a stress
rating only; functional operation of the device at these or any
other conditions above those indicated in the operational
section of this specification is not implied. Exposure to absolute
maximum rating conditions for extended periods may affect
device reliability.
−65°C to +150°C
−40°C to +125°C
Table 4. Thermal Characteristics
−65°C to +150°C
300°C
Differential input voltage is limited to ±5 V or the supply voltage, whichever
is less.
Package Type
5-Lead TSOT-23 (UJ-5)
5-Lead SOT-23 (RT-5)
8-Lead SOIC_N (R-8)
8-Lead MSOP (RM-8)
14-Lead SOIC_N (R-14)
14-Lead TSSOP (RU-14)
1
θJA 1
207
230
158
190
105
148
θJC
61
146
43
44
43
23
Unit
°C/W
°C/W
°C/W
°C/W
°C/W
°C/W
θJA is specified for worst-case conditions, that is, θJA is specified for the device
soldered in a circuit board for surface-mount packages. This was measured
using a standard 2-layer board.
ESD CAUTION
ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily accumulate on
the human body and test equipment and can discharge without detection. Although this product features
proprietary ESD protection circuitry, permanent damage may occur on devices subjected to high energy
electrostatic discharges. Therefore, proper ESD precautions are recommended to avoid performance
degradation or loss of functionality.
Rev. E | Page 6 of 24
AD8628/AD8629/AD8630
TYPICAL PERFORMANCE CHARACTERISTICS
180
100
VS = 2.7V
TA = 25°C
VS = 5V
VCM = 2.5V
TA = 25°C
90
80
140
NUMBER OF AMPLIFIERS
120
100
80
60
40
70
60
50
40
30
0
–2.5
–1.5
–0.5
0.5
INPUT OFFSET VOLTAGE (μV)
1.5
02735-006
02735-003
20
20
10
0
–2.5
2.5
–1.5
Figure 7. Input Offset Voltage Distribution
2.5
7
+85°C
NUMBER OF AMPLIFIERS
40
30
20
+25°C
10
0
1
2
3
4
5
INPUT COMMON-MODE VOLTAGE (V)
5
4
3
2
1
02735-004
–40°C
0
VS = 5V
TA = –40°C TO +125°C
6
50
02735-007
VS = 5V
INPUT BIAS CURRENT (pA)
1.5
Figure 10. Input Offset Voltage Distribution
60
0
0
6
2
4
6
TCVOS (nV/°C)
8
10
1
10
Figure 11. Input Offset Voltage Drift
Figure 8. AD8628 Input Bias Current vs. Input Common-Mode
1k
1500
VS = 5V
VS = 5V
TA = 25°C
150°C
1000
100
125°C
OUTPUT VOLTAGE (mV)
INPUT BIAS CURRENT (pA)
–0.5
0.5
INPUT OFFSET VOLTAGE (μV)
500
0
–500
10
SOURCE
SINK
1
0.1
02735-005
–1000
–1500
0
1
2
3
4
5
INPUT COMMON-MODE VOLTAGE (V)
0.01
0.0001
6
Figure 9. AD8628 Input Bias Current vs. Input Common-Mode Voltage at 5 V
Rev. E | Page 7 of 24
02735-008
NUMBER OF AMPLIFIERS
160
0.001
0.01
0.1
LOAD CURRENT (mA)
Figure 12. Output Voltage to Supply Rail vs. Load Current
AD8628/AD8629/AD8630
1k
1000
TA = 25°C
VS = 2.7V
800
SUPPLY CURRENT (μA)
10
SOURCE
SINK
1
0.1
600
400
02735-009
200
0.01
0.0001
0.001
0.01
0.1
LOAD CURRENT (mA)
1
02735-012
OUTPUT VOLTAGE (mV)
100
0
10
0
Figure 13. Output Voltage to Supply Rail vs. Load Current
1
2
3
4
SUPPLY VOLTAGE (V)
5
6
Figure 16. Supply Current vs. Supply Voltage
1500
900
450
40
0
45
20
90
135
180
0
100
225
–25
0
25
50
75
100
TEMPERATURE (°C)
125
150
02735-013
02735-010
175
10k
Figure 14. AD8628 Input Bias Current vs. Temperature
100k
1M
FREQUENCY (Hz)
Figure 17. Open-Loop Gain and Phase vs. Frequency
1250
70
TA = 25°C
VS = 5V
CL = 20pF
RL = ∞
φM = 52.1°
60
5V
2.7V
750
500
250
0
50
100
TEMPERATURE (°C)
150
40
0
30
45
20
90
10
135
0
180
–10
225
02735-014
OPEN-LOOP GAIN (dB)
50
02735-011
SUPPLY CURRENT (μA)
1000
0
–50
10M
–20
–30
10k
200
100k
1M
FREQUENCY (Hz)
10M
Figure 18. Open-Loop Gain and Phase vs. Frequency
Figure 15. Supply Current vs. Temperature
Rev. E | Page 8 of 24
PHASE SHIFT (Degrees)
0
–50
PHASE SHIFT (Degrees)
VS = 2.7V
CL = 20pF
RL = ∞
φM = 45°
60
OPEN-LOOP GAIN (dB)
INPUT BIAS CURRENT (pA)
1150
VS = 5V
VCM = 2.5V
TA = –40°C TO +150°C
AD8628/AD8629/AD8630
70
300
VS = 2.7V
CL = 20pF
RL = 2kΩ
60
VS = 5V
270
OUTPUT IMPEDANCE (Ω)
240
40
AV = 100
20
10
AV = 10
0
–10
AV = 1
AV = 1
180
AV = 100
150
120
90
AV = 10
60
–20
–30
1k
210
10k
100k
1M
FREQUENCY (Hz)
02735-018
30
02735-015
CLOSED-LOOP GAIN (dB)
50
30
0
100
10M
Figure 19. Closed-Loop Gain vs. Frequency
1k
10k
100k
1M
FREQUENCY (Hz)
10M
100M
Figure 22. Output Impedance vs. Frequency
70
VS = 5V
CL = 20pF
RL = 2kΩ
60
40
AV = 100
VOLTAGE (500mV/DIV)
CLOSED-LOOP GAIN (dB)
50
30
AV = 10
20
10
AV = 1
0
0V
VS = ±1.35V
CL = 300pF
RL = ∞
AV = 1
02735-016
02735-019
–10
–20
–30
1k
10k
100k
1M
FREQUENCY (Hz)
10M
TIME (4μs/DIV)
Figure 23. Large Signal Transient Response
Figure 20. Closed-Loop Gain vs. Frequency
300
VS = 2.7V
270
VOLTAGE (1V/DIV)
AV = 1
210
180
AV = 100
150
120
0V
VS = ±2.5V
CL = 300pF
RL = ∞
AV = 1
90
30
0
100
02735-020
AV = 10
60
02735-017
OUTPUT IMPEDANCE (Ω)
240
1k
10k
100k
1M
FREQUENCY (Hz)
10M
100M
TIME (5μs/DIV)
Figure 24. Large Signal Transient Response
Figure 21. Output Impedance vs. Frequency
Rev. E | Page 9 of 24
AD8628/AD8629/AD8630
80
VS = ±2.5V
RL = 2kΩ
TA = 25°C
70
60
OVERSHOOT (%)
VOLTAGE (50mV/DIV)
VS = ±1.35V
CL = 50pF
RL = ∞
AV = 1
0V
50
40
30
OS–
20
02735-021
OS+
02735-024
10
0
1
TIME (4μs/DIV)
Figure 25. Small Signal Transient Response
1k
Figure 28. Small Signal Overshoot vs. Load Capacitance
VS = ±2.5V
CL = 50pF
RL = ∞
AV = 1
VS = ±2.5V
AV = –50
RL = 10kΩ
CL = 0
CH1 = 50mV/DIV
CH2 = 1V/DIV
0V
0V
0V
02735-025
VOLTAGE (V)
VIN
02735-022
VOLTAGE (50mV/DIV)
10
100
CAPACITIVE LOAD (pF)
VOUT
TIME (4μs/DIV)
TIME (2μs/DIV)
Figure 26. Small Signal Transient Response
Figure 29. Positive Overvoltage Recovery
100
VS = ±1.35V
RL = 2kΩ
TA = 25°C
90
0V
VS = ±2.5V
AV = –50
RL = 10kΩ
CL = 0
CH1 = 50mV/DIV
CH2 = 1V/DIV
80
VOLTAGE (V)
60
OS–
50
40
VIN
VOUT
OS+
30
20
10
0
1
10
100
CAPACITIVE LOAD (pF)
1k
02735-026
0V
02735-023
OVERSHOOT (%)
70
TIME (10μs/DIV)
Figure 27. Small Signal Overshoot vs. Load Capacitance
Figure 30. Negative Overvoltage Recovery
Rev. E | Page 10 of 24
AD8628/AD8629/AD8630
140
VS = ±1.35V
120
100
80
PSRR (dB)
VOLTAGE (1V/DIV)
VS = ±2.5V
VIN = 1kHz @ ±3V p-p
CL = 0pF
RL = 10kΩ
AV = 1
0V
60
+PSRR
40
20
–PSRR
0
–40
–60
100
TIME (200μs/DIV)
140
100
100
80
80
60
60
PSRR (dB)
120
40
20
20
0
–20
–40
1M
10M
–PSRR
–40
–60
100
10M
1k
10k
100k
FREQUENCY (Hz)
Figure 35. PSRR vs. Frequency
Figure 32. CMRR vs. Frequency
3.0
140
VS = 5V
VS = 2.7V
RL = 10kΩ
TA = 25°C
AV = 1
2.5
OUTPUT SWING (V p-p)
100
80
60
40
20
0
–20
2.0
1.5
1.0
–40
1k
10k
100k
FREQUENCY (Hz)
1M
0
100
10M
02735-032
0.5
02735-029
CMRR (dB)
1M
+PSRR
–20
–60
100
10M
40
0
02735-028
CMRR (dB)
120
120
1M
VS = ±2.5V
VS = 2.7V
10k
100k
FREQUENCY (Hz)
10k
100k
FREQUENCY (Hz)
02735-031
140
1k
1k
Figure 34. PSRR vs. Frequency
Figure 31. No Phase Reversal
–60
100
02735-030
02735-027
–20
1k
10k
FREQUENCY (Hz)
100k
Figure 36. Maximum Output Swing vs. Frequency
Figure 33. CMRR vs. Frequency
Rev. E | Page 11 of 24
1M
AD8628/AD8629/AD8630
5.5
120
VS = 2.7V
NOISE AT 1kHz = 21.3nV
5.0
3.0
2.5
2.0
1.5
0.5
0
100
1k
10k
FREQUENCY (Hz)
100k
0
VOLTAGE NOISE DENSITY (nV/√Hz)
VOLTAGE (μV)
0.30
0.15
0
–0.15
–0.30
02735-034
–0.45
–0.60
2.0
2.5
2
3
4
5
6
TIME (μs)
7
8
9
VS = 2.7V
NOISE AT 10kHz = 42.4nV
105
90
75
60
45
30
15
0
10
0
5
10
15
FREQUENCY (kHz)
20
25
Figure 41. Voltage Noise Density at 2.7 V from 0 Hz to 25 kHz
Figure 38. 0.1 Hz to 10 Hz Noise
0.60
120
VS = 5V
VOLTAGE NOISE DENSITY (nV/√Hz)
0.45
0.30
0.15
0
–0.15
–0.30
–0.45
02735-035
VOLTAGE (μV)
1.0
1.5
FREQUENCY (kHz)
120
0.45
–0.60
1
0.5
Figure 40. Voltage Noise Density at 2.7 V from 0 Hz to 2.5 kHz
VS = 2.7V
0
30
0
0.60
1
45
1M
Figure 37. Maximum Output Swing vs. Frequency
0
60
15
02735-033
1.0
75
02735-036
3.5
90
02735-037
4.0
105
2
3
4
5
6
TIME (μs)
7
8
9
VS = 5V
NOISE AT 1kHz = 22.1nV
105
90
75
60
45
30
15
02735-038
OUTPUT SWING (V p-p)
4.5
VOLTAGE NOISE DENSITY (nV/√Hz)
VS = 5V
RL = 10kΩ
TA = 25°C
AV = 1
0
10
0
Figure 39. 0.1 Hz to 10 Hz Noise
0.5
1.0
1.5
FREQUENCY (kHz)
2.0
Figure 42. Voltage Noise Density at 5 V from 0 Hz to 2.5 kHz
Rev. E | Page 12 of 24
2.5
AD8628/AD8629/AD8630
150
105
90
75
60
45
30
02735-039
15
0
0
5
10
15
FREQUENCY (kHz)
20
50
ISC–
0
ISC+
–50
–25
0
25
50
75
100
TEMPERATURE (°C)
125
150
175
Figure 46. Output Short-Circuit Current vs. Temperature
150
105
90
75
60
45
30
02735-040
15
0
0
5
FREQUENCY (kHz)
VS = 5V
TA = –40°C TO +150°C
100
ISC–
50
0
–50
ISC+
–100
–50
10
Figure 44. Voltage Noise
02735-043
VS = 5V
OUTPUT SHORT-CIRCUIT CURRENT (mA)
120
–25
0
25
50
75
100
TEMPERATURE (°C)
125
150
175
Figure 47. Output Short-Circuit Current vs. Temperature
1k
150
VS = 5V
OUTPUT-TO-RAIL VOLTAGE (mV)
140
130
VS = 2.7V TO 5V
TA = –40°C TO +125°C
120
110
100
90
80
02735-041
70
60
50
–50
–25
0
25
50
TEMPERATURE (°C)
75
100
VCC – VOH @ 1kΩ
100
VOL – VEE @ 1kΩ
VCC – VOH @ 10kΩ
10
VOL – VEE @ 10kΩ
VCC – VOH @ 100kΩ
1
VOL – VEE @ 100kΩ
0.10
–50
125
02735-044
VOLTAGE NOISE DENSITY (nV/√Hz)
100
–100
–50
25
Figure 43. Voltage Noise Density at 5 V from 0 Hz to 25 kHz
POWER SUPPLY REJECTION (dB)
VS = 2.7V
TA = –40°C TO +150°C
02735-042
VS = 5V
NOISE AT 10kHz = 36.4nV
OUTPUT SHORT-CIRCUIT CURRENT (mA)
VOLTAGE NOISE DENSITY (nV/√Hz)
120
–25
0
25
50
75
100
TEMPERATURE (°C)
125
150
Figure 48. Output-to-Rail Voltage vs. Temperature
Figure 45. Power Supply Rejection vs. Temperature
Rev. E | Page 13 of 24
175
AD8628/AD8629/AD8630
140
1k
VSY = ±2.5V
120
VOL – VEE @ 1kΩ
VCC – VOH @ 10kΩ
10
VOL – VEE @ 10kΩ
VCC – VOH @ 100kΩ
1
VOL – VEE @ 100kΩ
0.10
–50
–25
0
25
50
75
100
TEMPERATURE (°C)
125
150
100
80
60
40
R1
10kΩ
+2.5V
VIN
28mV p-p
+
–
20
R2
100Ω
V–
V+
A
B
V–
VOUT
V+
02735-062
CHANNEL SEPARATION (dB)
VCC – VOH @ 1kΩ
100
02735-045
OUTPUT-TO-RAIL VOLTAGE (mV)
VS = 2.7V
–2.5V
0
1k
175
10k
100k
FREQUENCY (Hz)
1M
Figure 50. AD8629/AD8630 Channel Separation
Figure 49. Output-to-Rail Voltage vs. Temperature
Rev. E | Page 14 of 24
10M
AD8628/AD8629/AD8630
FUNCTIONAL DESCRIPTION
Previous designs used either auto-zeroing or chopping to add
precision to the specifications of an amplifier. Auto-zeroing
results in low noise energy at the auto-zeroing frequency, at the
expense of higher low frequency noise due to aliasing of wideband noise into the auto-zeroed frequency band. Chopping
results in lower low frequency noise at the expense of larger
noise energy at the chopping frequency. The AD8628/AD8629/
AD8630 family uses both auto-zeroing and chopping in a
patented ping-pong arrangement to obtain lower low frequency
noise together with lower energy at the chopping and autozeroing frequencies, maximizing the signal-to-noise ratio (SNR)
for the majority of applications without the need for additional
filtering. The relatively high clock frequency of 15 kHz
simplifies filter requirements for a wide, useful, noise-free
bandwidth.
The AD8628 is among the few auto-zero amplifiers offered in
the 5-lead TSOT-23 package. This provides a significant
improvement over the ac parameters of the previous auto-zero
amplifiers. The AD8628/AD8629/AD8630 have low noise over
a relatively wide bandwidth (0 Hz to 10 kHz) and can be used
where the highest dc precision is required. In systems with
signal bandwidths of from 5 kHz to 10 kHz, the AD8628/
AD8629/AD8630 provide true 16-bit accuracy, making them
the best choice for very high resolution systems.
1/f noise, also known as pink noise, is a major contributor to
errors in dc-coupled measurements. This 1/f noise error term
can be in the range of several μV or more, and, when amplified
with the closed-loop gain of the circuit, can show up as a large
output offset. For example, when an amplifier with a 5 μV p-p
1/f noise is configured for a gain of 1,000, its output has 5 mV of
error due to the 1/f noise. But the AD8628/AD8629/AD8630
eliminate 1/f noise internally, and thereby greatly reduce output
errors.
The internal elimination of 1/f noise is accomplished as follows.
1/f noise appears as a slowly varying offset to AD8628/AD8629/
AD8630 inputs. Auto-zeroing corrects any dc or low frequency
offset. Therefore, the 1/f noise component is essentially removed,
leaving the AD8628/AD8629/AD8630 free of 1/f noise.
One of the biggest advantages that the AD8628/AD8629/
AD8630 bring to systems applications over competitive autozero amplifiers is their very low noise. The comparison shown
in Figure 51 indicates an input-referred noise density of
19.4 nV/√Hz at 1 kHz for the AD8628, which is much better
than the LTC2050 and LMC2001. The noise is flat from dc to
1.5 kHz, slowly increasing up to 20 kHz. The lower noise at
low frequency is desirable where auto-zero amplifiers are
widely used.
120
Rev. E | Page 15 of 24
LTC2050
(89.7nV/√Hz)
105
90
75
60
LMC2001
(31.1nV/√Hz)
45
30
15
AD8628
(19.4nV/√Hz)
MK AT 1kHz FOR ALL 3 GRAPHS
0
0
2
4
6
FREQUENCY (kHz)
8
10
Figure 51. Noise Spectral Density of AD8628 vs. Competition
02735-046
The AD8628/AD8629/AD8630 achieve a high degree of precision through a patented combination of auto-zeroing and
chopping. This unique topology allows the AD8628/AD8629/
AD8630 to maintain their low offset voltage over a wide
temperature range and over their operating lifetime. The
AD8628/AD8629/AD8630 also optimize the noise and bandwidth over previous generations of auto-zero amplifiers,
offering the lowest voltage noise of any auto-zero amplifier by
more than 50%.
1/f NOISE
VOLTAGE NOISE DENSITY (nV/√Hz)
The AD8628/AD8629/AD8630 are single-supply, ultrahigh
precision rail-to-rail input and output operational amplifiers.
The typical offset voltage of less than 1 μV allows these amplifiers to be easily configured for high gains without risk of
excessive output voltage errors. The extremely small temperature drift of 2 nV/°C ensures a minimum of offset voltage error
over their entire temperature range of −40°C to +125°C, making
these amplifiers ideal for a variety of sensitive measurement
applications in harsh operating environments.
12
AD8628/AD8629/AD8630
50
PEAK-TO-PEAK NOISE
45
Because of the ping-pong action between auto-zeroing and
chopping, the peak-to-peak noise of the AD8628/AD8629/AD8630
is much lower than the competition. Figure 52 and Figure 53
show this comparison.
40
NOISE (dB)
35
en p-p = 0.5μV
BW = 0.1Hz TO 10Hz
30
25
20
VOLTAGE (0.5μV/DIV)
15
02735-050
10
5
0
0
10
20
30
40
50
60
70
FREQUENCY (kHz)
80
90
100
Figure 55. Simulation Transfer Function of the Test Circuit
02735-047
50
45
40
TIME (1s/DIV)
Figure 52. AD8628 Peak-to-Peak Noise
NOISE (dB)
35
en p-p = 2.3μV
BW = 0.1Hz TO 10Hz
30
25
20
VOLTAGE (0.5μV/DIV)
15
02735-051
10
5
0
0
10
20
30
40
50
60
70
FREQUENCY (kHz)
80
90
100
Figure 56. Actual Transfer Function of the Test Circuit
02735-048
The measured noise spectrum of the test circuit charted in
Figure 56 shows that noise between 5 kHz and 45 kHz is
successfully rolled off by the first-order filter.
TIME (1s/DIV)
TOTAL INTEGRATED INPUT-REFERRED
NOISE FOR FIRST-ORDER FILTER
NOISE BEHAVIOR WITH FIRST-ORDER
LOW-PASS FILTER
The AD8628 was simulated as a low-pass filter (Figure 55) and
then configured as shown in Figure 54. The behavior of the
AD8628 matches the simulated data. It was verified that noise is
rolled off by first-order filtering. Figure 55 and Figure 56 show
the difference between the simulated and actual transfer
functions of the circuit shown in Figure 54.
IN
OUT
LTC2050
AD8551
AD8628
1
470pF
0.1
10
Figure 54. Test Circuit: First-Order Low-Pass Filter,
×101 Gain and 3 kHz Corner Frequency
02735-052
1kΩ
10
02735-049
100kΩ
For a first-order filter, the total integrated noise from the
AD8628 is lower than the LTC2050.
RMS NOISE (μV)
Figure 53. LTC2050 Peak-to-Peak Noise
100
1k
3dB FILTER BANDWIDTH (Hz)
Figure 57. 3 dB Filter Bandwidth in Hz
Rev. E | Page 16 of 24
10k
AD8628/AD8629/AD8630
INPUT OVERVOLTAGE PROTECTION
These diodes are connected between the inputs and each supply
rail to protect the input transistors against an electrostatic discharge event, and they are normally reverse-biased. However, if
the input voltage exceeds the supply voltage, these ESD diodes
can become forward-biased. Without current limiting, excessive
amounts of current could flow through these diodes, causing
permanent damage to the device. If inputs are subject to overvoltage, appropriate series resistors should be inserted to limit
the diode current to less than 5 mA maximum.
TIME (500μs/DIV)
Figure 58. Positive Input Overload Recovery for the AD8628
02735-054
0V
TIME (500μs/DIV)
Figure 59. Positive Input Overload Recovery for LTC2050
CH1 = 50mV/DIV
CH2 = 1V/DIV
AV = –50
VIN
VOLTAGE (V)
Many auto-zero amplifiers are plagued by a long overload
recovery time, often in ms, due to the complicated settling
behavior of the internal nulling loops after saturation of the
outputs. The AD8628/AD8629/AD8630 have been designed so
that internal settling occurs within two clock cycles after output
saturation happens. This results in a much shorter recovery
time, less than 10 μs, when compared to other auto-zero
amplifiers. The wide bandwidth of the AD8628/AD8629/
AD8630 enhances performance when the parts are used to
drive loads that inject transients into the outputs. This is a
common situation when an amplifier is used to drive the input
of switched capacitor ADCs.
0V
VOUT
The AD8628/AD8629/AD8630 amplifiers have been carefully
designed to prevent any output phase reversal, provided that
both inputs are maintained within the supply voltages. If one or
both inputs could exceed either supply voltage, a resistor should
be placed in series with the input to limit the current to less
than 5 mA. This ensures that the output does not reverse its
phase.
OVERLOAD RECOVERY TIME
CH1 = 50mV/DIV
CH2 = 1V/DIV
AV = –50
VIN
Rev. E | Page 17 of 24
0V
0V
02735-055
Output phase reversal occurs in some amplifiers when the input
common-mode voltage range is exceeded. As common-mode
voltage is moved outside of the common-mode range, the
outputs of these amplifiers can suddenly jump in the opposite
direction to the supply rail. This is the result of the differential
input pair shutting down, causing a radical shifting of internal
voltages that results in the erratic output behavior.
0V
VOUT
VOLTAGE (V)
OUTPUT PHASE REVERSAL
0V
02735-053
VOLTAGE (V)
Although the AD8628/AD8629/AD8630 are rail-to-rail input
amplifiers, care should be taken to ensure that the potential
difference between the inputs does not exceed the supply voltage. Under normal negative feedback operating conditions, the
amplifier corrects its output to ensure that the two inputs are at
the same voltage. However, if either input exceeds either supply
rail by more than 0.3 V, large currents begin to flow through the
ESD protection diodes in the amplifier.
CH1 = 50mV/DIV
CH2 = 1V/DIV
AV = –50
VIN
VOUT
TIME (500μs/DIV)
Figure 60. Positive Input Overload Recovery for LMC2001
AD8628/AD8629/AD8630
The results shown in Figure 58 to Figure 63 are summarized in
Table 5.
0V
VOLTAGE (V)
CH1 = 50mV/DIV
CH2 = 1V/DIV
AV = –50
Table 5. Overload Recovery Time
VIN
VOUT
02735-056
0V
Negative Overload
Recovery (μs)
9
25,000
35,000
INFRARED SENSORS
Infrared (IR) sensors, particularly thermopiles, are increasingly
being used in temperature measurement for applications as
wide-ranging as automotive climate control, human ear
thermometers, home insulation analysis, and automotive repair
diagnostics. The relatively small output signal of the sensor
demands high gain with very low offset voltage and drift to
avoid dc errors.
TIME (500μs/DIV)
Figure 61. Negative Input Overload Recovery for the AD8628
0V
CH1 = 50mV/DIV
CH2 = 1V/DIV
AV = –50
VIN
VOUT
0V
02735-057
VOLTAGE (V)
Positive Overload
Recovery (μs)
6
650
40,000
Product
AD8628
LTC2050
LMC2001
If interstage ac coupling is used, as in Figure 64, low offset and
drift prevent the input amplifier’s output from drifting close to
saturation. The low input bias currents generate minimal errors
from the sensor’s output impedance. As with pressure sensors,
the very low amplifier drift with time and temperature eliminate additional errors once the temperature measurement is
calibrated. The low 1/f noise improves SNR for dc measurements taken over periods often exceeding one-fifth of a second.
Figure 64 shows a circuit that can amplify ac signals from
100 μV to 300 μV up to the 1 V to 3 V levels, with gain of
10,000 for accurate A/D conversion.
TIME (500μs/DIV)
Figure 62. Negative Input Overload Recovery for LTC2050
10kΩ
100Ω
100kΩ
100kΩ
5V
5V
100μV – 300μV
IR
DETECTOR
VIN
VOUT
10μF
1/2 AD8629
1/2 AD8629
10kΩ
fC ≈ 1.6Hz
TO BIAS
VOLTAGE
Figure 64. AD8629 Used as Preamplifier for Thermopile
0V
02735-058
VOLTAGE (V)
CH1 = 50mV/DIV
CH2 = 1V/DIV
AV = –50
TIME (500μs/DIV)
Figure 63. Negative Input Overload Recovery for LMC2001
Rev. E | Page 18 of 24
02735-059
0V
AD8628/AD8629/AD8630
PRECISION CURRENT SHUNT SENSOR
OUTPUT AMPLIFIER FOR HIGH PRECISION DACS
A precision current shunt sensor benefits from the unique
attributes of auto-zero amplifiers when used in a differencing
configuration, as shown in Figure 65. Current shunt sensors are
used in precision current sources for feedback control systems.
They are also used in a variety of other applications, including
battery fuel gauging, laser diode power measurement and
control, torque feedback controls in electric power steering, and
precision power metering.
The AD8628/AD8629/AD8360 are used as output amplifiers for
a 16-bit high precision DAC in a unipolar configuration. In this
case, the selected op amp needs to have very low offset voltage
(the DAC LSB is 38 μV when operated with a 2.5 V reference)
to eliminate the need for output offset trims. Input bias current
(typically a few tens of picoamperes) must also be very low,
because it generates an additional zero code error when
multiplied by the DAC output impedance (approximately 6
kΩ).
I
100kΩ
e = 1,000 RS I
100mV/mA
RS
0.1Ω
RL
Rail-to-rail input and output provide full-scale output with very
little error. Output impedance of the DAC is constant and codeindependent, but the high input impedance of the AD8628/
AD8629/AD8630 minimizes gain errors. The amplifiers’ wide
bandwidth also serves well in this case. The amplifiers, with
settling time of 1 μs, add another time constant to the system,
increasing the settling time of the output. The settling time of
the AD5541 is 1 μs. The combined settling time is approximately 1.4 μs, as can be derived from the following equation:
100Ω
C
5V
AD8628
100Ω
C
02735-060
100kΩ
t S (TOTAL ) =
Figure 65. Low-Side Current Sensing
In such applications, it is desirable to use a shunt with very low
resistance to minimize the series voltage drop; this minimizes
wasted power and allows the measurement of high currents
while saving power. A typical shunt might be 0.1 Ω. At
measured current values of 1 A, the shunt’s output signal is
hundreds of mV, or even V, and amplifier error sources are not
critical. However, at low measured current values in the 1 mA
range, the 100 μV output voltage of the shunt demands a very
low offset voltage and drift to maintain absolute accuracy. Low
input bias currents are also needed, so that injected bias current
does not become a significant percentage of the measured
current. High open-loop gain, CMRR, and PSRR help to
maintain the overall circuit accuracy. As long as the rate of
change of the current is not too fast, an auto-zero amplifier can
be used with excellent results.
5V
(t S DAC )2 + (t S AD8628)2
2.5V
0.1μF
0.1μF
SERIAL
INTERFACE
Rev. E | Page 19 of 24
VDD
10μF
REF(REF*)
REFS*
CS
DIN
SCLK
AD5541/AD5542
LDAC*
UNIPOLAR
OUTPUT
OUT
AD8628
DGND
AGND
*AD5542 ONLY
Figure 66. AD8628 Used as an Output Amplifier
03023-061
SUPPLY
AD8628/AD8629/AD8630
OUTLINE DIMENSIONS
5.00 (0.1968)
4.80 (0.1890)
2.90 BSC
5
4
2.80 BSC
1.60 BSC
1
2
8
5
4.00 (0.1574)
3.80 (0.1497) 1
4
3
1.27 (0.0500)
BSC
PIN 1
0.95 BSC
*1.00 MAX
0.10 MAX
0.50
0.30
0.51 (0.0201)
COPLANARITY
SEATING 0.31 (0.0122)
0.10
PLANE
0.20
0.08
8°
4°
0°
SEATING
PLANE
0.60
0.45
0.30
0.50 (0.0196)
× 45°
0.25 (0.0099)
1.75 (0.0688)
1.35 (0.0532)
0.25 (0.0098)
0.10 (0.0040)
1.90
BSC
*0.90
0.87
0.84
6.20 (0.2440)
5.80 (0.2284)
8°
0.25 (0.0098) 0° 1.27 (0.0500)
0.40 (0.0157)
0.17 (0.0067)
COMPLIANT TO JEDEC STANDARDS MS-012AA
CONTROLLING DIMENSIONS ARE IN MILLIMETERS; INCH DIMENSIONS
(IN PARENTHESES) ARE ROUNDED-OFF MILLIMETER EQUIVALENTS FOR
REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN
*COMPLIANT TO JEDEC STANDARDS MO-193-AB WITH
THE EXCEPTION OF PACKAGE HEIGHT AND THICKNESS.
Figure 69. 8-Lead Standard Small Outline Package [SOIC_N]
Narrow Body
(R-8)
Dimensions shown in millimeters and (inches)
Figure 67. 5-Lead Thin Small Outline Transistor Package [TSOT]
(UJ-5)
Dimensions shown in millimeters
3.00
BSC
2.90 BSC
5
8
4
3.00
BSC
2.80 BSC
1.60 BSC
1
2
3
PIN 1
1
5
4.90
BSC
4
PIN 1
0.95 BSC
0.65 BSC
1.90
BSC
1.30
1.15
0.90
1.10 MAX
0.15
0.00
1.45 MAX
0.15 MAX
0.50
0.30
SEATING
PLANE
0.22
0.08
10°
5°
0°
0.60
0.45
0.30
0.38
0.22
COPLANARITY
0.10
0.23
0.08
8°
0°
SEATING
PLANE
COMPLIANT TO JEDEC STANDARDS MO-187AA
COMPLIANT TO JEDEC STANDARDS MO-178AA
Figure 70. 8-Lead Mini Small Outline Package [MSOP]
(RM-8)
Dimensions shown in millimeters
Figure 68. 5-Lead Small Outline Transistor Package [SOT-23]
(RT-5)
Dimensions shown in millimeters
Rev. E | Page 20 of 24
0.80
0.60
0.40
AD8628/AD8629/AD8630
5.10
5.00
4.90
8.75 (0.3445)
8.55 (0.3366)
4.00 (0.1575)
3.80 (0.1496)
0.25 (0.0098)
0.10 (0.0039)
COPLANARITY
0.10
14
8
1
7
1.27 (0.0500)
BSC
0.51 (0.0201)
0.31 (0.0122)
6.20 (0.2441)
5.80 (0.2283)
1.75 (0.0689)
1.35 (0.0531)
SEATING
PLANE
14
0.50 (0.0197)
× 45°
0.25 (0.0098)
8
4.50
4.40
4.30
6.40
BSC
1
7
PIN 1
8°
0.25 (0.0098) 0° 1.27 (0.0500)
0.40 (0.0157)
0.17 (0.0067)
1.05
1.00
0.80
COMPLIANT TO JEDEC STANDARDS MS-012AB
CONTROLLING DIMENSIONS ARE IN MILLIMETERS; INCH DIMENSIONS
(IN PARENTHESES) ARE ROUNDED-OFF MILLIMETER EQUIVALENTS FOR
REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN
0.65
BSC
1.20
MAX
0.15
0.05
0.30
0.19
0.20
0.09
SEATING
COPLANARITY
PLANE
0.10
8°
0°
COMPLIANT TO JEDEC STANDARDS MO-153AB-1
Figure 71. 14-Lead Standard Small Outline Package [SOIC_N]
Narrow Body
(R-14)
Dimensions shown in millimeters and (inches)
Figure 72. 14-Lead Thin Shrink Small Outline Package [TSSOP]
(RU-14)
Dimensions shown in millimeters
Rev. E | Page 21 of 24
0.75
0.60
0.45
AD8628/AD8629/AD8630
ORDERING GUIDE
Model
AD8628AUJ-R2
AD8628AUJ-REEL
AD8628AUJ-REEL7
AD8628AUJZ-R2 1
AD8628AUJZ-REEL1
AD8628AUJZ-REEL71
AD8628AR
AD8628AR-REEL
AD8628AR-REEL7
AD8628ARZ1
AD8628ARZ-REEL1
AD8628ARZ-REEL71
AD8628ART-R2
AD8628ART-REEL7
AD8628ARTZ-R21
AD8628ARTZ-REEL71
AD8629ARZ1
AD8629ARZ-REEL1
AD8629ARZ-REEL71
AD8629ARMZ-R21
AD8629ARMZ-REEL1
AD8630ARUZ1
AD8630ARUZ-REEL1
AD8630ARZ1
AD8630ARZ-REEL1
AD8630ARZ-REEL71
1
Temperature Range
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
Package Description
5-Lead TSOT-23
5-Lead TSOT-23
5-Lead TSOT-23
5-Lead TSOT-23
5-Lead TSOT-23
5-Lead TSOT-23
8-Lead SOIC_N
8-Lead SOIC_N
8-Lead SOIC_N
8-Lead SOIC_N
8-Lead SOIC_N
8-Lead SOIC_N
5-Lead SOT-23
5-Lead SOT-23
5-Lead SOT-23
5-Lead SOT-23
8-Lead SOIC_N
8-Lead SOIC_N
8-Lead SOIC_N
8-Lead MSOP
8-Lead MSOP
14-Lead TSSOP
14-Lead TSSOP
14-Lead SOIC_N
14-Lead SOIC_N
14-Lead SOIC_N
Z = Pb-free part.
Rev. E | Page 22 of 24
Package Option
UJ-5
UJ-5
UJ-5
UJ-5
UJ-5
UJ-5
R-8
R-8
R-8
R-8
R-8
R-8
RT-5
RT-5
RT-5
RT-5
R-8
R-8
R-8
RM-8
RM-8
RU-14
RU-14
R-14
R-14
R-14
Branding
AYB
AYB
AYB
A0L
A0L
A0L
AYA
AYA
A0L
A0L
A06
A06
AD8628/AD8629/AD8630
NOTES
Rev. E | Page 23 of 24
AD8628/AD8629/AD8630
NOTES
©2005 Analog Devices, Inc. All rights reserved. Trademarks and
registered trademarks are the property of their respective owners.
C02735–0–5/05(E)
Rev. E | Page 24 of 24
Similar pages