AD AD8612 Ultrafast 4 ns single supply comparator Datasheet

a
FEATURES
4 ns Propagation Delay at 5 V
Single Supply Operation: 3 V to 5 V
100 MHz Input
Latch Function
APPLICATIONS
High-Speed Timing
Clock Recovery and Clock Distribution
Line Receivers
Digital Communications
Phase Detectors
High-Speed Sampling
Read Channel Detection
PCMCIA Cards
Zero Crossing Detector
High-Speed A/D Converter
Upgrade for LT1394 and LT1016 Designs
Ultrafast 4 ns
Single Supply Comparators
AD8611/AD8612
PIN CONFIGURATIONS
8-Lead Narrow Body SO
(SO-8)
OUT
OUT
GND
LATCH
Vⴙ
ⴙIN
ⴚIN
Vⴚ
AD8611
8-Lead MSOP
(RM-8)
1
Vⴙ
ⴙIN
ⴚIN
Vⴚ
8
OUT
OUT
GND
LATCH
AD8611
4
5
GENERAL DESCRIPTION
The AD8611/AD8612 are single and dual 4 ns comparators with
latch function and complementary output.
Fast 4 ns propagation delay makes the AD8611/AD8612 a good
choice for timing circuits and line receivers. Propagation delays
for rising and falling signals are closely matched and track over
temperature. This matched delay makes the AD8611/AD8612 a
good choice for clock recovery, since the duty cycle of the output
will match the duty cycle of the input.
The AD8611 has the same pinout as the LT1016 and LT1394,
with lower supply current and a wider common-mode input range,
which includes the negative supply rail.
14-Lead TSSOP
(RU-14)
QA 1
14
QB
QA
2
13
QB
GND 3
12
GND
AD8612
LE A 4
TOP VIEW 11 LE B
(Not to Scale) 10 V+
Vⴚ 5
IN Aⴚ 6
9
IN Bⴚ
IN A+ 7
8
IN B+
The AD8611/AD8612 is specified over the industrial (–40°C to
+85°C) temperature range. The AD8611 is available in both 8-lead
MSOP and narrow SO-8 surface mount packages. The AD8612
is available in 14-lead TSSOP surface-mount package.
REV. 0
Information furnished by Analog Devices is believed to be accurate and
reliable. However, no responsibility is assumed by Analog Devices for its
use, nor for any infringements of patents or other rights of third parties
which may result from its use. No license is granted by implication or
otherwise under any patent or patent rights of Analog Devices.
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Fax: 781/326-8703
© Analog Devices, Inc., 2000
AD8611/AD8612–SPECIFICATIONS
ELECTRICAL SPECIFICATIONS
(@ V+ = 5.0 V, V– = VGND = 0 V, TA = 25ⴗC unless otherwise noted)
Parameter
Symbol
INPUT CHARACTERISTICS
Offset Voltage
VOS
Offset Voltage Drift
Input Bias Current
Input Offset Current
Input Common-Mode Voltage Range
Common-Mode Rejection Ratio
Large Signal Voltage Gain
Input Capacitance
LATCH ENABLE INPUT
Logic “1” Voltage Threshold
Logic “0” Voltage Threshold
Logic “1” Current
Logic “0” Current
Latch Enable
Pulsewidth
Setup Time
Hold Time
∆VOS/∆T
IB
IB
IOS
VCM
CMRR
AVO
CIN
VIH
VIL
IIH
IIL
Conditions
Min
Typ
Max
Unit
1
7
8
mV
mV
µV/°C
µA
µA
µA
V
dB
V/V
pF
–40°C ≤ TA ≤ +85°C
VCM = 0 V
–40°C ≤ TA ≤ +85°C
VCM = 0 V
0 V ≤ VCM ≤ 3.0 V
RL = 10 kΩ
–6
–7
0.0
55
2.0
VLH = 3.0 V
VLL = 0.3 V
–1.0
–5
tPW(E)
tS
tH
4
–4
–4.5
±4
3.0
85
3,000
3.0
1.65
1.60
–0.3
–2.7
ns
ns
ns
3.35
3.4
0.25
V
V
V
VOH
VOH
VOL
IOH = 50 µA, ∆VIN > 250 mV
IOH = 3.2 mA, ∆VIN > 250 mV
IOL = 3.2 mA, ∆VIN > 250 mV
DYNAMIC PERFORMANCE
Input Frequency
Propagation Delay
fMAX
tP
400 mV p-p sine wave
200 mV Step with 100 mV Overdrive1
–40°C ≤ TA ≤ +85°C
100 mV Step with 5 mV Overdrive
100
4.0
5
5
∆tP
100 mV Step with 100 mV Overdrive1
20% to 80%
80% to 20%
0.5
2.5
1.1
PSRR
I+
4.5 V ≤ V+ ≤ 5.5 V
Propagation Delay
Differential Propagation Delay
(Rising Propagation Delay vs.
Falling Propagation Delay)
Rise Time
Fall Time
POWER SUPPLY
Power Supply Rejection Ratio
V+ Supply Current2
tP
Ground Supply Current2
IGND
V– Supply Current2
I–
–40°C ≤ TA ≤ +85°C
VO = 0 V, RL = ∞
–40°C ≤ TA ≤ +85°C
55
73
5.7
3.5
2.2
–40°C ≤ TA ≤ +85°C
V
V
µA
µA
3
0.5
0.5
DIGITAL OUTPUTS
Logic “1” Voltage
Logic “1” Voltage
Logic “0” Voltage
3.0
2.4
0.8
0.4
5.5
2.0
10
10
7
7
4
5
MHz
ns
ns
ns
ns
ns
ns
dB
mA
mA
mA
mA
mA
mA
NOTES
1
Guaranteed by design.
2
Per comparator.
Specifications subject to change without notice.
–2–
REV. 0
AD8611/AD8612
ELECTRICAL SPECIFICATIONS
Parameter
(@ V+ = 3.0 V, V– = VGND = 0 V, TA = 25ⴗC unless otherwise noted)
Symbol
INPUT CHARACTERISTICS
Offset Voltage
Input Bias Current
Input Common-Mode Voltage Range
Common-Mode Rejection Ratio
OUTPUT CHARACTERISTICS
Output High Voltage
Output Low Voltage
POWER SUPPLY
Power Supply Rejection Ratio
Supply Currents
V+ Supply Current2
VOS
IB
IB
VCM
CMRR
Conditions
Min
VCM = 0 V
–40°C ≤ TA ≤ +85°C
–6
–7
0
55
0 V ≤ VCM ≤ 1.0 V
VOH
VOL
IOH = –3.2 mA, VIN > 250 mV
IOL = +3.2 mA, VIN > 250 mV
PSRR
2.7 V ≤ V+ ≤ 6 V
VO = 0 V, RL = ∞
Typ
Max
Unit
1
–4.0
–4.5
7
mV
µA
µA
V
dB
1.0
1.21
0.3
46
I+
dB
4.5
–40°C ≤ TA ≤ +85°C
Ground Supply Current2
IGND
V– Supply Current2
2.5
–40°C ≤ TA ≤ +85°C
I–
2
–40°C ≤ TA ≤ +85°C
DYNAMIC PERFORMANCE
Propagation Delay
tP
100 mV Step with 20 mV Overdrive3
V
V
4.5
6.5
10
3.5
5.5
3.5
4.8
mA
mA
mA
mA
mA
mA
6.5
ns
NOTES
1
Output high voltage without pull-up resistor. It may be useful to have a pull-up resistor to V+ for 3 V operation.
2
Per comparator.
3
Guaranteed by design.
Specifications subject to change without notice.
ABSOLUTE MAXIMUM RATINGS
Total Analog Supply Voltage . . . . . . . . . . . . . . . . . . . . . 7.0 V
Digital Supply Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . 7.0 V
Input Voltage1 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . ± 4 V
Differential Input Voltage . . . . . . . . . . . . . . . . . . . . . . . ± 5 V
Output Short-Circuit Duration to GND . . . . . . . . . Indefinite
Storage Temperature Range
R, RU, RM Packages . . . . . . . . . . . . . . . –65°C to +150°C
Operating Temperature Range . . . . . . . . . . . –40°C to +85°C
Junction Temperature Range
R, RU, RM Packages . . . . . . . . . . . . . . . . –65°C to +150°C
Lead Temperature Range (Soldering, 10 sec) . . . . . . . 300°C
Package Type
␪JA2
␪JC
Unit
8-Lead SO (R)
8-Lead MSOP (RM)
14-Lead TSSOP (RU)
158
240
240
43
43
43
°C/W
°C/W
°C/W
NOTES
1
The analog input voltage is equal to ± 4 V or the analog supply voltage, whichever
is less.
2
θJA is specified for the worst-case conditions, i.e., θJA is specified for device in socket
for P-DIP and θJA is specified for device soldered in circuit board for SOIC and
TSSOP packages.
ORDERING GUIDE
Model
Temperature
Range
Package
Description
Package
Option
Branding
Information
AD8611ARM
AD8611AR
AD8612ARU
–40°C to +85°C
–40°C to +85°C
–40°C to +85°C
8-Lead Micro SOIC
8-Lead Small Outline IC
14-Lead Thin Shrink Small Outline
RM-8
SO-8
RU-14
G1A
CAUTION
ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily
accumulate on the human body and test equipment and can discharge without detection.
Although the AD8611/AD8612 features proprietary ESD protection circuitry, permanent damage may occur on devices subjected to high-energy electrostatic discharges. Therefore, proper
ESD precautions are recommended to avoid performance degradation or loss of functionality.
REV. 0
–3–
WARNING!
ESD SENSITIVE DEVICE
AD8611/AD8612
8
18
V+ = 5V
OVERDRIVE > 10mV
6
5
␶PDⴚ
4
V+ = 5V
TA = 25ⴗC
OVERDRIVE = 5mV
14
PROPAGATION DELAY – ns
PROPAGATION DELAY – ns
7
␶PD+
3
2
␶PDⴚ
12
␶PD+
8
6
2
1
0
ⴚ50
0
ⴚ25
0
25
50
TEMPERATURE – ⴗC
75
100
V+ = 5V
TA = 25ⴗC
␶PDⴚ
7
14
12
PROPAGATION DELAY – ns
PROPAGATION DELAY – ns
16
␶PD+
10
8
6
4
2.0
2.5
TA = 25ⴗC
STEP = 100 mV
OVERDRIVE > 10 mV
␶PD+
6
5
␶PDⴚ
4
3
2
1
2
0
0
10
15
OVERDRIVE – mV
5
20
25
2
3
4
SUPPLY VOLTAGE – V
6
5
Figure 5. Propagation Delay vs. Supply Voltage
Figure 2. Propagation Delay vs. Overdrive
35
8
␶PDⴚ
TA = 25ⴗC
STEP = 100 mV
OVERDRIVE = 50 mV
30
PROPAGATION DELAY – ns
V+ = 5V
TA = 25ⴗC
OVERDRIVE > 10mV
7
PROPAGATION DELAY – ns
1.0
1.5
SOURCE RESISTANCE – k⍀
8
18
6
␶PD+
5
4
3
2
25
␶PD+
20
15
10
5
1
0
0.5
Figure 4. Propagation Delay vs. Source Resistance
Figure 1. Propagation Delay Over Temperature
0
0
␶PDⴚ
0
0
20
40
CAPACITANCE – pF
60
80
2
3
4
5
COMMON-MODE VOLTAGE – V
6
Figure 6. Propagation Delay vs. Common-Mode Voltage
Figure 3. Propagation Delay vs. Load Capacitance
–4–
REV. 0
AD8611/AD8612
1.2
0.40
VS = 3V
+25ⴗC
0.35
1.0
+85ⴗC
ⴚ40ⴗC
LOAD CURRENT – V
0.30
0.8
VOS – mV
VS = 5V
0.6
0.4
ⴚ40ⴗC
0.25
0.20
+85ⴗC
0.15
+25ⴗC
0.10
0.2
0.05
0
ⴚ60
ⴚ40
ⴚ20
0
20
40
60
80
0
100
0
2
4
6
8
SINK CURRENT – mA
TEMPERATURE – ⴗC
Figure 7. Offset Voltage vs. Temperature
4.0
V+ = 5V
TA = 25ⴗC
3.8
OUTPUT HIGH VOLTAGE – V
35
30
25
ISY+ – mA
12
Figure 10. Output Low Voltage vs. Load Current
(Sinking) Over Temperature
40
20
15
10
+85ⴗC
3.6
3.4
+25ⴗC
3.2
ⴚ40ⴗC
3.0
2.8
2.6
5
0
10
1
10
INPUT FREQUENCY – MHz
2.4
100
Figure 8. Supply Current vs. Input Frequency
0
2
4
6
8
LOAD CURRENT – mA
10
12
Figure 11. Output High Voltage vs. Load Current
(Sourcing) Over Temperature
2.0
8
V+ = 5V
1.8
7
1.6
6
VS = 5V
5
1.2
ISY – mA
TIMING – ns
1.4
1.0
0.8
SETUP TIME
4
VS = 3V
3
0.6
2
0.4
HOLD TIME
1
0.2
0
ⴚ50
ⴚ25
0
25
50
TEMPERATURE – ⴗC
75
0
ⴚ60
100
Figure 9. Latch Setup and Hold Time Over Temperature
REV. 0
ⴚ40
ⴚ20
0
20
40
TEMPERATURE – ⴗC
60
80
100
Figure 12. Supply Current vs. Temperature
–5–
AD8611/AD8612
0
V+ = 5V
TA = 25ⴗC
ⴚ0.5
ⴚ1.0
VIN
ⴚ2.0
VOLTAGE
IGND – mA
ⴚ1.5
VS = 3V
ⴚ2.5
0V
VOUT
ⴚ3.0
VS = 5V
ⴚ3.5
VIN TRACE – 10mV/DIV
VOUT TRACE – 1V/DIV
ⴚ4.0
ⴚ4.5
ⴚ50
100
50
0
TEMPERATURE – ⴗC
TIME – 2ns/DIV
Figure 13. IGND vs. Temperature
Figure 16. Falling Edge Response
0
V+ = 5V
TA = 25ⴗC
ⴚ0.5
VOUT
VOLTAGE
ISY – mA
ⴚ1.0
VS = 3V
ⴚ1.5
ⴚ2.0
VIN
VS = 5V
ⴚ2.5
ⴚ3.0
ⴚ60
VIN TRACE – 10mV/DIV
VOUT TRACE – 1V/DIV
ⴚ40
ⴚ20
0
20
40
60
80
100
TIME – 4ns/DIV
TEMPERATURE – ⴗC
Figure 14. ISY– vs. Temperature
V+ = 5V
TA = 25ⴗC
VOLTAGE
0V
Figure 17. Response to a 50 MHz 100 mV Input Sine Wave
VOUT
0V
VIN
VIN TRACE – 10mV/DIV
VOUT TRACE – 1V/DIV
TIME – 2ns/DIV
Figure 15. Rising Edge Response
–6–
REV. 0
AD8611/AD8612
common-mode voltage range to the comparator. Note that signals much greater than 3.0 V will result in increased input
currents and may cause the comparator to operate more slowly.
Optimizing High-Speed Performance
As with any high-speed comparator or amplifier, proper design and
layout should be used to ensure optimal performance from the
AD8611/AD8612. Excess stray capacitance or improper grounding
can limit the maximum performance of high-speed circuitry.
Minimizing resistance from the source to the comparator’s input is
necessary to minimize the propagation delay of the circuit. Source
resistance, in combination with the equivalent input capacitance of
the AD8611/AD8612 creates an R-C filter that could cause a
lagged voltage rise at the input to the comparator. The input
capacitance of the AD8611/AD8612 in combination with stray
capacitance from an input pin to ground results in several picofarads of equivalent capacitance. Using a surface-mount package
and a minimum of input trace length, this capacitance is typically
around 3 pF to 5 pF. A combination of 3 kΩ source resistance
and 3 pF of input capacitance yields a time constant of 9 ns, which
is slower than the 4 ns propagation delay of the AD8611/AD8612.
Source impedances should be less than 1 kΩ for best performance.
Another important consideration is the proper use of power supply
bypass capacitors around the comparator. A 1 µF bypass capacitor
should be placed within 0.5 inches of the device between each
power supply pin and ground. Another 10 nF ceramic capacitor
should be placed as close as possible to the device in parallel with
the 1 µF bypass capacitor. The 1 µF capacitor will reduce any
potential voltage ripples from the power supply, and the 10 nF
capacitor acts as a charge reservoir for the comparator during
high-frequency switching.
The AD8611 is able to swing within 200 mV of ground and within
1.5 V of positive supply voltage. This is slightly more output voltage
swing than the LT1016. The AD8611 also uses less current than
the LT1016, 5 mA as compared to 25 mA of typical supply current.
The AD8611 has a typical propagation delay of 4 ns, compared to
the LT1394 and LT1016, whose propagation delays are typically
7 ns and 10 ns, respectively.
Maximum Input Frequency and Overdrive
The AD8611 can accurately compare input signals up to 100 MHz
with less than 10 mV of overdrive. The level of overdrive required
increases with ambient temperature, with up to 50 mV of overdrive
recommended for a 100 MHz input signal and an ambient temperature of +85°C.
It is not recommend to use an input signals with a fundamental
frequency above 100 MHz as the AD8611 could draw up to 20 mA
of supply current and the outputs may not settle to a definite
state. The device will return to its specified performance once
the fundamental input frequency returns to below 100 MHz.
A continuous ground plane on the PC board is also recommended
to maximize circuit performance. A ground plane can be created by
using a continuous conductive plane over the surface of the circuit
board, only allowing breaks in the plane for necessary traces and
vias. The ground plane provides a low inductive current return
path for the power supply, thus eliminating any potential differences at different ground points throughout the circuit board
caused from “ground bounce.” A proper ground plane will also
minimize the effects of stray capacitance on the circuit board.
Output Loading Considerations
The AD8611 can deliver up to 10 mA of output current without
increasing its propagation delay. The outputs of the device should
not be connected to more than 40 TTL input logic gates or drive
less than 400 Ω of load resistance.
The AD8611 output has a typical output swing between ground
and 1 V below the positive supply voltage. Decreasing the output
load resistance to ground will lower the maximum output voltage
due to the increase in output current. Table I shows the typical
output high voltage versus load resistance to ground.
Upgrading the LT1394 and LT1016
The AD8611 single comparator is pin-for-pin compatible with
the LT1394 and LT1016 and offers an improvement in propagation delay over both comparators. These devices can easily be
replaced with the higher performance AD8611, but there are differences and it is useful to check that these ensure proper operation.
Table I. Maximum Output Voltage vs. Resistive Load
The five major differences between the AD8611 and the LT1016
include input voltage range, input bias currents, propagation delay,
output voltage swing, and power consumption. Input commonmode voltage is found by taking the average of the two voltages
at the inputs to the comparator. The LT1016 has an input voltage
range from 1.25 V above the negative supply to 1.5 V below the
positive supply. The AD8611 input voltage range extends down to
the negative supply voltage to within 2 V of V+. If the input
common-mode voltage could be exceeded, input signals should
be shifted or attenuated to bring them into range, keeping in
mind the note about source resistance in Optimizing High-Speed
Performance.
Output Load
to Ground
V+ ⴚ VOUT, HI
(typ)
300 Ω
500 Ω
1 kΩ
10 kΩ
> 20 kΩ
1.5 V
1.3 V
1.2 V
1.1 V
1.0 V
Connecting a 500 Ω–2 kΩ pull-up resistor to V+ on the output
will help increase the output voltage closer to the positive rail;
in this configuration, however, the output voltage will not reach
its maximum until at least 20 ns to 50 ns after the output voltage
switches. This is due to the R-C time constant between the pull-up
resistor and the output and load capacitances. The output pull-up
resistor will not improve propagation delay.
Example: An AD8611 power from a 5 V single supply has its
noninverting input connected to 1 V peak-to-peak high-frequency
signal centered around 2.3 V and its inverting input connected to a
fixed 2.5 V reference voltage. The worst-case input common-mode
voltage to the AD8611 is 2.65 V. This is well below the 3.0 V input
REV. 0
The input bias current to the AD8611 is 7 µA maximum over
temperature (–40°C to +85°C). This is identical to the maximum
input bias current for the LT1394, and half of the maximum IB for
the LT1016. Input bias currents to the AD8611 and LT1394 flow
out from the comparator’s inputs, as opposed to the LT1016
whose input bias current flows into its inputs. Using low value
resistors around the comparator and low impedance sources
will minimize any potential voltage shifts due to bias currents.
–7–
AD8611/AD8612
The AD8611 is stable with all values of capacitive load; however,
loading an output with greater than 30 pF will increase the propagation delay of that channel. Capacitive loads greater than 500 pF
will also create some ringing on the output wave. Table II shows
propagation delay versus several values of load capacitance. The
loading on one output of the AD8611 does not affect the propagation delay of the other output.
SIGNAL
VREF
␶PD Rising
␶PD Falling
< 10 pF
33 pF
100 pF
390 pF
680 pF
3.5 ns
5 ns
8 ns
14.5 ns
26 ns
3.5 ns
5 ns
7 ns
10 ns
15 ns
R2
CF
Figure 18. Configuring the AD8611/AD8612 with
Hysteresis
Table II. Propagation Delay vs. Capacitive Load
CL
R1
COMPARATOR
Here, the input signal is connected directly to the inverting input
of the comparator. The output is fed back to the noninverting
input through R1 and R2. The ratio of R1 to R1 + R2 establishes
the width of the hysteresis window with VREF setting the center of
the window, or the average switching voltage. The Q output will
switch low when the input voltage is greater than VHI, and will
not switch high again until the input voltage is less than VLO as
given in Equation 1:
VHI = ( V+ − 1.5 − VREF )
Using the Latch to Maintain a Constant Output
The latch input to the AD8611/AD8612 can be used to retain
data at the output of the comparator. When the latch voltage goes
high, the output voltage will remain in its previous state, independent of changes in the input voltage.
VLO = VREF ×
R1
+ VREF
R1 + R2
(1)
R2
R1 + R2
Where V+ is the positive supply voltage.
The setup time for the AD8611/AD8612 is 0.5 ns and the hold
time is 0.5 ns. Setup time is defined as the minimum amount of
time the input voltage must remain in a valid state before the
latch is activated for the latch to function properly. Hold time is
defined as the amount of time the input must remain constant
after the latch voltage goes high for the output to remain latched
its voltage.
The capacitor CF is optional and can be added to introduce a
pole into the feedback network. This has the effect of increasing
the amount of hysteresis at high frequencies, which is useful when
comparing relatively slow signals in high-frequency noise environments. At frequencies greater than fP, the hysteresis window
approaches VHI = V+ – 1.5 V and VLO = 0 V. For frequencies less
than ƒP, the threshold voltages remain as in Equation 1.
The latch input is TTL and CMOS compatible, so a logic high is
a minimum of 2.0 V and a logic low is a maximum of 0.8 V. The
latch circuitry in the AD8611/AD8612 has no built-in hysteresis.
Clock Timing Recovery
Comparators are often used in digital systems to recover clock
timing signals. High-speed square waves transmitted over a distance,
even tens of centimeters, can become distorted due to stray capacitance and inductance. Poor layout or improper termination can also
cause reflections on the transmission line, further distorting the
signal waveform. A high-speed comparator can be used to recover
the distorted waveform while maintaining a minimum of delay.
Input Stage and Bias Currents
The AD8611 and AD8612 use a bipolar PNP differential input
stage. This enables the input common-mode voltage range to extend
from within 2.0 V of the positive supply voltage to 200 mV below the
negative supply voltage. Therefore, using a single 5 V supply, the
input common-mode voltage range is –200 mV to +3.0 V. Input
common-mode voltage is the average of the voltages at the two
inputs. For proper operation, the input common-mode voltage
should be kept within the common-mode voltage range.
Figure 19 shows the AD8611 used to recover a 65 MHz, 100 mV
peak-to-peak distorted clock signal into a 4 V peak-to-peak square
wave. The lower trace is the input to the AD8611 and the upper
trace is the Q output from the comparator. The AD8611 is powered
from a 5 V single supply.
The input bias current for the AD8611/AD8612 is 4 µA, which
is the amount of current that flows from each input of the comparator. This bias current will go to zero on an input that is high
and will double on an input that is low, which is a characteristic
common to any bipolar comparator. Care should be taken in
choosing resistances to be connected around the comparator as
large resistors could cause significant voltage drops due to the
input bias current.
VOUT
2V/DIV
The input capacitance for the AD8611/AD8612 is typically 3 pF.
This is measured by inserting a 5 kΩ source resistance in series
with the input and measuring the change in propagation delay.
20mV/DIV
VIN
Using Hysteresis
Hysteresis can easily be added to a comparator through the addition of positive feedback. Adding hysteresis to a comparator offers
an advantage in noisy environments where it is not desirable for
the output to toggle between states when the input signal is close
to the switching threshold. Figure 18 shows a simple method for
configuring the AD8611 or AD8612 with hysteresis.
TIME – 10ns/DIV
Figure 19. Using the AD8611 to Recover a Noisy Clock Signal
–8–
REV. 0
AD8611/AD8612
A 5 V High-Speed Window Comparator
5V
5V
A window comparator circuit is used to detect when a signal is
between two fixed voltages. The AD8612 can be used to create
a high-speed window comparator, as shown in Figure 20. Here,
the reference window voltages are set as:
VHI
R2
=
R1 + R2
VLO
6
3
VIN < VLO
VLO < VIN < VHI
VIN > VHI
1k⍀
Q1
AD612
Q1, Q2 = 2N3960
5V
AD612
9
R3
R4
Q2
500⍀
VIN
VLO
A2
8
5
11
14
12
1k⍀
500⍀
PINS 2 AND 13 ARE NO CONNECTS
Figure 20. A High-Speed Window Comparator
Table III. Window Comparator Output States
= 200 mV
+5V
= 200 mV
1
A1
4
To ensure a minimum of switching delay, high-speed transistors
are recommended for Q1 and Q2. Using the AD8612 with
2N3960 transistors provides a total propagation delay from
VIN to VOUT of less than 10 ns.
Input Voltage
VOUT
10
7
R2
The output of the A1 comparator will go high when the input
signal exceeds VHI, and the output of A2 will go high only when
VIN drops below VLO. When the input voltage is between VHI and
VLO, both comparator outputs will be low, turning off both Q1 and
Q2, thus driving VOUT to a high state. If the input signal goes
outside of the reference voltage window, then VOUT will go low.
REV. 0
VHI
R4
=
R 3 + R4
VOUT
1k⍀
5V
R1
–9–
AD8611/AD8612
SPICE Model
* AD8611 SPICE Macro-Model Typical Values
* 1/2000, Ver. 1.0
* TAM / ADSC
*
* Node assignments
*
non-inverting input
*
|
inverting input
*
|
|
positive supply
*
|
|
|
negative supply
*
|
|
|
|
Latch
*
|
|
|
|
|
DGND
*
|
|
|
|
|
|
Q
*
|
|
|
|
|
|
|
QNOT
*
|
|
|
|
|
|
|
|
.SUBCKT AD8611
1
2
99
50
80
51
45
65
*
* INPUT STAGE
*
*
Q1
4
3 5 PIX
Q2
6
2 5 PIX
IBIAS 99
5 800E-6
RC1
4 50 1E3
RC2
6 50 1E3
CL1
4
6 3E-13
CIN
1
2 3E-12
VCM1
99
7 DC 1.9
D1
5
7 DX
EOS
3
1 POLY(1) (31,98) 1E-3 1
*
* Reference Voltages
*
EREF
98 0 POLY(2) (99,0) (50,0) 0 0.5 0.5
RREF
98 0 100E3
*
* CMRR=66dB, ZERO AT 1kHz
*
ECM1 30 98 POLY(2) (1,98) (2,98) 0 0.5 0.5
RCM1 30 31 10E3
RCM2 31 98 5
CCM1 30 31 15.9E-9
*
* Latch Section
*
–10–
REV. 0
AD8611/AD8612
RX 80 51 100E3
RB4 60 62 2000
E1 10 98 (4,6) 1
CB3 99 61 0.5E-12
S1 10 11 (80,51) SLATCH1
CB4 62 51 1E-12
R2 11 12 1
RO3 66 64 1
C3 12 98 5.4E-12
D5
E2 13 98 (12,98) 1
RO4 67 65 500
R3 12 13 500
EO3 63 51 (20,51) 1
*
EO4 97 60 (20,51) 1
* Power Supply Section
*
*
* MODELS
GSY1 99 52 POLY(1) (99,50) 4E-3 -2.6E-4
*
GSY2 52 50 POLY(1) (99,50) 3.7E-3 -.6E-3
.MODEL PIX PNP(BF=100,IS=1E-16)
RSY
.MODEL NOX NPN(BF=100,VAF=130,IS=1E-14)
52 51 10
64 65 DX
*
.MODEL DX D(IS=1E-14)
* Gain Stage Av=250 fp=100MHz
.MODEL SLATCH1 VSWITCH(ROFF=1E6,RON=500,
*
+VOFF=2.1,VON=1.4)
G2 98 20 (12,98) 0.25
.ENDS AD8611
R1 20 98 1000
C1 20 98 10E-13
E3 97
0 (99,0) 1
E4 52
0 (51,0) 1
V1 97 21 DC 0.8
V2 22 52 DC 0.8
D2 20 21 DX
D3 22 20 DX
*
* Q Output
*
Q3
99 41 46 NOX
Q4
47 42 51 NOX
RB1 43 41 2000
RB2 40 42 2000
CB1 99 41 0.5E-12
CB2 42 51 1E-12
RO1 46 44 1
D4
44 45 DX
RO2 47 45 500
EO1 97 43 (20,51) 1
EO2 40 51 (20,51) 1
*
* Q NOT Output
*
Q5
99 61 66 NOX
Q6
67 62 51 NOX
RB3 63 61 2000
REV. 0
–11–
AD8611/AD8612
OUTLINE DIMENSIONS
Dimensions shown in inches and (mm).
8-Lead micro SO
(RM-8)
0.1968 (5.00)
0.1890 (4.80)
0.122 (3.10)
0.114 (2.90)
8
8
5
0.1574 (4.00)
0.1497 (3.80) 1
0.199 (5.05)
0.187 (4.75)
0.122 (3.10)
0.114 (2.90)
1
5
4
0.2440 (6.20)
0.2284 (5.80)
4
PIN 1
0.0098 (0.25)
0.0040 (0.10)
PIN 1
0.0256 (0.65) BSC
0.120 (3.05)
0.112 (2.84)
0.011 (0.28)
0.003 (0.08)
33ⴗ
27ⴗ
0.0500 0.0192 (0.49)
SEATING (1.27)
0.0098 (0.25)
PLANE BSC 0.0138 (0.35) 0.0075 (0.19)
0.0196 (0.50)
x 45°
0.0099 (0.25)
8°
0° 0.0500 (1.27)
0.0160 (0.41)
0.028 (0.71)
0.016 (0.41)
14-Lead Thin Shrink Small Outline
(RU-14)
0.201 (5.10)
0.193 (4.90)
14
8
1
7
0.256 (6.50)
0.246 (6.25)
PIN 1
0.006 (0.15)
0.002 (0.05)
SEATING
PLANE
0.0433
(1.10)
MAX
0.0256
(0.65)
BSC
0.0118 (0.30)
0.0075 (0.19)
0.0079 (0.20)
0.0035 (0.090)
8ⴗ
0ⴗ
0.028 (0.70)
0.020 (0.50)
PRINTED IN U.S.A.
0.018 (0.46)
SEATING 0.008 (0.20)
PLANE
0.043 (1.09)
0.037 (0.94)
0.177 (4.50)
0.169 (4.30)
0.006 (0.15)
0.002 (0.05)
0.120 (3.05)
0.112 (2.84)
0.0688 (1.75)
0.0532 (1.35)
C3862–2.5–4/00 (rev. 0) 01541
8-Lead Small Outline IC
(SO-8)
–12–
REV. 0
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