TI1 LMH6515 Lmh6515 600 mhz, digital controlled, variable gain amplifier Datasheet

LMH6515
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LMH6515 600 MHz, Digital Controlled, Variable Gain Amplifier
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FEATURES
DESCRIPTION
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The LMH6515 is a high performance, digitally
controlled variable gain amplifier (DVGA). It combines
precision gain control with a low noise, ultra-linear,
differential amplifier. Typically, the LMH6515 drives a
high performance ADC in a broad range of mixed
signal and digital communication applications such as
mobile radio and cellular base stations where
automatic gain control (AGC) is required to increase
system dynamic range. When used in conjunction
with a high speed ADC, system dynamic range can
be extended by up to 32 dB.
1
2
Adjustable Gain with a 31 dB Range
Precise 1 dB Gain Steps
Parallel 5-bit Gain Control
On Chip Register Stores Gain Setting
Fully Differential Signal Path
Single Ended to Differential Capable
200Ω Input Impedance
Small Footprint (4 mm x 4 mm) WQFN Package
APPLICATIONS
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Cellular Base Stations
IF Sampling Receivers
Instrumentation
Modems
Imaging
Differential Line Receiver
KEY SPECIFICATIONS
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600 MHz bandwidth @ 100Ω load
40 dBm OIP3 @ 75 MHz, 200Ω load
20 dB to 30 dB maximum gain
Selectable output impedance of 200Ω or 400Ω
8.3 dB noise figure
5 ns gain step switching time
100 mA supply current
The LMH6515 has a differential input and output
allowing large signal swings on a single 5V supply. It
is designed to accept signals from RF elements and
maintain a terminated impedance environment. The
input impedance is 200Ω resistive. The output
impedance is either 200Ω or 400Ω and is user
selectable. A unique internal architecture allows use
with both single ended and differential input signals.
Input signals to the LMH6515 are scaled by a highly
linear, digitally controlled attenuator with 31 accurate
1 dB steps. The attenuator output provides the input
signal for a high gain, ultra linear differential
transconductor. The transconductor differential output
current can be converted into a voltage by using the
on-chip 200Ω or 400Ω loads. The transconductance
gain is 0.1 Amp/Volt resulting in a maximum voltage
gain of +26 dB when driving a 200Ω load, or 32 dB
when driving the 400Ω load. On chip digital latches
are provided for local storage of the gain setting. The
gain step settling time is 5 ns and care has been
taken to reduce the sensitivity of bandwidth and
phase to gain setting.
The LMH6515 operates over the industrial
temperature range of −40°C to +85°C. The LMH6515
is available in a 16-Pin, thermally enhanced, WQFN
package.
1
2
Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of
Texas Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet.
All trademarks are the property of their respective owners.
PRODUCTION DATA information is current as of publication date.
Products conform to specifications per the terms of the Texas
Instruments standard warranty. Production processing does not
necessarily include testing of all parameters.
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Typical Application
VCC
LO
RLOAD
RF
ROUT
200
LMH6515
ADC
5
GAIN 1-5
LATCH
These devices have limited built-in ESD protection. The leads should be shorted together or the device placed in conductive foam
during storage or handling to prevent electrostatic damage to the MOS gates.
ABSOLUTE MAXIMUM RATINGS (1) (2)
ESD Tolerance (3)
Human Body Model
Machine Model
2 kV
150V
Positive Supply Voltage (Pin 3)
−0.6V to 5.5V
Output Voltage (pin 14,15)
−0.6V to 6.8V
Differential Voltage Between Any Two Grounds
<200 mV
Analog Input Voltage Range
−0.6V to VCC
Digital Input Voltage Range
−0.6V to 3.6V
Output Short Circuit Duration (one pin to ground)
Infinite
Junction Temperature
+150°C
−65°C to +150°C
Storage Temperature Range
Soldering Information
(1)
(2)
(3)
Infrared or Convection (20 sec)
235°C
Wave Soldering (10 sec)
260°C
Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for
which the device is intended to be functional, but specific performance is not ensured. For ensured specifications, see the Electrical
Characteristics tables.
If Military/Aerospace specified devices are required, please contact the TI Sales Office/ Distributors for availability and specifications.
Human Body Model, applicable std. MIL-STD-883, Method 3015.7. Machine Model, applicable std. JESD22-A115-A (ESD MM std. of
JEDEC)Field-Induced Charge-Device Model, applicable std. JESD22-C101-C (ESD FICDM std. of JEDEC).
OPERATING RATINGS (1)
Supply Voltage (Pin 3)
4V to 5.25V
Output Voltage Range (Pin 14, 15)
1.4V to 6.4V
Differential Voltage Between Any Two Grounds
<10 mV
Analog Input Voltage Range, AC Coupled
±1.4V
Temperature Range (2)
−40°C to +85°C
Package Thermal Resistance (θJA) 16-Pin WQFN
(1)
(2)
2
47°C/W
Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for
which the device is intended to be functional, but specific performance is not ensured. For ensured specifications, see the Electrical
Characteristics tables.
The maximum power dissipation is a function of TJ(MAX), θJA. The maximum allowable power dissipation at any ambient temperature is
PD = (TJ(MAX) – TA)/ θJA. All numbers apply for packages soldered directly onto a PC Board.
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5V ELECTRICAL CHARACTERISTICS (1)
The following specifications apply for single supply with VCC = 5V, Maximum Gain , RL = 100Ω (200Ω external || 200Ω
internal), VOUT = 2 VPP, fin = 150 MHz. Boldface limits apply at temperature extremes.
Symbol
Parameter
Conditions
Min (2)
Typ (3)
Max (2)
Units
Dynamic Performance
SSBW
−3 dB Bandwidth
Average of all Gain Settings
600
MHz
Noise and Distortion
−76
Third Order Intermodulation Products f = 75 MHz, VOUT = 2 VPP
OIP3
P1 dB
Output 3rd Order Intercept Point
Output Level for 1 dB Gain
Compression
f = 150 MHz, VOUT = 2 VPP
−72
f = 250 MHz, VOUT = 2 VPP
−66
f = 450 MHz, VOUT = 2 VPP
−58
f = 75 MHz, VOUT = 2 VPP,
Tone Spacing = 0.5 MHz
39
f = 150 MHz, VOUT = 2 VPP,
Tone Spacing = 2 MHz
37
f = 250 MHz, VOUT = 2 VPP,
Tone Spacing = 2 MHz
34
f = 75 MHz, RL = 200Ω, VOUT = 2 VPP,
Tone Spacing = 0.5 MHz
40
f = 150 MHz, RL = 200Ω, VOUT= 2 VPP,
Tone Spacing = 2 MHz
37
f = 250 MHz, RL = 200Ω, VOUT = 2 VPP,
Tone Spacing = 2 MHz
34
f = 75 MHz, RL = 200Ω
16.7
f = 250 MHz, RL = 200Ω
14.7
f = 75 MHz
14.5
dBc
dBm
dBm
f = 450 MHz
13.2
VNI
Input Noise Voltage
Maximum Gain, f = 40 MHz
1.8
nV/√Hz
VNO
Output Noise Voltage
Maximum Gain, f = 40 MHz
18
nV/√Hz
NF
Noise Figure
Maximum Gain
8.3
dB
Analog I/O
Differential Input Resistance
165
160
186
210
220
Ω
Input Common Mode Resistance
825
785
971
1120
1160
Ω
Differential Output Impedance
(1)
(2)
(3)
Low Gain Option
187
Ω
High Gain Option
330
325
370
410
415
Internal Load Resistors
Between Pins 13, 14 and Pins 15, 16
165
160
187
210
235
Input Signal Level (AC Coupled)
Max Gain, VO = 2 VPP, RL = 1 kΩ
126
Maximum Differential Input Signal
AC Coupled
5.6
Input Common Mode Voltage
Self Biased
Input Common Mode Voltage Range
Driven Externally
0.9 to 2.0
V
Minimum Input Voltage
DC
0
V
Maximum Input Voltage
DC
3.3
V
1.3
1.1
1.4
Ω
mVPP
VPP
1.5
1.7
V
Electrical Table values apply only for factory testing conditions at the temperature indicated. No specified parametric performance is
indicated in the electrical tables under conditions different than those tested
Limits are 100% production tested at 25°C. Limits over the operating temperature range are specified through correlation using
Statistical Quality Control (SQC) methods.
Typical values represent the most likely parametric norm as determined at the time of characterization. Actual typical values may vary
over time and will also depend on the application and configuration. The typical values are not tested and are not specified on shipped
production material.
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5V ELECTRICAL CHARACTERISTICS(1) (continued)
The following specifications apply for single supply with VCC = 5V, Maximum Gain , RL = 100Ω (200Ω external || 200Ω
internal), VOUT = 2 VPP, fin = 150 MHz. Boldface limits apply at temperature extremes.
Symbol
Parameter
Conditions
Min (2)
Typ (3)
Max (2)
Units
Maximum Differential Output Voltage VCC = 5V, Output Common Mode = 5V
Swing
5.5
VPP
VOS
Output Offset Voltage
30
mV
CMRR
Common Mode Rejection Ratio
85
dB
PSRR
Power Supply Rejection Ratio
All Gain Settings
63
61
83
dB
Gain Parameters
Maximum Gain
DC, Internal RL = 200Ω,
External RL = 1280Ω
23.9
23.4
24.2
24.6
24.8
dB
Minimum Gain
DC, Internal RL = 200Ω,
External RL = 1280Ω
−7.2
−7.7
−6.9
−6.5
−6.4
dB
Gain Step Size
DC
1.0
Gain Step Error
DC
0.02
f = 150 MHz
0.07
Cumulative Gain Step Error
DC, Gain Step 31 to Gain Step 0
−0.1
−0.2
Gain Step Switching Time
0.05
dB
dB
0.3
0.4
dB
5
ns
3.3
V
Digital Inputs/Timing
Logic Compatibility
CMOS Logic
VIL
Logic Input Low Voltage
VIH
Logic Input High Voltage
0.8
V
IIH
Logic Input High Input Current (4)
32
40
μA
TSU
Setup Time
3
ns
THOLD
Hold Time
3
ns
TPW
Minimum Latch Pulse Width
10
ns
2.0
V
Power Requirements
ICC
(4)
4
Total Supply Current
VOUT = 0V Differential, VOUT Common
Mode = 5V
107
124
134
mA
Amplifier Supply Current
Pin 3 Only
56
66
74
mA
Output Stage Bias Currents
Pins 13, 14 and Pins 15, 16;
VOUT Common Mode = 5 V
48
58
60
mA
Negative input current implies current flowing out of the device.
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NC
VCC
LATCH
GAIN_0
4
3
2
1
CONNECTION DIAGRAM
GND
5
16
LOAD-
IN+
6
15
OUT-
IN-
7
14
OUT+
GND
8
13
LOAD+
9
10
11
12
GAIN_4
GAIN_3
GAIN_2
GAIN_1
GND
Figure 1. 16-Pin WQFN (Top View)
Gain Control Pins
Pin Number
Pin Name
Gain Step Size
1
GAIN_0
1 dB
12
GAIN_1
2 dB
11
GAIN_2
4 dB
10
GAIN_3
8 dB
9
GAIN_4
16 dB
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PIN DESCRIPTIONS
Pin Number
Symbol
Description
6
IN+
Non-inverting analog input. Internally biased to 1.4V. Input voltage should not exceed VCC or
go below GND by more than 0.5V.
7
IN−
Inverting analog input. Internally biased to 1.4V. Input voltage should not exceed VCC or go
below GND by more than 0.5V. If using amplifier single ended this input should be capacitively
coupled to ground.
15
OUT−
Open collector inverting output. This pin is an output that also requires a power source. This
pin should be connected to 5V through either an RF choke or an appropriately sized inductor
that can form part of a filter. See APPLICATION INFORMATION section for details.
14
OUT+
Open collector non-inverting output. This pin is an output that also requires a power source.
This pin should be connected to 5V through either an RF choke or an appropriately sized
inductor that can form part of a filter. See APPLICATION INFORMATION section for details.
16
LOAD−
Internal 200Ω resistor connection to pin 15. This pin can be left floating for higher gain or
shorted to pin 13 for lower gain and lower effective output impedance. See APPLICATION
INFORMATION section for details.
13
LOAD+
Internal 200Ω resistor connection to pin 14. This pin can be left floating for higher gain or
shorted to pin 16 for lower gain and lower effective output impedance. See APPLICATION
INFORMATION section for details.
3
VCC
5V power supply pin. Use ceramic, low ESR bypass capacitors. This pin powers everything
except the output stage.
5,8
GND
Ground pins. Connect to low impedance ground plane. All pin voltages are specified with
respect to the voltage on these pins. The exposed thermal pad is also a ground connection.
Analog I/O
Power
6
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PIN DESCRIPTIONS (continued)
Pin Number
Symbol
Description
1,12,11,
10,9
GAIN_0 to
GAIN_4
Gain setting pins. See above table for gain step sizes for each pin. These pins are 3.3V CMOS
logic compatible. 5V inputs may cause damage.
2
LATCH
This pin controls the function of the gain setting pins mentioned above. With LATCH in the
logic HIGH state the gain is fixed and will not change. With the LATCH in the logic LOW state
the gain is set by the state of the gain control pins. Any changes in gain made with the LATCH
pin in the LOW state will take effect immediately. This pin is 3.3V CMOS logic compatible. 5V
inputs may cause damage.
4
NC
This pin is not connected. It can be grounded or left floating.
Digital Inputs
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TYPICAL PERFORMANCE CHARACTERISTICS
VCC = 5V
Frequency Response with Capacitive Load
22
14
19
11
8
5
16
GAIN (dB)
GAIN (dB)
Frequency Response All Gain Settings
20
17
2
-1
-4
13
CL = 1.8 pF
10
CL = 4.7 pF
7
-7
-10
-13
-16
CL = 0 pF
CL = 10 pF
4
1
LOAD = 100: || CL
RL = 100:
-19
10
100
-2
10
1000
100
FREQUENCY (MHz)
Figure 2.
Figure 3.
Frequency Response Over Temperature, Maximum Gain
Frequency Response Over Temperature, Minimum Gain
20
-11
-40°C
-40°C
19
-12
85°C
25°C
GAIN (dB)
GAIN (dB)
25°C
18
17
16
15
-14
-15
1
10
100
-16
1000
1
10
100
FREQUENCY (MHz)
FREQUENCY (MHz)
Figure 4.
Figure 5.
OIP3 High Gain Mode
1000
OIP3 Low Gain Mode
45
RL = 200:
43
VOUT = 2 VPP
41
41
39
39
37
35
33
31
f = 150 MHz
29
RL = 100:
43
f = 75 MHz
OIP3 (dBm)
OIP3 (dBm)
85°C
-13
45
VOUT = 2 VPP
f = 75 MHz
37
35
33
31
f = 250 MHz
f = 150 MHz
29
27
f = 250 MHz
27
INPUT CLIPPING
INPUT CLIPPING
25
25
0
3
6
9
12 15 18 21 24 27 30
GAIN STEP (0 = MAX GAIN)
0
3
6
9
12 15 18 21 24 27 30
GAIN STEP (0 = MAX GAIN)
Figure 6.
8
1000
FREQUENCY (MHz)
Figure 7.
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TYPICAL PERFORMANCE CHARACTERISTICS
VCC = 5V (continued)
OIP3 Over Temperature
OIP3 High Gain Mode
45
45
f = 150 MHz
43
75 MHz
40
RL = 200:
41
35
250 MHz
30
OIP3 (dBm)
OIP3 (dBm)
39
150 MHz
INPUT CLIPPING
VOUT = 1 VPP
37
35
33
VOUT = 2 VPP
31
29
25
VOUT = 2.8 VPP
27
RL = 200:
25
20
-40
-20
0
20
40
60
0
80
3
6
9
12 15 18 21 24 27 30
GAIN STEP (0 = MAX GAIN)
TEMPERATURE (°C)
Figure 8.
Figure 9.
IMD3 Low Gain Mode
IMD3 High Gain Mode
-40
-50
RL = 100:
-45
RL = 200:
-55
VOUT = 2 VPP
-50
VOUT = 2 VPP
-55
f = 250 MHz
f = 150 MHz
-60
-65
f = 250 MHz
-65
IMD (dBc)
IMD (dBc)
INPUT CLIPPING
f = 150 MHz
-70
-75
-70
-80
-75
-85
f = 75 MHz
-80
0
3
6
9
f = 75 MHz
-90
12 15 18 21 24 27 30
0
GAIN STEP (0 = MAX GAIN)
3
Figure 11.
IMD3 High Gain Mode
-20
12 15 18 21 24 27 30
9
6
GAIN STEP (0 = MAX GAIN)
Figure 10.
HD2 vs. Frequency
-30
f = 150 MHz
RL = 100:
-40
-50
INPUT CLIPPING
-60
2.8 VPP
-70
DISTORTION (dBc)
-30 RL = 200:
IMD3 (dBc)
INPUT CLIPPING
-60
-40
-50
2.8 VPP
-60
2 VPP
-70
-80
2 VPP
1 VPP
-80
-90
1 VPP
-100
0
3
6
9
12 15 18 21 24 27 30
-90
GAIN STEP (0 = MAX GAIN)
0
50 100 150 200 250 300 350 400 450
FREQUENCY (MHz)
Figure 12.
Figure 13.
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TYPICAL PERFORMANCE CHARACTERISTICS
VCC = 5V (continued)
HD3 vs. Frequency
HD2 vs. Frequency
-30
-30
RL = 200:
-40
-40
2.8 VPP
-50
DISTORTION (dBc)
DISTORTION (dBc)
RL = 100:
-60
2 VPP
-70
-80
-50
2.8 VPP
-60
2 VPP
-70
-80
1 VPP
-90
1 VPP
-90
-100
0
50 100 150 200 250 300 350 400 450
0
FREQUENCY (MHz)
50 100 150 200 250 300 350 400 450
FREQUENCY (MHz)
Figure 14.
Figure 15.
HD3 vs. Frequency
Noise Figure for All Gain Settings
-30
40
RL = 200:
35
2.8 VPP
-50
-60
NOISE FIGURE (dB)
DISTORTION (dBc)
-40
2 VPP
-70
-80
1 VPP
-90
25
20
70 MHz
15
10
-100
5
0
150 MHz
30
50 100 150 200 250 300 350 400 450
0
10
20
30
GAIN STEP (0 = MAXIMUM GAIN)
FREQUENCY (MHz)
Figure 16.
Figure 17.
Noise Figure vs. Frequency
Differential Output Noise
60
13
f = 40 MHz
OUTPUT NOISE (nV/ Hz)
NOISE FIGURE (dB)
12
11
10
9
50
RL = 200:
40
30
20
10
RL = 100:
8
0
0
100
200
300
400
500
600
FREQUENCY (MHz)
10
20
30
GAIN SETTING (0 = MAXIMUM GAIN)
Figure 18.
10
0
Figure 19.
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TYPICAL PERFORMANCE CHARACTERISTICS
VCC = 5V (continued)
19.8
19.6
25.6
LOW GAIN MODE, RL = 100:
25.4
19.4
19.2
25.2
19
HIGH GAIN MODE, RL = 200:
24.8
18.8
24.6
18.6
24.4
18.4
24.2 PIN = -24 dBm
f = 75 MHz
24
3.5
4
18.2
4.5
36
INTERNAL LOAD
= 400:
28
24
INTERNAL LOAD =
200:
20
16
200: INTERNAL WITH 200:
EXTERNAL = 20 dB NET
12
10
18
5.5
5
400: INTERNAL WITH 400:
EXTERNAL = 26 dB NET
32
MAXIMUM GAIN (dB)
25.8
25
Gain vs. External Load
20
MAXIMUM GAIN, LOW GAIN MODE (dB)
MAXIMUM GAIN, HIGH GAIN MODE (dB)
Maximum Gain vs. Supply Voltage
26
10k
100k
Figure 20.
Figure 21.
Maximum Gain Over Temperature
Worst Case Gain Step Error vs. Frequency
0.5
19.5
RL = 100:
f = 70 MHz
0.45
GAIN STEP ERROR (dB)
19
f = 150 MHz
18.5
f = 250 MHz
18
f = 450 MHz
17.5
RL = 100:
17
0
-50 -25
0.4
0.35
0.3
0.25
0.2
0.15
0.1
0.05
0
25
50
75
100
125
0
100
200
300
400
500
FREQUENCY (MHz)
TEMPERATURE (°C)
Figure 22.
Figure 23.
Worst Case Gain Step Error vs. Frequency
Worst Case Gain Step Error Over Temperature
0.4
1.6
RL = 200:
RL = 100:
1.4
0.35
1.2
0.3
1
0.25
ERROR (dB)
GAIN STEP ERROR (dB)
1k
EXTERNAL DIFFERENTIAL LOAD (:)
SUPPLY VOLTAGE (V)
MAXIMUM GAIN (dB)
100
0.8
0.6
85°C
0.2
0.15
0.4
0.1
0.2
0.05
25°C
-40°C
0
0
0
100
200
300
400
500
0
50
100
150
200
250
300
FREQUENCY (MHz)
FREQUENCY (MHz)
Figure 24.
Figure 25.
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TYPICAL PERFORMANCE CHARACTERISTICS
VCC = 5V (continued)
Digital Crosstalk
Digital Crosstalk
40
40
10
0
-10
3
-20
-30
30
20
10
0
-10
3
-20
-30
PINS 9, 10, 11,12
-40
PINS 9, 10, 11,12
-40
0
10 20 30 40 50 60 70 80 90 100
0
0
0
10 20 30 40 50 60 70 80 90 100
TIME (ns)
TIME (ns)
Figure 26.
Figure 27.
Digital Pin to Output Isolation
Minimum Gain to Maximum Gain Switching
Using Latch Pin
3
-30
PIN = -10 dBm
LOAD = 200:
-40 MAX GAIN
LATCH
2
1
0
LATCH
-60
LATCH (V)
-50
VOUT (V)
CROSSTALK (dBc)
GAIN CONTROL SIGNALS (V)
DIFFERENTIAL OUTPUT (mV)
20
DIFFERENTIAL OUTPUT (mV)
LATCH = 3.3V
GAIN CONTROL SIGNALS (V)
LATCH = 0
30
0.6
0.3
VOUT
-70
0
-80
-0.3
GAIN 1
-0.6
-90
10
100
0
1000
10 20 30 40 50 60 70 80 90 100
TIME (ns)
FREQUENCY (MHz)
Figure 28.
Figure 29.
Maximum Gain to Minimum Gain Switching
Using Latch Pin
LATCH
16 dB Gain Step Using Latch Pin
3
3
2
2
1
LATCH
0.3
VOUT (V)
0
LATCH (V)
VOUT (V)
0
0.6
0.6
0.3
VOUT
VOUT
0
0
-0.3
-0.3
-0.6
-0.6
0
12
1
LATCH (V)
1
10 20 30 40 50 60 70 80 90 100
0
10 20 30 40 50 60 70 80 90 100
TIME (ns)
TIME (ns)
Figure 30.
Figure 31.
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TYPICAL PERFORMANCE CHARACTERISTICS
VCC = 5V (continued)
3
3
2
2
GAIN BIT 3
0.3
VOUT
0
1
0
VOUT (V)
0
0.6
GAIN PIN VIN (V)
1
GAIN BIT 4
0.6
VOUT
0.3
0
-0.3
-0.3
-0.6
-0.6
10 20 30 40 50 60 70 80 90 100
0
10 20 30 40 50 60 70 80 90 100
TIME (ns)
TIME (ns)
Figure 32.
Figure 33.
4 dB Gain Step Using Latch Pin
Power On Timing, Maximum Gain
3
0.4
V
2
1
LATCH
6
+
0.3
5
0.2
4
VOUT
0.3
VOUT (V)
0.6
LATCH (V)
VOUT (V)
0
0
-0.3
VOUT
0
2
-0.1
1
-0.2
0
-0.3 f = 250 MHz
ENVELOPE DISPLAYED
-0.4
0
5
10 15
-10 -5
-0.6
0
10 20 30 40 50 60 70 80 90 100
TIME (Ps)
Figure 34.
Figure 35.
5
0.3
0.2
4
0.2
VOUT (V)
3
0.1
VOUT
0
2
-0.1
1
-0.2
0
VOUT (V)
0.3
POWER SUPPLY (V)
0.4
+
25
30
Power Off Timing, Maximum Gain
6
V
20
TIME (ns)
Power On Timing, Minimum Gain
0.4
3
0.1
POWER SUPPLY (V)
0
6
f = 250 MHz
ENVELOPE DISPLAYED 5
4
VOUT
0.1
3
0
2
-0.1
1
0
-0.2
POWER SUPPLY (V)
VOUT (V)
8 dB Gain Step with Latch Pin Low
Switching Gain Pin 3
GAIN PIN VIN (V)
16 dB Gain Step with Latch Pin Low
Switching Gain Pin 4
+
-0.3 f = 250 MHz
ENVELOPE DISPLAYED
-0.4
0
5
10 15
-10 -5
V
-0.3
20
25
30
-0.4
-10
-5
0
5
10
15
TIME (Ps)
TIME (Ps)
Figure 36.
Figure 37.
20
25
30
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TYPICAL PERFORMANCE CHARACTERISTICS
VCC = 5V (continued)
Power Off Timing, Minimum Gain
0.3
4
VOUT (V)
0.2
VOUT
0.1
3
0
2
-0.1
1
0
-0.2
+
-0.3
-0.4
-10
POWER SUPPLY (V)
6
f = 250 MHz
ENVELOPE DISPLAYED 5
0.4
V
-5
0
5
10
15
20
25
30
TIME (Ps)
Figure 38.
14
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APPLICATION INFORMATION
The LMH6515 is a fully differential amplifier optimized for signal path applications up to 400 MHz. The LMH6515
has a 200Ω input. The absolute gain is load dependent, however the gain steps are always 1 dB. The LMH6515
output stage is a class A amplifier. This class A operation results in excellent distortion and linearity
characteristics. This makes the LMH6515 ideal for voltage amplification and an ideal ADC driver where high
linearity is necessary.
VCC
VCC
44.3 nH
200
200
LMH6515
VCM = VCC
10 pF
ADC
5
GAIN 1-5
LATCH
Figure 39. LMH6515 Typical Application
The LMH6515 output common mode should be set carefully. Using inductors to set the output common mode is
one preferred method and will give maximum output swing. AC coupling of the output is recommended. The
inductors mentioned above will shift the idling output common mode to the positive supply. Also, with the
inductors, the output voltage can exceed the supply voltage. Other options for setting the output common mode
require supply voltages above 5V. If using a supply higher than 5V care should be taken to make sure the output
common mode does not exceed the 5.25V supply rating.
It is also important to note the maximum voltage limits for the OUT+ and OUT− pins, which is 6.4V. When using
inductors these pins will experience voltage swings beyond the supply voltage. With a 5V output common mode
operating point this makes the effective maximum swing 5.6 VPP differential. System calibration and automatic
gain control algorithms should be tailored to avoid exceeding this limit.
In order to help with system design TI offers the ADC14V155KDRB High IF Receiver reference design board.
This board combines the LMH6515 DVGA with the ADC14V155 ADC and provides a ready made solution for
many IF receiver applications. Using an IF frequency of 169 MHz it achieves a small signal SNR of 72 dBFS and
an SFDR of greater than 90 DBFS. Large signal measurements show an SNR of 68 dBFS and an SFDR of 77
dBFS. The High IF Receiver board also features the LMK03000 low-jitter precision clock conditioner.
16
OUT-
13
200:
200:
OUT+
0 to -31 dB
6
14
15
400:
VARIABLE
ATTENUATOR
200:
7
+32 dB
+IN
+
-
-IN
5, 8
Figure 40. LMH6515 Block Diagram
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INPUT CHARACTERISTICS
The LMH6515 input impedance is set by internal resistors to a nominal 200Ω. Process variations will result in a
range of values as shown in the 5V Electrical Characteristics table. At higher frequencies parasitics will start to
impact the impedance. This characteristic will also depend on board layout and should be verified on the
customer’s system board.
At maximum gain the digital attenuator is set to 0 dB and the input signal will be much smaller than the output. At
minimum gain the output is 12 dB or more smaller than the input. In this configuration the input signal size may
limit the amplifier output amplitude, depending on the output configuration and the desired output signal voltage.
The input signal cannot swing more than 0.5V below the negative supply voltage (normally 0V) nor should it
exceed the positive supply voltage. The input signal will clip and cause severe distortion if it is too large. Because
the input stage self biases to approximately 1.4V the lower supply voltage will impose the limit for input voltage
swing. To drive larger input signals the input common mode can be forced higher than 1.4V to allow for more
swing. An input common mode of 2.0V will allow an 8 VPP maximum input signal. The trade off for input signal
swing is that as the input common mode is shifted away from the 1.4V internal bias point the distortion
performance will suffer slightly.
5V
INTERNAL BIAS = 1.4V
R1
C2
200
RIN = R1 || 200
LMH6515
C1
Vin
5
GAIN 1-5
LATCH
(Note capacitor on grounded input)
Figure 41. Single Ended Input
OUTPUT CHARACTERISTICS
The LMH6515 has the option of two different output configurations. The LMH6515 is an open collector topology.
As shown in Figure 46 each output has an on chip 200Ω pull up resistor. In addition there is an internal 400Ω
resistor between the two outputs. This results in a 200Ω or a 400Ω differential load in parallel with the external
load. The 400Ω option is the high gain option and the 200Ω provides for less gain. The 200Ω configuration is
recommended unless more gain is required.
The output common mode of the LMH6515 must be set by external components. Most applications will benefit
from the use of inductors on the output stage. In particular, the 400Ω option, as shown in Figure 47, will require
inductors in order to be able to develop an output voltage. The 200Ω option as shown in Figure 48 or Figure 49
will also require inductors since the voltage drop due to the on chip 200Ω resistors will saturate the output
transistors. It is also possible to use resistors and high voltage power supplies to set the output common mode.
This operation is not recommended, unless it is necessary to DC couple the output. If DC coupling is required the
input common mode and output common mode voltages must be taken into account.
Maximum bandwidth with the LMH6515 is achieved by using the low gain, low impedance output option and
using a low load resistance. With an effective load of 67Ω a bandwidth of nearly 1 GHz can be realized. As the
effective resistance on the output stage goes up the capacitance of the board traces and amplifier output stage
limit bandwidth in a roughly linear fashion. At an output impedance of 100Ω the bandwidth is down to 600 MHz,
and at 200Ω the bandwidth is 260 MHz. For this reason driving very high impedance loads is not recommended.
Although bandwidth goes down with higher values of load resistance, the distortion performance improves and
gain increases. The LMH6515 has a common emitter Class A output stage and minimizing the amount of current
swing in the output devices improves distortion substantially.
16
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The LMH6515 output stage is powered through the collectors of the output transistors. Power for the output
stage is fed through inductors and the reactance of the inductors allows the output voltage to develop. In
Figure 39 the inductors are shown with a value of 44.4 nH. The value of the inductors used will be different for
different applications. In Figure 39 the inductors have been chosen to resonate with the ADC and the load
capacitor to provide a weak band pass filter effect. For broad band applications higher value inductors will allow
for better low frequency operation. However, large valued inductors will reduce high frequency performance,
particularly inductors of small physical sizes like 0603 or smaller. Larger inductors will tend to perform better than
smaller ones of the same value even for narrow band applications. This is because the larger inductors will have
a lower DC resistance and less inter-winding capacitance and hence a higher Q and a higher self resonance
frequency. The self resonance frequency should be higher than any desired signal content by at least a factor of
two. Another consideration is that the power inductors and the filter inductors need to be placed on the circuit
board such that their magnetic fields do not cause coupling. Mutual coupling of inductors can compromise filter
characteristics and lead to unwanted distortion products.
1
RL = 100: TOTAL
0
NORMALIZED GAIN (dB)
1 PH
-1
-2
-3
470 nH
-4
-5
200 nH
-6
-7
-8
-9
1
10
100
1000
10000
FREQUENCY (MHz)
Figure 42. Bandwidth Changes Due to Different Inductor Values
36
MAXIMUM GAIN (dB)
32
400: INTERNAL WITH 400:
EXTERNAL = 26 dB NET
INTERNAL LOAD
= 400:
28
24
INTERNAL LOAD =
200:
20
16
12
10
200: INTERNAL WITH 200:
EXTERNAL = 20 dB NET
100
1k
10k
100k
EXTERNAL DIFFERENTIAL LOAD (:)
Figure 43. Gain vs. External Load
DIGITAL CONTROL
The LMH6515 has 32 gain settings covering a range of 31 dB. To avoid undesirable signal transients the
LMH6515 should be powered on at the minimum gain state (all logic input pins at 0V). The LMH6515 has a 5-bit
gain control bus as well as a latch pin. When the latch pin is low, data from the gain control pins is immediately
sent to the gain circuit (i.e. gain is changed immediately). When the latch pin transitions high the current gain
state is held and subsequent changes to the gain set pins are ignored. To minimize gain change glitches multiple
gain control pins should not change while the latch pin is low. In order to achieve the very fast gain step
switching time of 5 ns the internal gain change circuit is very fast. Gain glitches could result from timing skew
between the gain set bits. This is especially the case when a small gain change requires a change in state of
three or more gain control pins. If continuous gain control is desired the latch pin can be tied to ground. This
state is called transparent mode and the gain pins are always active. In this state the timing of the gain pin logic
transitions should be planned carefully to avoid undesirable transients.
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The LMH6515 was designed to interface with 3.3V CMOS logic circuits. If operation with 5V logic is required a
simple voltage divider at each logic pin will allow for this. To properly terminate 100Ω transmission lines a divider
with a 66.5Ω resistor to ground and a 33.2Ω series resistor will properly terminate the line as well as give the
3.3V logic levels. Care should be taken not to exceed the 3.6V absolute maximum voltage rating of the logic
pins.
EXPOSED PAD WQFN PACKAGE
The LMH6515 is in a thermally enhanced package. The exposed pad is connected to the GND pins. It is
recommended, but not necessary, that the exposed pad be connected to the supply ground plane. In any case,
the thermal dissipation of the device is largely dependent on the attachment of this pad. The exposed pad should
be attached to as much copper on the circuit board as possible, preferably external copper. However, it is also
very important to maintain good high speed layout practices when designing a system board. Please refer to the
LMH6515 evaluation board for suggested layout techniques.
Package information is available on the TI Web site.www.ti.com/packaging
INTERFACING TO ADC
The LMH6515 was designed to be used with high speed ADCs such as the ADC14155. As shown in the Typical
Application schematic, AC coupling provides the best flexibility especially for IF sub-sampling applications. Any
resistive networks on the output will also cause a gain loss because the output signal is developed across the
output resistors. The chart Maximum Gain vs. External Load shows the change in gain when an external load is
added.
The inputs of the LMH6515 will self bias to the optimum voltage for normal operation. The internal bias voltage
for the inputs is approximately 1.4V. In most applications the LMH6515 input will need to be AC coupled.
The output common mode voltage is not self biasing, it needs to be pulled up to the positive supply rail with
external inductors as shown in Figure 39. This gives the LMH6515 the capability for large signal swings with very
low distortion on a single 5V supply. The internal load resistors provide the LMH6515 with very consistent gain.
A unique internal architecture allows the LMH6515 to be driven by either a differential or single ended source. If
driving the LMH6515 single ended, the unused input should be terminated to ground with a 0.01 µF capacitor.
Directly shorting the unused input to ground will disrupt the internal bias circuitry and will result in poor
performance.
5V
680 nH
AMP ROUT
390 nH
3 pF
41 pF
27 nH
200:
ADC CIN
390 nH
3 pF
200
680 nH
5V
Figure 44. Bandpass Filter
Center Frequency is 140 MHz with a 20 MHz Bandwidth
Designed for 200Ω Impedance
18
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ADC Noise Filter
Figure 44 shows a filter schematic and the following table of values are for some common IF frequencies. The
filter shown offers a good compromise between bandwidth, noise rejection and cost. This filter topology is the
same as used on the ADC14V155KDRB High IF Receiver reference design board. This filter topology works best
with the 12 and 14-bit sub-sampling analog to digital converters shown in the Table 2 table.
Table 1. Filter Component Values
Filter Component Values
Components
Fc
75
MHz
140
MHz
170
MHz
250
MHz
BW
40
MHz
20
MHz
25
MHz
Narrow Band
10 µH
L1, L2
10 µH
10 µH
10 µH
L3, L4
390 nH
390 nH
560 nH
—
C1, C2
10 pF
3 pF
1.4 pF
47 pF
C3
22 pF
41 pF
32 pF
11 pF
L5
220 nH
27 nH
30 nH
22 nH
R1, R2
100
200
100
499
5V
L1
L3
AMP VOUT -
C1
L5
AMP VOUT +
L2
ADC ZIN
C2
L4
R1
C3
AMP ZOUT
R2
ADC VIN +
ADC VIN -
ADC VCM
5V
Figure 45. Sample Filter
POWER SUPPLIES
As shown in Figure 46, the LMH6515 has a number of options for power supply connections on the output pins.
Pin 3 (VCC) is always connected. The output stage can be connected as shown in Figure 47, Figure 48, or
Figure 49. The supply voltage range for VCC is 4V to 5.25V. A 5V supply provides the best performance while
lower supplies will result in less power consumption. Power supply regulation of 2.5% or better is advised.
Of special note is that the digital circuits are powered from an internal supply voltage of 3.3V. The logic pins
should not be driven above the absolute maximum value of 3.6V. See the DIGITAL CONTROL section for
details.
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LMH6515
NC
VCC
LATCH
GAIN_0
3
2
1
www.ti.com
4
SNOSAX4C – AUGUST 2007 – REVISED MARCH 2013
IN-
7
14
OUT+
GND
8
13
LOAD+
12
OUT-
GAIN_1
15
11
6
GAIN_2
IN+
10
LOAD-
GAIN_3
16
9
5
GAIN_4
GND
NC
VCC
LATCH
GAIN_0
4
3
2
1
Figure 46. Internal Load Resistors
5V
GND
5
16
NC
IN+
6
15
OUT-
IN-
7
14
OUT+
GND
8
13
NC
VOUT
9
10
11
12
GAIN_4
GAIN_3
GAIN_2
GAIN_1
+
5V
Figure 47. Using High Gain Mode (400Ω Load)
20
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VCC
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GAIN_0
3
2
1
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4
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5V
GND
5
16
IN+
6
15
OUT-
IN-
7
14
OUT+
GND
8
13
VOUT
+
12
GAIN_1
11
GAIN_2
10
GAIN_3
GAIN_4
9
5V
NC
VCC
LATCH
GAIN_0
4
3
2
1
Figure 48. Using Low Gain Mode (200Ω Load)
5V
GND
5
16
IN+
6
15
OUT-
IN-
7
14
OUT+
GND
8
13
VOUT
+
9
10
11
12
GAIN_4
GAIN_3
GAIN_2
GAIN_1
5V
Figure 49. Alternate Connection for Low Gain Mode (200Ω Load)
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Table 2. Compatible High Speed Analog to Digital Converters
Product Number
Max Sampling Rate (MSPS)
Resolution
Channels
ADC12L063
62
12
SINGLE
ADC12DL065
65
12
DUAL
ADC12L066
66
12
SINGLE
ADC12DL066
66
12
DUAL
CLC5957
70
12
SINGLE
ADC12L080
80
12
SINGLE
ADC12DL080
80
12
DUAL
ADC12C080
80
12
SINGLE
ADC12C105
105
12
SINGLE
ADC12C170
170
12
SINGLE
ADC12V170
170
12
SINGLE
ADC14C080
80
14
SINGLE
ADC14C105
105
14
SINGLE
ADC14DS105
105
14
DUAL
ADC14155
155
14
SINGLE
ADC14V155
155
14
SINGLE
ADC08D500
500
8
DUAL
ADC08500
500
8
SINGLE
ADC08D1000
1000
8
DUAL
ADC081000
1000
8
SINGLE
ADC08D1500
1500
8
DUAL
ADC081500
1500
8
SINGLE
ADC08(B)3000
3000
8
SINGLE
ADC08L060
60
8
SINGLE
ADC08060
60
8
SINGLE
ADC10DL065
65
10
DUAL
ADC10065
65
10
SINGLE
ADC10080
80
10
SINGLE
ADC08100
100
8
SINGLE
ADCS9888
170
8
SINGLE
ADC08(B)200
200
8
SINGLE
ADC11C125
125
11
SINGLE
ADC11C170
170
11
SINGLE
22
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REVISION HISTORY
Changes from Revision B (March 2013) to Revision C
•
Page
Changed layout of National Data Sheet to TI format .......................................................................................................... 21
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PACKAGE OPTION ADDENDUM
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24-Sep-2015
PACKAGING INFORMATION
Orderable Device
Status
(1)
LMH6515SQ/NOPB
ACTIVE
Package Type Package Pins Package
Drawing
Qty
WQFN
RGH
16
1000
Eco Plan
Lead/Ball Finish
MSL Peak Temp
(2)
(6)
(3)
Green (RoHS
& no Sb/Br)
CU SN
Level-3-260C-168 HR
Op Temp (°C)
Device Marking
(4/5)
-40 to 85
L6515SQ
(1)
The marketing status values are defined as follows:
ACTIVE: Product device recommended for new designs.
LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.
NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design.
PREVIEW: Device has been announced but is not in production. Samples may or may not be available.
OBSOLETE: TI has discontinued the production of the device.
(2)
Eco Plan - The planned eco-friendly classification: Pb-Free (RoHS), Pb-Free (RoHS Exempt), or Green (RoHS & no Sb/Br) - please check http://www.ti.com/productcontent for the latest availability
information and additional product content details.
TBD: The Pb-Free/Green conversion plan has not been defined.
Pb-Free (RoHS): TI's terms "Lead-Free" or "Pb-Free" mean semiconductor products that are compatible with the current RoHS requirements for all 6 substances, including the requirement that
lead not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, TI Pb-Free products are suitable for use in specified lead-free processes.
Pb-Free (RoHS Exempt): This component has a RoHS exemption for either 1) lead-based flip-chip solder bumps used between the die and package, or 2) lead-based die adhesive used between
the die and leadframe. The component is otherwise considered Pb-Free (RoHS compatible) as defined above.
Green (RoHS & no Sb/Br): TI defines "Green" to mean Pb-Free (RoHS compatible), and free of Bromine (Br) and Antimony (Sb) based flame retardants (Br or Sb do not exceed 0.1% by weight
in homogeneous material)
(3)
MSL, Peak Temp. - The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder temperature.
(4)
There may be additional marking, which relates to the logo, the lot trace code information, or the environmental category on the device.
(5)
Multiple Device Markings will be inside parentheses. Only one Device Marking contained in parentheses and separated by a "~" will appear on a device. If a line is indented then it is a continuation
of the previous line and the two combined represent the entire Device Marking for that device.
(6)
Lead/Ball Finish - Orderable Devices may have multiple material finish options. Finish options are separated by a vertical ruled line. Lead/Ball Finish values may wrap to two lines if the finish
value exceeds the maximum column width.
Important Information and Disclaimer:The information provided on this page represents TI's knowledge and belief as of the date that it is provided. TI bases its knowledge and belief on information
provided by third parties, and makes no representation or warranty as to the accuracy of such information. Efforts are underway to better integrate information from third parties. TI has taken and
continues to take reasonable steps to provide representative and accurate information but may not have conducted destructive testing or chemical analysis on incoming materials and chemicals.
TI and TI suppliers consider certain information to be proprietary, and thus CAS numbers and other limited information may not be available for release.
In no event shall TI's liability arising out of such information exceed the total purchase price of the TI part(s) at issue in this document sold by TI to Customer on an annual basis.
Addendum-Page 1
Samples
PACKAGE OPTION ADDENDUM
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24-Sep-2015
Addendum-Page 2
PACKAGE MATERIALS INFORMATION
www.ti.com
2-Sep-2015
TAPE AND REEL INFORMATION
*All dimensions are nominal
Device
LMH6515SQ/NOPB
Package Package Pins
Type Drawing
WQFN
RGH
16
SPQ
Reel
Reel
A0
Diameter Width (mm)
(mm) W1 (mm)
1000
178.0
12.4
Pack Materials-Page 1
4.3
B0
(mm)
K0
(mm)
P1
(mm)
4.3
1.3
8.0
W
Pin1
(mm) Quadrant
12.0
Q1
PACKAGE MATERIALS INFORMATION
www.ti.com
2-Sep-2015
*All dimensions are nominal
Device
Package Type
Package Drawing
Pins
SPQ
Length (mm)
Width (mm)
Height (mm)
LMH6515SQ/NOPB
WQFN
RGH
16
1000
213.0
191.0
55.0
Pack Materials-Page 2
PACKAGE OUTLINE
RGH0016A
WQFN - 0.8 mm max height
SCALE 3.500
WQFN
4.1
3.9
B
A
PIN 1 INDEX AREA
0.5
0.3
0.3
0.2
4.1
3.9
DETAIL
OPTIONAL TERMINAL
TYPICAL
C
0.8 MAX
SEATING PLANE
(0.1)
TYP
2.6 0.1
5
8
SEE TERMINAL
DETAIL
12X 0.5
4
9
4X
1.5
1
12
16X
PIN 1 ID
(OPTIONAL)
13
16
16X
0.3
0.2
0.1
0.05
C A
C
B
0.5
0.3
4214978/A 10/2013
NOTES:
1. All linear dimensions are in millimeters. Dimensions in parenthesis are for reference only. Dimensioning and tolerancing
per ASME Y14.5M.
2. This drawing is subject to change without notice.
3. The package thermal pad must be soldered to the printed circuit board for thermal and mechanical performance.
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EXAMPLE BOARD LAYOUT
RGH0016A
WQFN - 0.8 mm max height
WQFN
( 2.6)
SYMM
16
13
SEE DETAILS
16X (0.6)
16X (0.25)
1
12
(0.25) TYP
SYMM
(3.8)
(1)
9
4
12X (0.5)
5X ( 0.2)
VIA
8
5
(1)
(3.8)
LAND PATTERN EXAMPLE
SCALE:15X
0.07 MIN
ALL AROUND
0.07 MAX
ALL AROUND
METAL
SOLDER MASK
OPENING
METAL
SOLDER MASK
OPENING
NON SOLDER MASK
DEFINED
(PREFERRED)
SOLDER MASK
DEFINED
SOLDER MASK DETAILS
4214978/A 10/2013
NOTES: (continued)
4. This package is designed to be soldered to a thermal pad on the board. For more information, see QFN/SON PCB application report
in literature No. SLUA271 (www.ti.com/lit/slua271).
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EXAMPLE STENCIL DESIGN
RGH0016A
WQFN - 0.8 mm max height
WQFN
SYMM
(0.675)
METAL
TYP
13
16
16X (0.6)
16X (0.25)
12
1
(0.25) TYP
(0.675)
SYMM
(3.8)
12X (0.5)
9
4
8
5
4X
(1.15)
(3.8)
SOLDER PASTE EXAMPLE
BASED ON 0.125 mm THICK STENCIL
EXPOSED PAD
78% PRINTED SOLDER COVERAGE BY AREA
SCALE:15X
4214978/A 10/2013
NOTES: (continued)
5. Laser cutting apertures with trapezoidal walls and rounded corners may offer better paste release. IPC-7525 may have alternate
design recommendations.
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