MGA-53543 50 MHz to 6 GHz High Linear Amplifier Data Sheet Description Features Avago Technologies’s MGA-53543 is a high dynamic range low noise amplifier MMIC housed in a 4-lead SC-70 (SOT343) surface mount plastic package. Lead-free Option Available The combination of high linearity, low noise figure and high gain makes the MGA-53543 ideal for cellular/PCS/ W-CDMA base stations, Wireless LAN, WLL and other systems in the 50 MHz to 6 GHz frequency range. Advanced enhancement mode PHEMT technology MGA-53543 is especially ideal for Cellular/PCS/ W-CDMA basestation applications. With high IP3 and low noise figure, the MGA-53543 may be utilized as a driver amplifier in the transmit chain and as a second stage LNA in the receive chain. Very high linearity at low DC bias power[1] Low noise figure Excellent uniformity in product specifications Low cost surface mount small plastic package SOT343 (4-lead SC-70) Tape-and-Reel packaging option available Specifications 1.9 GHz, 5V, 54 mA (typ) OIP3: 39 dBm Surface Mount Package SOT-343/4-lead SC70 Noise figure: 1.5 dB Gain: 15.4 dB P-1dB: 18.6 dBm Applications Base station radio card Pin Connections and Package Marking 3 GND 4 53x INPUT 1 GND 2 OUTPUT & Vd Note: Top View. Package marking provides orientation and identification. “53” = Device Code “x” = Date code character identifies month of manufacture. Attention: Observe precautions for handling electrostatic sensitive devices. ESD Machine Model (Class A) ESD Human Body Model (Class 1A) Refer to Avago Application Note A004R: lectrostatic Discharge Damage and Control. High linearity LNA for base stations, WLL, WLAN, and other applications in the 50 MHz to 6 GHz range Note: 1. The MGA-53543 has a superior LFOM of 15 dB. Linearity Figure of Merit (LFOM) is essentially OIP3 divided by DC bias power. There are few devices in the market that can match its combination of high linearity and low noise figure at the low DC bias power of 5V/54 mA. Simplified Schematic INPUT OUTPUT, Vd bias GND MGA-53543 Absolute Maximum Ratings [1] Symbol Parameter Units Absolute Maximum Vin Maximum Input Voltage V 0.8 Vd Supply Voltage V 5.5 Pd Power Dissipation [2] mW 400 Pin CW RF Input Power dBm 13 Tj Junction Temperature °C 150 TSTG Storage Temperature °C -65 to 150 Thermal Resistance [3] (Vd=5.0V) jc = 130C/W Notes: 1. Operation of this device in excess of any of these limits may cause permanent damage. 2. Source lead temperature is 25°C. Derate 7.7mW/°C for TL > 98°C 3. Thermal resistance measured using 150°C Liquid Crystal Measurement Technique. Electrical Specifications Tc = +25°C, Zo = 50 Ω, Vd = 5V, unless noted Symbol Parameter and Test Condition Frequency Units Min. Typ. Max. [3] Id Current Drawn N/A mA 40 54 70 2.7 Noise Figure 2.4 GHz 1.9 GHz 0.9 GHz dB 1.9 1.5 1.3 1.9 0.06 2.4 GHz 1.9 GHz 0.9 GHz dB 14 15.1 15.4 17.4 17.0 0.25 2.4 GHz 1.9 GHz 0.9 GHz dBm 36 38.7 39.1 39.7 Output Power at 1 dB Gain Compression 2.4 GHz 1.9 GHz 0.9 GHz dBm 18.3 18.6 19.3 NF [1] Gain[1] OIP3 [1,2] P1dB [1] Gain Output Third Order Intercept Point PAE[1] Power Added Effciency at P1dB 1.9 GHz 0.9 GHz % % 29.7 28.3 RLin[1] Input Return Loss 2.4 GHz 1.9 GHz 0.9 GHz dB -12.7 -13.2 -11.1 2.4 GHz 1.9 GHz 0.9 GHz dB -25.1 -14.3 -14.4 RLout [1] ISOL[1] Output Return Loss Isolation |s12|2 1.9 GHz 0.9 GHz dB 1.89 -23.4 -22.3 Notes: 1. Measurements obtained from a test circuit described in Figure 1. Input and output tuners tuned for maximum OIP3 while keeping VSWR better than 2:1. Data corrected for board losses. 2. I) Output power level and frequency of two fundamental tones at 1.9 GHz: F1 = 5.49 dBm, F2 = 5.49 dBm, F1 = 1.905 GHz, and F2 = 1.915 GHz. II) Output power level and frequency of two fundamental tones at 900 MHz: F1 = -0.38 dBm, F2 = -0.38 dBm, F1 = 905 MHz, and F2 = 915 MHz. 3. Standard deviation data are based on at least 500 pieces sample size taken from 8 wafer lots. Future wafers allocated to this product may have nominal values anywhere between the upper and lower spec limits. Input Gamma & Transmission Line ΓSource = 0.38 ∠ 156° (0.7 dBm Loss) Vd 53x RF Input Figure 1. Block Diagram of 1.9 GHz Test Fixture. 2 Output Gamma & Transmission Line with Bias Tee ΓLoad = 0.05 ∠ 45° (0.85 dBm Loss) RF Output MGA-53543 Typical Performance All data measured at Tc = 25°C, Vd = 5 V with input and output tuners tuned for maximum OIP3 while keeping VSWR better than 2:1 unless stated otherwise. 45 45 -40C +25C +85C -40C +25C +85C 40 35 30 P1dB (dBm) 20 OIP3 (dBm) OIP3 (dBm) 40 24 35 30 16 12 25 25 8 20 20 0 1 2 3 4 5 6 7 -5 -1 3 FREQUENCY (GHz) 7 11 0 15 3.8 4 5 6 -5 15 S11 & S22 (dB) Fmin (dB) |S21|2 (dB) 2.8 10 -10 -15 1.8 S22 S11 -20 -40C +25C +85C 5 0 1 2 3 4 5 0.8 6 0 1 FREQUENCY (GHz) 2 3 4 5 6 FREQUENCY (GHz) Figure 5. |S21|2 vs. Frequency and Temperature. 60 -21 50 Id (mA) -23 -25 40 30 20 -27 -40C +25C +85C 10 0 -29 1 2 3 4 FREQUENCY (GHz) Figure 8. Isolation vs. Frequency. 5 6 0 1 2 3 0 1 2 3 4 Figure 7. S11 and S22 (50) vs. Frequency. 70 S12 -25 FREQUENCY (GHz) Figure 6. Fmin vs. Frequency and Temperature. -19 0 7 0 -40C +25C +85C ISOLATION (dB) 3 Figure 4. Output Power at 1dB Compression vs. Frequency and Temperature. Figure 3. Output Third Order Intercept Point vs. Output Power at 2 GHz. 20 2 FREQUENCY (GHz) Pout (dBm) Figure 2. Output Third Order Intercept Point vs. Frequency and Temperature. 3 1 4 5 Vd (V) Figure 9. Current vs. Voltage and Temperature. 6 5 6 MGA-53543 Typical Scattering Parameters TC = 25°C, Vd = 5.0V, Id = 54 mA, ZO = 50 Ω, (in ICM test fixture) Freq (GHz) S11 Mag. S11 Ang. S21 dB S21 Mag. S21 Ang. S12 dB S12 Mag. S12 Ang. S22 Mag. S22 Ang. K 0.05 0.1 0.2 0.3 0.4 0.5 0.6 0.7 0.8 0.9 1.0 1.1 1.2 1.3 1.4 1.5 1.6 1.7 1.8 1.9 2.0 2.1 2.2 2.3 2.4 2.5 3.0 3.5 4.0 4.5 5.0 5.5 6.0 6.5 7.0 7.5 8.0 8.5 9.0 9.5 10.0 0.823 0.641 0.439 0.349 0.305 0.251 0.233 0.22 0.212 0.207 0.201 0.198 0.196 0.194 0.195 0.197 0.199 0.201 0.205 0.212 0.216 0.221 0.229 0.235 0.241 0.25 0.293 0.342 0.394 0.445 0.497 0.534 0.565 0.595 0.615 0.635 0.662 0.682 0.715 0.752 0.754 -38.8 -66.7 -98.7 -116.8 -128.9 -135.6 -142.5 -147.5 -151.1 -153.6 -155.3 -157.3 -158.2 -158.4 -159.4 -160 -160.1 -160.5 -161.5 -162.6 -163.1 -164.8 -166.1 -167.2 -169.2 -171.4 176.8 162.2 148.2 133.9 121.6 109.9 99.5 88.2 77.5 65.2 53.9 43.4 32.3 24.9 16 26.26 24.39 21.55 20.14 19.39 18.92 18.6 18.34 18.12 17.9 17.7 17.51 17.31 17.1 16.9 16.7 16.48 16.26 16.04 15.82 15.59 15.36 15.14 14.9 14.67 14.43 13.28 12.13 10.99 9.84 8.7 7.56 6.46 5.38 4.31 3.3 2.29 1.37 0.45 -0.31 -1.12 20.56 16.584 11.954 10.165 9.317 8.826 8.509 8.261 8.053 7.854 7.674 7.505 7.335 7.165 7 6.836 6.666 6.498 6.341 6.179 6.017 5.862 5.714 5.56 5.412 5.265 4.611 4.039 3.544 3.105 2.721 2.388 2.105 1.857 1.643 1.462 1.301 1.171 1.053 0.965 0.879 161.3 148.9 142.7 141.8 140.7 139.3 136.7 133.6 130.2 126.7 123 119.2 115.4 111.6 107.7 103.9 100.1 96.3 92.6 88.9 85.3 81.7 78.3 74.7 71.2 67.8 51.5 36.2 21.6 7.8 -5.2 -17.5 -28.8 -39.6 -49.8 -59.6 -68.8 -77.6 -86 -93.5 -101.7 -27.96 -24.29 -22.50 -22.05 -21.94 -21.83 -21.72 -21.72 -21.72 -21.62 -21.62 -21.62 -21.62 -21.62 -21.62 -21.62 -21.72 -21.72 -21.72 -21.83 -21.83 -21.94 -21.94 -22.05 -22.16 -22.16 -22.50 -22.73 -22.62 -22.27 -21.51 -20.72 -19.83 -18.94 -18.27 -17.72 -17.27 -16.77 -16.31 -15.86 -15.55 0.04 0.061 0.075 0.079 0.08 0.081 0.082 0.082 0.082 0.083 0.083 0.083 0.083 0.083 0.083 0.083 0.082 0.082 0.082 0.081 0.081 0.08 0.08 0.079 0.078 0.078 0.075 0.073 0.074 0.077 0.084 0.092 0.102 0.113 0.122 0.13 0.137 0.145 0.153 0.161 0.167 59.7 40.6 22.9 15.4 11.2 9 7 5.4 4 2.8 1.7 0.7 -0.2 -1.1 -2 -2.8 -3.6 -4.3 -4.9 -5.6 -6.2 -6.7 -7.3 -7.6 -7.9 -8.2 -8.6 -7.3 -5.3 -3.4 -2.7 -3.5 -5.9 -10.4 -16 -22.1 -28.2 -34.2 -40.9 -47.5 -55.3 0.72 0.558 0.344 0.235 0.176 0.097 0.087 0.094 0.11 0.129 0.148 0.169 0.186 0.203 0.219 0.235 0.248 0.261 0.273 0.283 0.293 0.301 0.31 0.316 0.322 0.327 0.338 0.333 0.313 0.287 0.256 0.229 0.204 0.185 0.162 0.127 0.084 0.033 0.028 0.081 0.129 -33 -61.5 -95.3 -118.3 -138.2 -167.4 159.7 131.8 110.7 95.4 84.1 74.8 66.6 59.6 53.1 47.6 42.2 37.1 32.4 28 23.8 19.8 16 12.3 8.8 5.5 -9.4 -22.6 -34.9 -48 -62.1 -77.8 -94.1 -108.7 -120.2 -128.8 -132.9 -145.4 57.9 51.3 50.1 0.3 0.4 0.7 0.9 0.9 1 1 1.1 1.1 1.1 1.1 1.1 1.1 1.1 1.1 1.1 1.1 1.1 1.1 1.2 1.2 1.2 1.2 1.2 1.3 1.3 1.4 1.5 1.6 1.6 1.6 1.6 1.5 1.5 1.5 1.6 1.6 1.6 1.6 1.5 1.6 4 MGA-53543 Typical Noise Parameters TC = 25°C, Vd = 5.0V, Id = 54 mA, ZO = 50 Ω, (in ICM test fixture) Freq (GHz) Fmin (dB) opt Mag opt Ang Rn/Zo Ga (dB) 0.5 0.8 0.9 1.0 1.1 1.5 1.8 1.9 2.0 2.1 2.2 2.3 2.4 2.5 3.0 3.5 3.8 3.9 4.0 4.5 5.0 5.5 5.7 5.8 5.9 6.0 6.5 7.0 7.5 8.0 8.5 9.0 9.5 10.0 1.07 1.11 1.12 1.14 1.14 1.22 1.3 1.31 1.34 1.36 1.35 1.4 1.44 1.49 1.59 1.64 1.71 1.74 1.76 1.96 2.11 2.38 2.49 2.51 2.54 2.61 2.81 3.14 3.48 3.81 4.07 4.16 4.18 4.62 0.108 0.144 0.159 0.171 0.213 0.238 0.223 0.229 0.237 0.243 0.254 0.255 0.264 0.272 0.298 0.369 0.4 0.41 0.417 0.469 0.521 0.555 0.563 0.568 0.583 0.579 0.613 0.63 0.652 0.673 0.694 0.741 0.778 0.771 156.5 173.2 175.3 173.9 166.3 -179 -175.2 -172 -169.3 -167.3 -165 -163.2 -159.9 -158 -142.3 -131.2 -123.8 -123 -120.2 -108 -99.4 -90.1 -87.3 -84.3 -82.7 -81.7 -72.1 -63.1 -52 -42 -32.5 -22.7 -16.7 -8.9 0.1 0.09 0.09 0.09 0.08 0.08 0.09 0.09 0.09 0.09 0.09 0.09 0.09 0.1 0.12 0.13 0.16 0.17 0.18 0.26 0.35 0.49 0.56 0.6 0.64 0.66 0.9 1.17 1.56 2.05 2.56 3.21 3.89 4.48 19.13 18.28 18.08 17.89 17.71 16.99 16.45 16.27 16.07 15.88 15.69 15.49 15.29 15.09 14.12 13.14 12.56 12.39 12.19 11.23 10.34 9.42 9.04 8.84 8.7 8.52 7.66 6.71 5.78 4.92 4.11 3.47 3.2 2.41 MGA-53543 Typical Linearity Parameters TC = 25°C, Vd = 5V, ZO = 50 Ω Freq Source[1] Mag Source[1] (°) Load[1] Mag Load[1] (°) OIP3 (dBm) 500 MHz 900 MHz 1.9 GHz 2.4 GHz 0.31 0.15 0.38 0.49 -102 -90 156 177 0.25 0.05 0.05 0.17 -13 -165 45 141 40 40 39 36 Note: 1. Input and output tuners tuned for maximum OIP3 while keeping VSWR better than 2:1 5 MGA-53543 Applications Information RF Output Description Few matching elements are required on the output of the MGA-53543 to achieve good linearity because the output Gamma (L) is close to 50Ω. The MGA-53543 is a highly linear enhancement mode PHEMT (Pseudomorphic High Electron Mobility Transistor) amplifier with a frequency range extending from 450 MHz to 6 GHz. This range makes the MGA-53543 ideal for both Cellular and PCS basestation applications. With high IP3 and low noise figure, the MGA-53543 may be utilized as a driver amplifier in a transmit chain or as a first or second stage LNA in a receive chain or any other application requiring high linearity. The MGA-53543 operates from a +5 volt power supply and draws a nominal current of 53.8 mA. The RFIC is contained in a miniature SOT-343 (SC-70 4-lead) package to minimize printed circuit board space. This package also offers good thermal dissipation and RF characteristics. DC Bias To bias the MGA-53543, a +5 volt supply is connected to the output pin through an inductor, RFC, which isolates the inband signal from the DC supply as shown in Figure 2. Capacitor C3 serves as an RF bypass for inband signals while C4 helps eliminate out of band low frequency signals. An optional resistor R1 may be added to de-Q any resonance created between C3 and C4. Typically values range from 2.2Ω to 10Ω. A DC blocking capacitor, C2, is used at the output of the MMIC to isolate the supply voltage from succeeding circuits. C2 Application Guidelines For most applications, all that is required to operate the MGA is to apply a DC bias of +5 volts and match the RF input and output. 1 RFout 2 RFC 53 RFin C1 3 RF Input 4 C3 R1 L1 *S *L C4 +5V Figure 11. Schematic diagram with bias connections. Operating at Other Voltages Operating this RFIC at voltages less than 5V will affect NF, Gain, P1dB and IP3. Figure 12 below demonstrates the affects of changing supply voltage at 1900 MHz. 20 NF, GAIN, and P1dB (dB) The first step to achieve maximum linearity is to match the input of MGA-53543 to one of the linearity values listed on the data sheet. For example, at 1900 MHz the MGA-53543 needs to see a complex impedance of 0.38 156° looking towards the source and an output impedance of 0.05 45° looking towards the load. This may be accomplished by a conjugate match from the system input impedance (typically 50Ω) to S*. Figure 10 shows the location of these input and output Gammas (S and L) required for a high linearity. 15 10 NF Gain P1dB 5 0 1 2 3 4 5 SUPPLY VOLTAGE (V) Figure 12. Gain, NF and P1dB vs. supply voltage at 1900 MHz. Figure 10. Matching for linearity at 1900 MHz. 6 The affects of supply voltage on OIP3 and current at 1900 MHz are shown in Table 1. The MGA-53543 is internally biased for optimal performance at a quiescent current of 53.8 mA. Table 1. OIP3 vs. supply power. Voltage (V) OIP3 (dBm) Id (mA) 1V 0 4 2V 17 3V 28 Table 2. Required matching for NF, IP3, input & output Return Loss and Gain. Match for Input Tuning Output Tuning 16 IP3 s L 24 NF opt none S11* none 4V 35 41 RLin 5V 39 51 RLout none S22* Gain S11* S22* Matching The most important criterion when designing with the MGA-53543 is choosing the input and output-matching network. The MGA-53543 is designed to give excellent IP3 performance, however to achieve this requires both the input and output matching network to present specific impedances (S and L) to the device. It is also possible to match this part for best NF or best gain. However, this will impact the IP3 performance. To achieve best noise figure, the input match will need to be modified to present gamma opt to the device. To achieve the best gain will require both the input and output to be conjugately matched (which will also result in the best return loss). Where needed, the match presented to the input and the output of the device can be modified to compromise between IP3, NF and gain performance. PCB Layout A recommended PCB pad layout for the miniature SOT343 (SC-70) package used by the MGA-53543 is shown in Figure 14. 1.30 0.051 1.00 0.039 2.00 0.079 0.60 0.024 The MGA-53543 has isolation large enough to allows input and output reflection coefficients to be replaced by S11 and S22. In general matching for minimum noise figure does not necessarily guarantee good IP3 performance nor does it guarantee good gain. This is due to the fact that the impedance parameters shown below in Table 2 are not guaranteed to lie near each other on a Smith Chart. So, ideally if all input matching parameters lied near each other or at the same point, and all output parameters also lied near each other or at the same point, the amplifier would have minimum Noise Figure, maximum IP3 and maximum Gain all with a single match. Typically this is not the case and some parameter must be sacrificed to improve another. Table 2 briefly lists the input and output parameters required for each type of match while Figure 13 depicts how each is defined. Input Match Output Match 53 1.15 0.045 Dimensions in This layout provides ample allowance for package placement by automated assembly equipment without adding parasitics that could impair the high frequency RF performance of the MGA-53543. The layout is shown with a footprint of a SOT-343 package superimposed on the PCB pads for reference. A microstrip layout with sufficient ground vias as shown in Figure 6 is recommended for the MGA-53543 in transitioning from a package pad layout as in Figure 14. RF OUTPUT 53 NF Γopt Γopt* IP3 ΓS ΓS* ΓL* ΓL Gain S11* S11 S22 S22* Figure 13. Definition of matching parameters. mm inches Figure 14. Recommended PCB Pad Layout for Avago’s SC70 4L/SOT-343 Products. 50Ω 50Ω 7 0.9 0.035 RF INPUT Figure 15. Microstripline Layout. RF Grounding 1900 MHz HLA Design Adequate grounding of Pins 1 and 4 of the RFIC are important to maintain device stability and RF performance. Each of the ground pins should be connected to the ground plane on the backside of the PCB by means of plated through holes (vias). The ground vias should be placed as close to the package terminals as practical to reduce inductance in ground path. It is good practice to use multiple vias to further minimize ground path inductance. The following describes a typical application for the MGA53543 as used in a PCS 1900 MHz band radio receiver optimized for maximum linearity. Steps include matching the input and output as well as providing a DC bias while maintaining acceptable stability, gain and noise figure. PCB Materials FR-4 or G-10 type material is a good choice for most low cost wireless applications using single or multi-layer printed circuit boards. Typical single-layer board thickness is 0.020 to 0.031 inches. Circuit boards thicker than 0.031 inches are not recommended due to excessive inductance in the ground vias. As described earlier, a pure linearity match entails matching only to s and L, thus sacrificing some NF and Gain. This tradeoff is explained below and quantified in Figures 8 and 9. Using the device S-parameters at 1900 MHz, the minimum noise figure possible, whilst matching the input to S, is shown to be 1.7 dB. *S – Optimum linearity match For noise figure critical or higher frequency applications, the additional cost of PTFE/glass dielectric materials may be warranted to minimize transmission line loss at the amplifier’s input. Application Example NF = 1.7 dB The demonstration circuit board for the MGA-53543 is shown in Figure 16. This simple two-layer board contains microstripline on the topside and a solid metal ground plane on the backside with all RF traces having characteristic impedance of 50Ω. Multiple 0.02" vias are used to bring the ground to the topside of the board and help reduce ground inductance. NF = 1.6 dB NF = 1.5 dB The PCB is fabricated on 0.031" thick Getek® GR200D dielectric material with dielectric constant of 4.2. MGA - 5X *opt – Optimum NF match Figure 17. Noise figure performance. Because gain depends both on the input and output match, the maximum gain is taken from two sets of circles. One is centered around S11 and the other is centered on S22. Thus the maximum attainable gain is the lesser of two circles which completely enclose s or L. For example, in Figure 18 the 16.1 dB input gain circle completely encloses s, but the smallest circle that encloses L is 15.9 dB. Thus the maximum gain is the weakest link or 15.9 dB. Ga = 15.9 dB Ga = 16.1 dB Ga = 16.2 dB IN OUT *L *S S11 SE 12/01 S22 Vd Figure 16. MGA-53453 PCB Layout. Ga = 16.2 dB Ga = 16.1 dB Figure 18. Input and output gain circles. 8 No matching is required for the output, but a good rule of thumb to use when biasing is to limit series reactance to less than 5Ω and keep shunt reactance above 500Ω. Therefore choosing an RFC of 47 nH, which has a reactance of 561Ω at 1.9 GHz, helps isolate the DC supply from inband signals. If any high frequency signal is created or enters the DC supply, a 150 pF capacitor is ready to short it to ground. An 8.2 pF capacitor serves primarily as a DC block, but also helps the output match. The completed 1900 MHz amplifier schematic is shown in Figure 19. 8.2 pF 1 RFout 2 2.2 pF 3 GAIN and NF (dB) 15 Gain 10 5 NF 0 1.6 1.8 2 2.2 2.4 2.6 FREQUENCY (GHz) Figure 20. Gain and Noise Figure vs Frequency. 0 -5 47 nH 53 RFin 20 RETURN LOSS (dB) To accomplish the above performance, a high pass configuration consisting of a 3.3 nH inductor and a 2.2 pF capacitor is used for the input match. Unlike a low pass configuration, a high pass configuration provides not only the impedance transfer required, but also provides excellent stability for the demo board by diminishing low frequency gain. S11 -10 -15 S22 -20 150 pF -25 1.6 4 2.2Ω 1.8 2 2.2 2.4 2.6 FREQUENCY (GHz) 3.3 nH +5V 0.1 μF Figure 19. Schematic for a 1900 MHz stable circuit. Included with the schematic is a complete RF layout (Figure 24) which includes placement of all components and SMA connectors. A list of part numbers and manufacturer used is given below in Table 3. Figure 21. Input and Output return loss vs Frequency. More significant is the linearity delivered by MGA-53543 at 1900 MHz. Figure 22 plots OIP3 over a frequency range from 1850 MHz to1950 MHz. This device produces IIP3 of 24 dBm, OIP3 of 38 dBm and P1dB of 17.8 dBm at 1900 MHz. Table 3. Component parts list for the MGA-53543 HLA at 1900 MHz. TOKO LL1608-FS3N3S 47 nH TOKO LL1005-FH47N 2.2Ω RHOM MCR01J2R2 2.2 pF Phycomp 0402CG229C9B200 8.2 pF Phycomp 0402CG829D9B200 150 pF Phycomp 0402CG151J9B200 0.1 μF Phycomp 06032F104M8B20 40 OIP3 (dBm) 3.3 nH 45 35 30 TX 25 1840 1880 RX 1920 1960 2000 FREQUENCY (MHz) Performance of MGA-53543 at 1900 MHz With a device voltage of +5V, demonstration board MGA5X delivers a measured noise figure of 1.78 dB and an average gain of 14.5 dB as shown in Figure 20. Gain here is slightly lower than data sheet due to the losses acquired in creating a stable broadband match. Input and output VSWR are both better than 2:1 at 1900 MHz, with input return loss being 10 dB and output return loss at 13 dB. 9 Figure 22. OIP3 vs. Frequency. Due to component parasitics and part variations, actual performance may not be identical to this example. 900 MHz HLA Design Performance of MGA-53543 at 900 MHz Optimizing the MGA-53543 for maximum linearity at the Cellular band follows very similar to that of 1900 MHz, except that the input and output tuning conditions will change according to the linearity table on the data sheet. Figure 14 below shows the schematic diagram for a complete 900 MHz circuit using s of 0.15 -90° and L of At 900 MHz MGA-53543 delivers OIP3 of 40 dBm along with a noise figure of 1.43 dB. Gain is measured to be 17.1 dB and input return loss is 13.7 dB and output return loss is 13.3 dB as shown in Figures 16 and 17. P1dB is 18.8 dBm. 20 0.05 -165°. Table 4 shows the component parts list used. 15 GAIN and NF (dB) An optional 2.2Ω resistor at the input helps resistively load the amplifier and improve stability but slightly degrade noise figure. Gain 4.7 pF 1 5.6 pF 2 3 5 NF RFout 0 400 15 nH 53 RFin 600 800 1000 1200 1400 FREQUENCY (MHz) 1000 pF 4 Figure 25. Gain and Noise Figure vs Frequency. 2.2Ω 22 nH 10 0 +5V Figure 23. Schematic diagram for 900 MHz HLA. Table 4. Component parts list for the MGA-53543 HLA at 900 MHz. 22 nH TOKO LL1608-FS22N 15 nH TOKO LL1005-FS15N 2.2Ω RHOM MCR01J2R2 4.7 pF Phycomp 0402CG479C9B200 5.6 pF Phycomp 0402CG569D9B200 RETURN LOSS (dB) 2.2Ω S11 S22 -20 400 C2 IN 53 L2 C3 J1 L1 02/01 Figure 24. RF Layout for 1900 MHz HLA . 800 1000 1200 1400 Figure 26. Input and Output return loss vs Frequency. R1 C1 600 FREQUENCY (MHz) MGA - 5X 10 -10 -15 1000 pF Phycomp 04022R102K9B200 SE -5 R2 OUT Vd J2 900 MHz LNA Design 20 Gain 15 GAIN and NF (dB) To demonstrate the versatility of the MGA-53543, the following example describes a cellular band Low Noise Amplifier (LNA) design. The methodology for a 900 MHz LNA design differs from the previous examples in that only the input match affects noise figure. Thus, optimizing for minimum noise figure entails matching only the input to opt instead of S, and the output can either be matched to S22 for better gain or L for better linearity. Figure 27 shows the complete schematic for a 900 MHz low noise amplifier design and Table 5 describes the required components. 10 5 NF 0 400 600 RFout 2 4.7 pF 3 -5 4 +5V Figure 27. Schematic for 900 MHz LNA design. -10 -15 -20 Table 5. Component Parts List for the MGA-53543 HLA at 900 MHz. -25 12 nH TOKO LL1608-FS12NJ 15 nH TOKO LL1005-FS15N -30 400 4.7 pF Phycomp 0402CG479C9B200 2.2Ω RHOM MCR01J2R2 1000 pF Phycomp 04022R102K9B200 Performance of MGA-53543 at 900 MHz Biased with a +5 Volt supply MGA-53543 delivers a Noise Figure of 1.33 dB at 900 MHz. This number is higher than NFmin only because of loss from lumped element components with parasitic losses. A microstip or distributed element match may improve noise figure by .2 dB. Gain is measured to be 17.4 dB as shown in Figure 28. Input and output VSWR are both better than 2:1, with input return loss of 25 dB and output return loss at 17.5 dB shown in Figure 29. 11 1400 0 1000 pF 2.2Ω 12 nH 1200 15 nH 53 RFin 1000 Figure 28. Gain, Noise Figure and Output Power at 900 MHz. RETURN LOSS (dB) 1 800 FREQUENCY (MHz) 4.7 pF S11 S22 600 800 1000 1200 1400 FREQUENCY (MHz) Figure 29. Input and Output return loss at 900 MHz. Input IIP3 is measured to be 18.6 dBm and P1dB is 19.0 dB at 900 MHz. 1900 MHz LNA Design Performance of MGA-53543 at 1900 MHz The final example presented in this application note is a PCS band low noise amplifier circuit. As in the 900 MHz LNA example, the input is matched to opt which at 1900 MHz is given as .229 -172° and the output is matched for maximum linearity i.e. L. Biasing the DC supply is done very similar to the 1900 MHz HLA. In fact, the only major difference between the PCS HLA presented earlier and this PCS LNA schematic is a 3.9nH inductor on the input. The complete schematic is shown below. The typical noise figure for the 1900 MHz LNA is measured to be 1.62 dB with OIP3 at a nominal 37 dBm. Figure 31 shows a measured gain of 14.8 dB and Figure 32 shows the input and output return loss to be 16.4 dB and 11.3 dB respectively. P1dB is 18 dBm. 1 RFout 2 47 nH 53 RFin 2.2 pF 15 GAIN and NF (dB) 8.2 pF 20 Gain 10 5 150 pF NF 3 4 2.2Ω 3.9 nH 0 1.6 1.8 +5V Figure 30. Schematic for 1900 MHz LNA design. TOKO LL1608-FS3N9S 47 nH TOKO LL1005-FH47N 2.2Ω RHOM MCR01J2R2 2.2 pF Phycomp 0402CG229C9B200 8.2 pF Phycomp 0402CG829D9B200 150 pF Phycomp 0402CG151J9B200 2.4 2.6 0 -5 RETURN LOSS (dB) 3.9 nH 2.2 Figure 31. Gain, Noise Figure vs. Frequency for 1900 MHz LNA. Table 6 shows the complete parts list used for the 1900 MHz low noise amplifier. Table 6. Component parts list for the MGA-53453 LNA amplifier at 1900 MHz. 2.0 FREQUENCY (GHz) S22 -10 S11 -15 -20 -25 1.6 1.8 2.0 2.2 2.4 2.6 FREQUENCY (GHz) Figure 32. Input and Output Return Loss for 1900 MHz LNA. Summary Device Model In summary, the MGA-53543 offers very high IP3 as designed, but is versatile enough to give good NF performance wherever needed. Below is a summary of the preceding four examples. Refer to Avago’s web site www.avagotech.com/view/rf Table 7. 1900 MHz and 900 MHz HLA and 1900 MHz and 900 MHz LNA summary. 1900 MHz HLA LNA 12 900 MHz NF = 1.78 dB NF = 1.42 dB OIP3 = 38 dBm OIP3 = 40 dBm Ga = 14.5 dB Ga = 17.1 dB P1dB = 17.8 dBm P1dB = 18.8 dBm NF = 1.62 dB NF = 1.33 dB OIP3 = 37 dBm OIP3 = 36 dBm Ga = 14.8 dB Ga = 17.4 dB P1dB = 18.0 dBm P1dB = 19.0 dBm Part Number Ordering Information Part Number No. of Devices Container MGA-53543-TR1G 3000 7" Reel MGA-53543-TR2G 10000 13" Reel MGA-53543-BLKG 100 antistatic bag Package Dimensions Recommended PCB Pad Layout for Avago’s SC70 4L/SOT-343 Products Outline 43 (SOT-343/SC70 4 lead) 1.30 (0.051) 1.30 (.051) BSC 1.00 (0.039) HE 2.00 (0.079) E 0.60 (0.024) 1.15 (.045) BSC 0.9 (0.035) b1 D 1.15 (0.045) Dimensions in A2 A A1 b L C DIMENSIONS (mm) SYMBOL E D HE A A2 A1 b b1 c L 13 MIN. 1.15 1.85 1.80 0.80 0.80 0.00 0.15 0.55 0.10 0.10 MAX. 1.35 2.25 2.40 1.10 1.00 0.10 0.40 0.70 0.20 0.46 NOTES: 1. All dimensions are in mm. 2. Dimensions are inclusive of plating. 3. Dimensions are exclusive of mold flash & metal burr. 4. All specifications comply to EIAJ SC70. 5. Die is facing up for mold and facing down for trim/form, ie: reverse trim/form. 6. Package surface to be mirror finish. mm (inches) Device Orientation REEL TOP VIEW END VIEW 4 mm CARRIER TAPE 8 mm 53x USER FEED DIRECTION COVER TAPE 53x 53x 53x (Package marking example orientation shown.) Tape Dimensions For Outline 4T P P2 D P0 E F W C D1 t1 (CARRIER TAPE THICKNESS) Tt (COVER TAPE THICKNESS) K0 10° MAX. A0 DESCRIPTION 10° MAX. B0 SYMBOL SIZE (mm) SIZE (INCHES) CAVITY LENGTH WIDTH DEPTH PITCH BOTTOM HOLE DIAMETER A0 B0 K0 P D1 2.40 ± 0.10 2.40 ± 0.10 1.20 ± 0.10 4.00 ± 0.10 1.00 + 0.25 0.094 ± 0.004 0.094 ± 0.004 0.047 ± 0.004 0.157 ± 0.004 0.039 + 0.010 PERFORATION DIAMETER PITCH POSITION D P0 E 1.55 ± 0.10 4.00 ± 0.10 1.75 ± 0.10 0.061 + 0.002 0.157 ± 0.004 0.069 ± 0.004 CARRIER TAPE WIDTH THICKNESS W t1 8.00 + 0.30 - 0.10 0.254 ± 0.02 0.315 + 0.012 0.0100 ± 0.0008 COVER TAPE WIDTH TAPE THICKNESS C Tt 5.40 ± 0.10 0.062 ± 0.001 0.205 + 0.004 0.0025 ± 0.0004 DISTANCE CAVITY TO PERFORATION (WIDTH DIRECTION) F 3.50 ± 0.05 0.138 ± 0.002 CAVITY TO PERFORATION (LENGTH DIRECTION) P2 2.00 ± 0.05 0.079 ± 0.002 For product information and a complete list of distributors, please go to our web site: www.avagotech.com Avago, Avago Technologies, and the A logo are trademarks of Avago Technologies in the United States and other countries. Data subject to change. Copyright © 2005-2012 Avago Technologies. All rights reserved. Obsoletes 5989-3741EN AV02-0455EN - June 8, 2012