NSC LMV652MM 12 mhz, low voltage, low power amplifier Datasheet

LMV651/LMV652/LMV654
12 MHz, Low Voltage, Low Power Amplifier
General Description
Features
National’s LMV651/LMV652/LMV654 are high performance,
low power operational amplifier ICs implemented with
National's advanced VIP50 process. This family of parts features 12 MHz of bandwidth while consuming only 116 μA of
current, which is an exceptional bandwidth to power ratio in
this op amp class. The LMV651/LMV652/LMV654 are unity
gain stable and provide an excellent solution for general purpose amplification in low voltage, low power applications.
This family of low voltage, low power amplifiers provides superior performance and economy in terms of power and
space usage. These op amps have a maximum input offset
voltage of 1.5 mV, a rail-to-rail output stage and an input common-mode voltage range that includes ground. The LMV651/
LMV652/LMV654 provide a PSRR of 95 dB, a CMRR of 100
dB and a total harmonic distortion (THD) of 0.003% at 1 kHz
frequency and 2 kΩ load.
The operating supply voltage range for this family of parts is
from 2.7V and 5.5V. These op amps can operate over a wide
temperature range (-40°C to +125°C) making these op amps
ideal for automotive applications, sensor applications and
portable equipment applications. The LMV651 is offered in
the ultra tiny 5-Pin SC70 package, which is about half the size
of the 5-Pin SOT23. The LMV652 is offered in an 8-Pin MSOP
package. The LMV654 is offered in a 14-Pin TSSOP package.
(Typical 5V supply, unless otherwise noted)
■ Guaranteed 3.0V and 5.0V performance
■ Low power supply current
— LMV651
116 μA
— LMV652
118 μA per amplifier
— LMV654
122 μA per amplifier
12 MHz
■ High unity gain bandwidth
1.5 mV
■ Max input offset voltage
100 dB
■ CMRR
95 dB
■ PSRR
17 nV/
■ Input referred voltage noise
120 mV from rail
■ Output swing with 2 kΩ load
0.003% @ 1 kHz, 2 kΩ
■ Total harmonic distortion
−40°C to 125°C
■ Temperature range
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High Gain Wide Bandwidth Inverting Amplifier
© 2007 National Semiconductor Corporation
201238
Applications
■
■
■
■
Portable equipment
Automotive
Battery powered systems
Sensors and Instrumentation
20123806
Open Loop Gain and phase vs. Frequency
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LMV651/LMV652/LMV654 12 MHz, Low Voltage, Low Power Amplifier
March 2007
LMV651/LMV652/LMV654
Soldering Information
Absolute Maximum Ratings (Note 1)
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales Office/
Distributors for availability and specifications.
ESD Tolerance (Note 2)
Human Body Model
Machine Model
Differential Input VID
Supply Voltage (VS = V+ - V−)
Input/Output Pin Voltage
Storage Temperature Range
Junction Temperature (Note 3)
Infrared or Convection (20 sec)
235°C
Wave Soldering Lead Temp (10
sec)
260°C
Operating Ratings
2000V
(Note 1)
Temperature Range (Note 3)
Supply Voltage
100V
±0.3V
6V
V+ +0.3V, V− −0.3V
−65°C to +150°C
+150°C
−40°C to 125°C
2.7V to 5.5V
Package Thermal Resistance (θJA)(Note 3)
5-Pin SC70
14-Pin TSSOP
456°C/W
160°C/W
3V DC Electrical Characteristics
Unless otherwise specified, all limits are guaranteed for TA = 25°C, V+ = 3V, V− = 0V, VO = VCM = V+/2, and RL > 1 MΩ. Boldface limits apply at the temperature extremes.
Symbol
Parameter
VOS
Input Offset Voltage
TC VOS
Input Offset Average Drift
IB
Input Bias Current
IOS
Input Offset Current
CMRR
Common Mode Rejection Ratio
PSRR
Power Supply Rejection Ratio
Conditions
Min
(Note 5)
±1.5
2.7
mV
μV/°C
80
120
nA
2.2
15
nA
0 ≤ VCM≤ 2.0 V
dB
3.0 ≤ V+ ≤ 5V, VCM = 0.5
87
81
95
dB
2.7 ≤ V+ ≤ 5.5V, VCM = 0.5
87
81
95
0
0
AVOL
Large Signal Voltage Gain
0.3 ≤ VO ≤ 2.7, RL = 2 kΩ to V+/2
CMRR ≥ 60 dB
0.4 ≤ VO ≤ 2.6, RL = 2 kΩ to
V+/2
0.3 ≤ VO ≤ 2.7, RL = 10 kΩ to V+/2
0.4 ≤ VO ≤ 2.6, RL = 10 kΩ to V+/2
2.1
2.1
80
76
85
86
83
93
80
95
120
RL = 10 kΩ to V+/2
45
50
60
RL = 2 kΩ to V+/2
95
110
125
RL = 10 kΩ to V+/2
60
65
75
Maximum Continuous Output
Current
Sourcing (Note 8)
17
Sinking (Note 8)
25
Supply Current per Amplifier
LMV651
115
LMV652
118
LMV654
122
AV = +1,
10% to 90% (Note 7)
3.0
SR
Slew Rate
GBW
Gain Bandwidth Product
en
Input-Referred Voltage Noise
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f = 100 kHz
17
f = 1 kHz
17
2
V
dB
RL = 2 kΩ to V+/2
Output Swing Low
IS
0.1
100
CMRR ≥ 75 dB
ISC
Units
87
80
Input Common-Mode Voltage
Range
Output Swing High
Max
(Note 5)
6.6
(Note 6)
CMVR
VO
Typ
(Note 4)
mV from
rail
mA
140
175
μA
V/μs
MHz
nV/
in
Parameter
Input-Referred Current Noise
THD
Total Harmonic Distortion
Conditions
Min
(Note 5)
Typ
(Note 4)
f = 100 kHz
0.1
f = 1 kHz
0.15
f = 1 kHz, AV = 2, RL = 2 kΩ
0.003
Max
(Note 5)
Units
pA/
%
5V DC Electrical Characteristics
Unless otherwise specified, all limits are guaranteed for TJ = 25°C, V+ = 5V, V− = 0V,VO = VCM = V+/2, and RL > 1 MΩ. Boldface
limits apply at the temperature extremes.
Symbol
Parameter
Conditions
Min
(Note 5)
Typ
(Note 4)
Max
(Note 5)
Units
±1.5
2.7
mV
VOS
Input Offset Voltage
0.1
TC VOS
Input Offset Average Drift
6.6
IB
Input Bias Current
IOS
Input Offset Current
CMRR
Common Mode Rejection Ratio
0 ≤ VCM≤ 4.0 V
90
83
100
dB
PSRR
Power Supply Rejection Ratio
3V ≤ V+ ≤ 5V, VCM = 0.5V
87
81
95
dB
2.7V ≤ V+ ≤ 5.5V, VCM = 0.5V
87
81
95
(Note 6)
80
120
nA
2.2
15
nA
CMVR
Input Common-Mode Voltage
Range
CMRR ≥ 80 dB
0
0
AVOL
Large Signal Voltage Gain
0.3 ≤ VO ≤ 4.7V, RL = 2 kΩ to V+/2
79
76
84
0.3 ≤ VO ≤ 4.7V, RL = 10 kΩ to V+/2
87
84
94
CMRR ≥ 68 dB
0.4 ≤ VO ≤ 4.6, RL = 2 kΩ to V+/2
0.4 ≤ VO ≤ 4.6, RL = 10 kΩ to V+/2
VO
Output Swing High
IS
dB
140
185
RL = 10 kΩ to V+/2
75
90
120
RL = 2 kΩ to V+/2
110
130
150
RL = 10 kΩ to V+/2
70
80
95
Maximum Continuous Output
Current
Sourcing (Note 8)
18.5
Sinking (Note 8)
25
Supply Current per Amplifier
LMV651
116
LMV652
118
LMV654
122
AV = +1, VO = 1 VPP
10% to 90% (Note 7)
3.0
V/μs
12
MHz
Slew Rate
GBW
Gain Bandwidth Product
en
Input-Referred Voltage Noise
THD
V
120
SR
in
4.1
4.1
RL = 2 kΩ to V+/2
Output Swing Low
ISC
μV/°C
Input-Referred Current Noise
Total Harmonic Distortion
f = 100 kHz
17
f = 1 kHz
17
f = 100 kHz
0.1
f = 1 kHz
0.15
f = 1 kHz, AV = 2, RL = 2 kΩ
0.003
3
mV from
rail
mA
140
175
μA
nV/
pA/
%
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LMV651/LMV652/LMV654
Symbol
LMV651/LMV652/LMV654
Note 1: Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for which the device is
intended to be functional, but specific performance is not guaranteed. For guaranteed specifications and the test conditions, see the Electrical Characteristics
Tables.
Note 2: Human Body Model, applicable std. MIL-STD-883, Method 3015.7. Machine Model, applicable std. JESD22-A115-A (ESD MM std. of JEDEC)
Field-Induced Charge-Device Model, applicable std. JESD22-C101-C (ESD FICDM std. of JEDEC).
Note 3: The maximum power dissipation is a function of TJ(MAX, θJA, and TA. The maximum allowable power dissipation at any ambient temperature is
PD = (TJ(MAX) - TA)/ θJA. All numbers apply for packages soldered directly onto a PC board.
Note 4: Typical values represent the most likely parametric norm as determined at the time of characterization. Actual typical values may vary over time and will
also depend on the application and configuration. The typical values are not tested and are not guaranteed on shipped production material.
Note 5: Limits are 100% production tested at 25°C. Limits over the operating temperature range are guaranteed through correlations using Statistical Quality
Control (SQC) method.
Note 6: Positive current corresponds to current flowing into the device.
Note 7: Slew rate is the average of the rising and falling slew rates.
Note 8: The part is not short circuit protected and is not recommended for operation with low resistive loads. Typical sourcing and sinking output current curves
are provided in the Typical Performance Characteristics and should be consulted before designing for heavy loads.
Connection Diagrams
5-Pin SC70
8-Pin MSOP
14-Pin TSSOP
20123802
Top View
20123803
Top View
20123804
Top View
Ordering Information
Package
5-Pin SC70
8-Pin MSOP
14-Pin TSSOP
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Part Number
LMV651MG
LMV651MGX
LMV652MM
LMV652MMX
LMV654MT
LMV654MTX
Package Marking
Transport Media
1k Units Tape and Reel
A93
3k Units Tape and Reel
1k Units Tape and Reel
AB3A
3.5k Units Tape and Reel
94 Units/Rail
LMV654MT
2.5k Units Tape and Reel
4
NSC Drawing
MAA05A
MUA08A
MTC14
Unless otherwise Specified, TA= 25°C, VS= 5V, V+= 5V, V−= 0V,
VCM= VS/2
Supply Current vs. Supply Voltage (LMV651)
Supply Current per Channel vs. Supply Voltage (LMV652)
20123865
20123834
Supply Current per Channel vs. Supply Voltage (LMV654)
VOS vs. VCM
20123864
20123825
VOS vs. VCM
VOS vs. Supply Voltage
20123826
20123821
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LMV651/LMV652/LMV654
Typical Performance Characteristics
LMV651/LMV652/LMV654
IBIAS vs. VCM
IBIAS vs. VCM
20123823
20123824
IBIAS vs. Supply Voltage
Positive Output Swing vs. Supply Voltage
20123822
20123828
Negative Output Swing vs. Supply Voltage
Positive Output Swing vs. Supply Voltage
20123829
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20123827
6
LMV651/LMV652/LMV654
Negative Output Swing vs. Supply Voltage
Sourcing Current vs. Output Voltage
20123832
20123830
Sinking Current vs. Output Voltage (LMV651)
Sinking Current vs. Output Voltage (LMV652)
20123833
20123866
Sinking Current vs. Output Voltage (LMV654)
Open Loop Gain and Phase with Capacitive Load
20123863
20123811
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LMV651/LMV652/LMV654
Open Loop Gain and Phase with Resistive Load
Phase Margin vs. Capacitive Load (Stability)
20123812
20123813
Input Referred Voltage Noise vs. Frequency
Input Referred Current Noise vs. Frequency
20123814
20123815
Slew Rate vs. Supply Voltage
THD+N vs. VOUT
20123809
20123816
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LMV651/LMV652/LMV654
THD+N vs. VOUT
THD+N vs. Frequency
20123807
20123810
THD+N vs. Frequency
Small Signal Transient Response
20123818
20123808
Small Signal Transient Response
Large Signal Transient Response
20123817
20123819
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LMV651/LMV652/LMV654
PSRR vs. Frequency
CMRR vs. Frequency
20123835
20123836
Closed Loop Output Impedance vs. Frequency
20123837
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LMV651/LMV652/LMV654
Application Information
ADVANTAGES OF THE LMV651/LMV652/LMV654
Low Voltage and Low Power Operation
The LMV651/LMV652/LMV654 have performance guaranteed at supply voltages of 3V and 5V. These parts are guaranteed to be operational at all supply voltages between 2.7V
and 5.5V. The LMV651 draws a low supply current of 116
μA, the LMV652 draws 118 μA/channel and the LMV654
draws 122 μA/channel. This family of op amps provides the
low voltage and low power amplification which is essential for
portable applications.
Wide Bandwidth
Despite drawing the very low supply current of 116 µA, the
LMV651/LMV652/LMV654 manage to provide a wide unity
gain bandwidth of 12 MHz. This is easily one of the best
bandwidth to power ratios ever achieved, and allows these op
amps to provide wideband amplification while using the minimum amount of power. This makes this family of parts ideal
for low power signal processing applications such as portable
media players and other accessories.
20123859
FIGURE 1. Gain vs. Frequency for an Op Amp
An op amp, ideally, has a dominant pole close to DC, which
causes its gain to decay at the rate of 20 dB/decade with respect to frequency. If this rate of decay, also known as the
rate of closure (ROC), remains the same until the op amp's
unity gain bandwidth, the op amp is stable. If, however, a large
capacitance is added to the output of the op amp, it combines
with the output impedance of the op amp to create another
pole in its frequency response before its unity gain frequency
( Figure 1 ). This increases the ROC to 40 dB/decade and
causes instability.
In such a case a number of techniques can be used to restore
stability to the circuit. The idea behind all these schemes is to
modify the frequency response such that it can be restored to
an ROC of 20 dB/decade, which ensures stability.
Low Input Referred Noise
The LMV651/LMV652/LMV654 provide a flatband input re, which is signififerred voltage noise density of 17 nV/
cantly better than the noise performance expected from a low
power op amp. These op amps also feature exceptionally low
1/f noise, with a very low 1/f noise corner frequency of 4 Hz.
This makes these parts ideal for low power applications which
require decent noise performance, such as PDAs and
portable sensors.
Ground Sensing and Rail-to-Rail Output
The LMV651/LMV652/LMV654 each have a rail-to-rail output
stage, which provides the maximum possible output dynamic
range. This is especially important for applications requiring
a large output swing. The input common mode range of this
family of devices includes the negative supply rail which allows direct sensing at ground in a single supply operation.
In The Loop Compensation
Figure 2 illustrates a compensation technique, known as ‘in
the loop’ compensation, that employs an RC feedback circuit
within the feedback loop to stabilize a non-inverting amplifier
configuration. A small series resistance, RS, is used to isolate
the amplifier output from the load capacitance, CL, and a small
capacitance, CF, is inserted across the feedback resistor to
bypass CL at higher frequencies.
Small Size
The small footprint of the packages for the LMV651/LMV652/
LMH654 saves space on printed circuit boards, and enables
the design of smaller and more compact electronic products.
Long traces between the signal source and the op amp make
the signal path susceptible to noise. By using a physically
smaller package, these op amps can be placed closer to the
signal source, reducing noise pickup and enhancing signal
integrity.
STABILITY OF OP AMP CIRCUITS
Stability and Capacitive Loading
If the phase margin of the LMV651/LMV652/LMV654 is plotted with respect to the capacitive load (CL) at its output, it is
seen that the phase margin reduces significantly if CL is increased beyond 100 pF. This is because the op amp is
designed to provide the maximum bandwidth possible for a
low supply current. Stabilizing it for higher capacitive loads
would have required either a drastic increase in supply current, or a large internal compensation capacitance, which
would have reduced the bandwidth of the op amp. Hence, if
these devices are to be used for driving higher capacitive
loads, they would have to be externally compensated.
20123858
FIGURE 2. In the Loop Compensation
11
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LMV651/LMV652/LMV654
The values for RS and CF are decided by ensuring that the
zero attributed to CF lies at the same frequency as the pole
attributed to CL. This ensures that the effect of the second
pole on the transfer function is compensated for by the presence of the zero, and that the ROC is maintained at 20 dB/
decade. For the circuit shown in Figure 2 the values of RS and
CF are given by Equation 1. Values of RS and CF required for
maintaining stability for different values of CL, as well as the
phase margins obtained, are shown in Table 1. RF and RIN
are taken to be 10 kΩ, RL is 2 kΩ, while ROUT is taken as
340Ω.
than 0.003% distortion. Two amplifier circuits are shown in
Figure 4 and Figure 5. Figure 4 is an inverting amplifier, with
a 100 kΩ feedback resistor, R2, and a 1 kΩ input resistor,
R1, and provides a gain of −100. With the LMV651/LMV652/
LMV654 these circuits can provide gain of −100 with a −3 dB
bandwidth of 120 kHz, for a quiescent current as low as 116
μA. Similarly, the circuit in Figure 5, a non-inverting amplifier
with a gain of 1001, can provide that gain with a −3 dB bandwidth of 12 kHz, for a similar low quiescent power dissipation.
Coupling capacitors CC1 and CC2 can be added to isolate the
circuit from DC voltages, while RB1 and RB2 provide DC biasing. A feedback capacitor CF can also be added to improve
compensation.
(1)
TABLE 1.
CL (pF)
RS (Ω)
CF (pF)
Phase Margin (°)
150
340
15
39.4
200
340
20
34.6
250
340
25
31.1
Although this methodology provides circuit stability for any
load capacitance, it does so at the price of bandwidth. The
closed loop bandwidth of the circuit is now limited by RF and
CF.
Compensation By External Resistor
In some applications it is essential to drive a capacitive load
without sacrificing bandwidth. In such a case, in the loop compensation is not viable. A simpler scheme for compensation
is shown in Figure 3. A resistor, RISO, is placed in series between the load capacitance and the output. This introduces a
zero in the circuit transfer function, which counteracts the effect of the pole formed by the load capacitance, and ensures
stability. The value of RISO to be used should be decided depending on the size of CL and the level of performance desired. Values ranging from 5Ω to 50Ω are usually sufficient to
ensure stability. A larger value of RISO will result in a system
with lesser ringing and overshoot, but will also limit the output
swing and the short circuit current of the circuit.
20123861
FIGURE 4. High Gain Inverting Amplifier
20123862
FIGURE 5. High Gain Non-Inverting Amplifier
20123860
FIGURE 3. Compensation by Isolation Resistor
ACTIVE FILTERS
With a wide unity gain bandwidth of 12 MHz, low input referred
noise density and a low power supply current, the LMV651/
LMV652/LMV654 are well suited for low-power filtering applications. Active filter topologies, like the Sallen-Key low pass
filter shown in Figure 6, are very versatile, and can be used
to design a wide variety of filters (Chebyshev, Butterworth or
Bessel). The Sallen-Key topology, in particular, can be used
to attain a wide range of Q, by using positive feedback to reject the undesired frequency range.
Typical Applications
HIGH GAIN LOW POWER AMPLIFIERS
With a low supply current, low power operation, and low harmonic distortion, the LMV651/LMV652/LMV654 are ideal for
wide-bandwidth, high gain amplification. The wide unity gain
bandwidth allows these parts to provide large gain over a wide
frequency range, while driving loads as low as 2 kΩ with less
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12
LMV651/LMV652/LMV654
In the circuit shown in Figure 6, the two capacitors appear as
open circuits at lower frequencies and the signal is simply
buffered to the output. At high frequencies the capacitors appear as short circuits and the signal is shunted to ground by
one of the capacitors before it can be amplified. Near the cutoff frequency, where the impedance of the capacitances is on
the same order as Rg and Rf, positive feedback through the
other capacitor allows the circuit to attain the desired Q. The
ratio of the two resistors, m2, provides a knob to control the
value of Q obtained.
20123820
FIGURE 6.
13
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LMV651/LMV652/LMV654
Physical Dimensions inches (millimeters) unless otherwise noted
5-Pin SC70
NS Package Number MAA05A
8-Pin MSOP
NS Package Number MUA08A
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14
LMV651/LMV652/LMV654
14-Pin TSSOP
NS Package Number MTC14
15
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LMV651/LMV652/LMV654 12 MHz, Low Voltage, Low Power Amplifier
Notes
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