Micrel MIC23150 4mhz pwm 2a buck regulator with hyperlight load Datasheet

MIC23150
4MHz PWM 2A Buck Regulator with
HyperLight Load™
General Description
Features
The MIC23150 is a high efficiency 4MHz 2A synchronous
buck regulator with HyperLight Load™ mode. HyperLight
Load™ provides very high efficiency at light loads and
ultra-fast transient response which is perfectly suited for
supplying processor core voltages. An additional benefit
of this proprietary architecture is very low output ripple
voltage throughout the entire load range with the use of
small output capacitors. The tiny 2mm x 2mm Thin MLF®
package saves precious board space and requires only
three external components.
The MIC23150 is designed for use with a very small
inductor, down to 0.47µH, and an output capacitor as small
as 2.2 µF that enables a total solution size, less than 1mm
height.
The MIC23150 has a very low quiescent current of 23µA
and achieves a peak efficiency of 93% in continuous
conduction mode. In discontinuous conduction mode, the
MIC23150 can achieve 87% efficiency at 1mA.
The MIC23150 is available in 8-pin 2mm x 2mm Thin
MLF® package with an operating junction temperature
range from –40°C to +125°C.
Datasheets and support documentation can be found on
Micrel’s web site at: www.micrel.com.
•
•
•
•
•
•
•
•
•
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•
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HyperLight Load™
Input voltage: 2.7V to 5.5V
2A output current
Up to 93% peak efficiency
87% typical efficiency at 1mA
23µA typical quiescent current
4MHz PWM operation in continuous mode
Ultra fast transient response
Low ripple output voltage
− 14mVpp ripple in HyperLight Load™ mode
− 5mV output voltage ripple in full PWM mode
Fully integrated MOSFET switches
0.01µA shutdown current
Thermal shutdown and current limit protection
Output Voltage as low as 0.95V
8-pin 2mm x 2mm Thin MLF®
–40°C to +125°C junction temperature range
Applications
• Mobile handsets
• Portable media/MP3 players
• Portable navigation devices (GPS)
• WiFi/WiMax/WiBro modules
• Solid State Drives/Memory
• Wireless LAN cards
• Portable applications
____________________________________________________________________________________________________________
Typical Application
U1 MIC23150
L1
VIN
VIN
C1
EN
SW
2mm×2mm
ThinMLF SNS
VOUT
100
Efficiency
V
= 1.8V
OUT
VIN = 2.7V
V = 3.0V
IN
V = 3.6V
IN
90
C2
80
70
EN
60
AGND
PGND
GND
50
GND
40
11
L = 1.0µH
C
= 4.7µF
OUT
0
100
1000 10000
OUTPUT CURRENT (mA)
HyperLight Load is a trademark of Micrel, Inc.
MLF and MicroLeadFrame are registered trademark Amkor Technology Inc.
Micrel Inc. • 2180 Fortune Drive • San Jose, CA 95131 • USA • tel +1 (408) 944-0800 • fax + 1 (408) 474-1000 • http://www.micrel.com
February 2009
M9999-082908-A
Micrel Inc.
MIC23150
Ordering Information
Part Number
Marking
Code
Nominal Output
Voltage
Junction
Temp. Range
Package
Lead Finish
MIC23150-CYMT
QKC
1.0V
-40°C to +125°C
8-Pin 2mm x 2mm Thin MLF®
Pb-Free
MIC23150-4YMT
QK4
1.2V
-40°C to +125°C
8-Pin 2mm x 2mm Thin MLF®
Pb-Free
8-Pin 2mm x 2mm Thin MLF
®
Pb-Free
8-Pin 2mm x 2mm Thin MLF
®
Pb-Free
MIC23150-GYMT
MIC23150-SYMT
QKG
1.8V
QKS
3.3V
–40°C to +125°C
–40°C to +125°C
Notes:
1. Other options available (0.95V - 3.6V). Contact Micrel Marketing for details.
®
2. Thin MLF is GREEN RoHS compliant package. Lead finish is NiPdAu. Mold compound is Halogen Free.
®
3. Thin MLF ▲ = Pin 1 identifier.
Pin Configuration
SW
1
8
PGND
SW
2
7
VIN
EN
3
6
VIN
SNS
4
5
AGND
(Top View)
2mm x 2mm Thin MLF (MT)
Pin Description
Pin Number
Pin Name
1,2
SW
Switch (Output): Internal power MOSFET output switches.
3
EN
Enable (Input): Logic high enables operation of the regulator. Logic low
will shut down the device. Do not leave floating.
4
SNS
5
AGND
February 2009
6,7
VIN
8
PGND
Pin Function
Sense: Connect to VOUT as close to output capacitor as possible to sense
output voltage.
Analog Ground: Connect to central ground point where all high current
paths meet (CIN, COUT, PGND) for best operation.
Input Voltage: Connect a capacitor-to-ground to decouple the noise.
Power Ground.
2
M9999-082908-A
Micrel Inc.
MIC23150
Absolute Maximum Ratings(1)
Operating Ratings(2)
Supply Voltage (VIN) . ……………………………………….6V
Sense (VSNS).. ..................................................................6V
Output Switch Voltage (VSW) ............................................6V
Enable Input Voltage (VEN).. ..............................-0.3V to VIN
Storage Temperature Range .. ……………-65°C to +150°C
ESD Rating(3) ..................................................................2kV
Supply Voltage (VIN)... …………………………..2.7V to 5.5V
Enable Input Voltage (VEN) .. ……………………….0V to VIN
Junction Temperature Range (TJ)... ….-40°C ≤ TJ ≤ +125°C
Thermal Resistance
2mm x 2mm Thin MLF-8 (θJA) ...........................90°C/W
Electrical Characteristics(4)
TA = 25°C; VIN = VEN = 3.6V; L = 1.0µH; COUT = 4.7µF unless otherwise specified.
Bold values indicate –40°C ≤ TJ ≤ +125°C, unless noted.
Parameter
Condition
Min
Supply Voltage Range
Under-Voltage Lockout Threshold
2.7
(turn-on)
2.45
Under-Voltage Lockout Hysteresis
IOUT = 0mA , SNS > 1.2 * VOUT Nominal
Shutdown Current
VEN = 0V; VIN = 5.5V
VIN = 3.6V if VOUTNOM < 2.5V, ILOAD = 20mA
VIN = 4.5V if VOUTNOM ≥ 2.5V, ILOAD = 20mA
Current Limit
SNS = 0.9*VOUTNOM
Output Voltage Line Regulation
VIN = 3.6V to 5.5V if VOUTNOM < 2.5V, ILOAD = 20mA
VIN = 4.5V to 5.5V if VOUTNOM ≥ 2.5V, ILOAD = 20mA
20mA < ILOAD < 500mA, VIN = 3.6V if VOUTNOM < 2.5V
20mA < ILOAD < 500mA, VIN = 5.0V if VOUTNOM ≥ 2.5V
Output Voltage Load Regulation
PWM Switch ON-Resistance
2.55
Max
Units
5.5
V
2.65
75
Quiescent Current
Output Voltage Accuracy
Typ
23
40
µA
0.01
5
µA
+2.5
%
-2.5
2.2
3.4
A
0.3
%/V
0.75
%/A
ISW = 100mA PMOS
0.150
ISW = -100mA NMOS
0.110
Switching Frequency
IOUT = 120mA
SoftStart Time
VOUT = 90%
Enable Threshold
Turn-On
V
mV
Ω
4
MHz
115
µs
0.8
1.2
V
Enable Input Current
0.1
2
µA
Over-temperature Shutdown
160
°C
Over-temperature Shutdown
Hysteresis
20
°C
0.5
Notes:
1. Exceeding the absolute maximum rating may damage the device.
2. The device is not guaranteed to function outside its operating rating.
3. Devices are ESD sensitive. Handling precautions recommended. Human body model, 1.5kΩ in series with 100pF.
4. Specification for packaged product only.
February 2009
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MIC23150
Typical Characteristics
OUT
February 2009
OUTPUT VOLTAGE (V)
1.81
1.80
1.79
1.78
L =1.0µH
1.77 C
= 4.7µF
OUT
1.76
LOAD = 120mA
1.75
TEMPERATURE (°C)
4
3.2 3.7 4.2 4.7 5.2
INPUT VOLTAGE (V)
5.7
Output Voltage
vs Output Current
V = 5.5V
IN
1.86
V = 4.2V
V = 3.6V
1.84 IN
IN
1.82
1.8
1.78
V
IN
= 2.7V
1.76 L = 1.0µH
1.74 V
= 1.8V
OUT
1.72 C
= 4.7µF
OUT
1.7
0.1
1
10
100 1000 10000
OUTPUT CURRENT (mA)
Enable Thresold
vs. Temperature
1.2
1.82
-20
120
1.6
2.7
Output Voltage
vs. Temperature
1.83
-40
OUTPUT VOLTAGE (V)
TEMPERATURE (°C)
100
80
60
40
20
0
-20
3.9
V = 3.6V
3.8 IN
L =1.0µH
3.7
C
= 4.7µF
3.6 OUT
LOAD = 120mA
3.5
-40
SWITCHING FREQUENCY (MHz)
4.0
= 4.7µF
10
100
1000 10000
OUTPUT CURRENT (mA)
1.85
1.84
4.1
1.7
1.65
VIN = 2.7V
ENABLE ON
VIN = 3.6V
1.0
VIN = 5.5V
0.8
ENABLE OFF
0.6
0.4
L = 1.0µH
0.2 COUT = 4.7µF
0
120
C
4.5
4.4
4.2
= 4.2V
L = 1.0µH
= 1.8V
V
Switching Frequency
vs. Temperature
4.3
= 3.6V
OUT
0.001
1
1.75 Load = 1000mA Load = 1500mA
1.9
1.88
0.1
0.01
Load = 200mA Load = 600mA
80
IN
1.8
100
V
Output Voltage
vs. Input Voltage
60
5.7
IN
= 1.8V
1
10
100 1000 10000
OUTPUT CURRENT (mA)
40
3.2 3.7 4.2 4.7 5.2
INPUT VOLTAGE (V)
V
OUT
0
1.6
2.7
IN
= 3.6V
COUT = 4.7µF
20
1.65
1
= 3.0V
IN
1.9
1.85
ENABLE THRESHOLD (V)
1.7
V
120
Load = 1mA
Load = 100mA
10
V
1.95
5.7
Switching Frequency
vs Output Current
80
Load = 10mA
10 Not Switching
L = open
5
= 1.2V × V
V
OUT
NOM
0
2.7 3.2 3.7 4.2 4.7 5.2
INPUT VOLTAGE (V)
100
1.9
15
60
1.95
-40°C
L = 2.2µH
V
-20
Output Voltage
vs. Input Voltage
25°C 125°C
25
20
65
60
55
50
0.1
OUTPUT VOLTAGE (V)
5.7
30
L = 1.5µH
75
70
2
35
40
2.8
2.6
2.4
L = 1.0µH
2.2 C
= 4.7µF
OUT
2.0
2.7 3.2 3.7 4.2 4.7 5.2
INPUT VOLTAGE (V)
= 5.5V
Quiescent Current
vs. Input Voltage
40
3.4
3.2
3.0
1.75
IN
L = 1.0µH
L = 0.68µH
90
85
80
-40
EFFICIENCY (%)
Current Limit
vs. Input Voltage
1.85
V
50 L = 1.0µH
= 4.7µF
C
OUT
40
0.1
1
10
100 1000 10000
OUTPUT CURRENT (mA)
1
10
100 1000 10000
OUTPUT CURRENT (mA)
2
VIN = 5.0V
60
L = 1.0µH
COUT = 4.7µF
4.0
3.8
3.6
1.8
70
QUIESCENT CURRENT (µA)
CURRENT LIMIT (A)
40
0.1
80
0
50
OUTPUT VOLTAGE (V)
VIN = 5.5V
VIN = 5.0V
SWITCHING FREQUENCY (MHz)
EFFICIENCY (%)
70
Efficiency with
Various Inductors
100
95
VIN = 4.2V
90
80
VIN = 4.2V
OUT
100
VIN = 3.6V
90
60
Efficiency
= 3.3V
V
20
OUT
100
VIN = 3.0V
VIN = 2.7V
EFFICIENCY (%)
Efficiency
= 1.8V
V
TEMPERATURE (°C)
M9999-082908-A
Micrel Inc.
MIC23150
Functional Characteristics
February 2009
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Micrel Inc.
February 2009
MIC23150
6
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Micrel Inc.
MIC23150
Functional Characteristics (cont.)
February 2009
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Micrel Inc.
MIC23150
Functional Characteristics (cont.)
February 2009
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MIC23150
Functional Diagram
VIN
EN
CONTROL
LOGIC
Timer &
Softstart
UVLO
Gate
Drive
Reference
SW
Current
Limit
ZERO 1
ERROR
COMPARATOR
ISENSE
PGND
SNS
AGND
Figure 1. Simplified MIC23150 Functional Block Diagram
February 2009
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MIC23150
Functional Description
SNS
The sense (SNS) pin is connected to the output of the
device to provide feedback to the control circuitry. The
SNS connection should be placed close to the output
capacitor. Refer to the layout recommendations for more
details.
VIN
The input supply (VIN) provides power to the internal
MOSFETs for the switch mode regulator along with the
internal control circuitry. The VIN operating range is 2.7V
to 5.5V so an input capacitor, with a minimum voltage
rating of 6.3V, is recommended. Due to the high
switching speed, a minimum 2.2µF bypass capacitor
placed close to VIN and the power ground (PGND) pin is
required. Refer to the layout recommendations for
details.
AGND
The analog ground (AGND) is the ground path for the
biasing and control circuitry. The current loop for the
signal ground should be separate from the power ground
(PGND) loop. Refer to the layout recommendations for
more details.
EN
A logic high signal on the enable pin activates the output
voltage of the device. A logic low signal on the enable
pin deactivates the output and reduces supply current to
0.01µA. MIC23150 features built-in soft-start circuitry
that reduces in-rush current and prevents the output
voltage from overshooting at start up. Do not leave the
EN pin floating.
PGND
The power ground pin is the ground path for the high
current in PWM mode. The current loop for the power
ground should be as small as possible and separate
from the analog ground (AGND) loop as applicable.
Refer to the layout recommendations for more details.
SW
The switch (SW) connects directly to one end of the
inductor and provides the current path during switching
cycles. The other end of the inductor is connected to the
load, SNS pin and output capacitor. Due to the high
speed switching on this pin, the switch node should be
routed away from sensitive nodes whenever possible.
February 2009
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Micrel Inc.
MIC23150
in inductance. Ensure the inductor selected can handle
the maximum operating current. When saturation current
is specified, make sure that there is enough margin so
that the peak current does not cause the inductor to
saturate. Peak current can be calculated as follows:
Application Information
The MIC23150 is a high performance DC-to-DC step
down regulator offering a small solution size. Supporting
an output current up to 2A inside a tiny 2mm x 2mm Thin
MLF® package, the IC requires only three external
components while meeting today’s miniature portable
electronic device needs. Using the HyperLight Load™
switching scheme, the MIC23150 is able to maintain
high efficiency throughout the entire load range while
providing ultra-fast load transient response. The
following sections provide additional device application
information.
⎡
⎛ 1 − VOUT /VIN ⎞⎤
I PEAK = ⎢IOUT + VOUT ⎜
⎟⎥
⎝ 2 × f × L ⎠⎦
⎣
As shown by the calculation above, the peak inductor
current is inversely proportional to the switching
frequency and the inductance; the lower the switching
frequency or the inductance the higher the peak current.
As input voltage increases, the peak current also
increases.
The size of the inductor depends on the requirements of
the application. Refer to the Typical Application Circuit
and Bill of Materials for details.
DC resistance (DCR) is also important. While DCR is
inversely proportional to size, DCR can represent a
significant efficiency loss. Refer to the Efficiency
Considerations.
Input Capacitor
A 2.2µF ceramic capacitor or greater should be placed
close to the VIN pin and PGND pin for bypassing. A TDK
C1608X5R0J475K, size 0603, 4.7µF ceramic capacitor
is recommended based upon performance, size and
cost. A X5R or X7R temperature rating is recommended
for the input capacitor. Y5V temperature rating
capacitors, aside from losing most of their capacitance
over temperature, can also become resistive at high
frequencies. This reduces their ability to filter out high
frequency noise.
Compensation
The MIC23150 is designed to be stable with a 0.47µH to
2.2µH inductor with a minimum of 2.2µF ceramic (X5R)
output capacitor.
Output Capacitor
The MIC23150 is designed for use with a 2.2µF or
greater ceramic output capacitor. Increasing the output
capacitance will lower output ripple and improve load
transient response but could also increase solution size
or cost. A low equivalent series resistance (ESR)
ceramic output capacitor such as the TDK
C1608X5R0J475K, size 0603, 4.7µF ceramic capacitor
is recommended based upon performance, size and
cost. Both the X7R or X5R temperature rating capacitors
are recommended. The Y5V and Z5U temperature rating
capacitors are not recommended due to their wide
variation in capacitance over temperature and increased
resistance at high frequencies.
Duty Cycle
The typical maximum duty cycle of the MIC23150 is
80%.
Efficiency Considerations
Efficiency is defined as the amount of useful output
power, divided by the amount of power supplied.
⎛V
×I
Efficiency % = ⎜⎜ OUT OUT
⎝ VIN × IIN
Maintaining high efficiency serves two purposes. It
reduces power dissipation in the power supply, reducing
the need for heat sinks and thermal design
considerations and it reduces consumption of current for
battery-powered applications. Reduced current draw
from a battery increases the devices operating time and
is critical in hand held devices.
There are two types of losses in switching converters;
DC losses and switching losses. DC losses are simply
the power dissipation of I2R. Power is dissipated in the
high side switch during the on cycle. Power loss is equal
to the high side MOSFET RDSON multiplied by the Switch
Current squared. During the off cycle, the low side Nchannel MOSFET conducts, also dissipating power.
Device operating current also reduces efficiency. The
product of the quiescent (operating) current and the
supply voltage represents another DC loss. The current
required driving the gates on and off at a constant 4MHz
frequency and the switching transitions make up the
switching losses.
Inductor Selection
When selecting an inductor, it is important to consider
the following factors (not necessarily in the order of
importance):
•
Inductance
•
Rated current value
•
Size requirements
•
DC resistance (DCR)
The MIC23150 is designed for use with a 0.47µH to
2.2µH inductor. For faster transient response, a 0.47µH
inductor will yield the best result. For lower output ripple,
a 2.2µH inductor is recommended.
Maximum current ratings of the inductor are generally
given in two methods; permissible DC current and
saturation current. Permissible DC current can be rated
either for a 40°C temperature rise or a 10% to 20% loss
February 2009
⎞
⎟ × 100
⎟
⎠
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M9999-082908-A
Micrel Inc.
MIC23150
100
EFFICIENCY (%)
90
the error comparator turns the PMOS off for a minimumoff-time until the output drops below the threshold. The
NMOS acts as an ideal rectifier that conducts when the
PMOS is off. Using a NMOS switch instead of a diode
allows for lower voltage drop across the switching device
when it is on. The asynchronous switching combination
between the PMOS and the NMOS allows the control
loop to work in discontinuous mode for light load
operations. In discontinuous mode, the MIC23150 works
in pulse frequency modulation (PFM) to regulate the
output. As the output current increases, the off-time
decreases, thus provides more energy to the output.
This switching scheme improves the efficiency of
MIC23150 during light load currents by only switching
when it is needed. As the load current increases, the
MIC23150 goes into continuous conduction mode (CCM)
and switches at a frequency centered at 4MHz. The
equation to calculate the load when the MIC23150 goes
into continuous conduction mode may be approximated
by the following formula:
Efficiency
= 1.8V
V
VIN = 2.7V
OUT
VIN = 3.0V
VIN = 3.6V
80
70
60
50
40
0.1
VIN = 4.2V
VIN = 5.0V
VIN = 5.5V
L = 1.0µH
COUT = 4.7µF
1
10
100 1000 10000
OUTPUT CURRENT (mA)
Figure 2. Efficiency Under Load
The figure above shows an efficiency curve. From no
load to 100mA, efficiency losses are dominated by
quiescent current losses, gate drive and transition
losses. By using the HyperLight Load™ mode, the
MIC23150 is able to maintain high efficiency at low
output currents.
Over 100mA, efficiency loss is dominated by MOSFET
RDSON and inductor losses. Higher input supply voltages
will increase the Gate-to-Source threshold on the
internal MOSFETs, thereby reducing the internal RDSON.
This improves efficiency by reducing DC losses in the
device. All but the inductor losses are inherent to the
device. In which case, inductor selection becomes
increasingly critical in efficiency calculations. As the
inductors are reduced in size, the DC resistance (DCR)
can become quite significant. The DCR losses can be
calculated as follows:
⎛ (V − VOUT ) × D ⎞
I LOAD > ⎜⎜ IN
⎟⎟
2L × f
⎝
⎠
As shown in the previous equation, the load at which
MIC23150 transitions from HyperLight Load™ mode to
PWM mode is a function of the input voltage (VIN), output
voltage (VOUT), duty cycle (D), inductance (L) and
frequency (f). As shown in Figure 3, as the Output
Current increases, the switching frequency also
increases until the MIC23150 goes from HyperLight
LoadTM mode to PWM mode at approximately 120mA.
The MIC23150 will switch at a relatively constant
frequency around 4MHz once the output current is over
120mA.
PDCR = IOUT2 x DCR
From that, the loss in efficiency due to inductor
resistance can be calculated as follows:
10
⎞⎤
⎟⎥ × 100
⎟
⎠⎦⎥
SW FREQUENCY (MHz)
⎡ ⎛
VOUT × IOUT
Efficiency Loss = ⎢1 − ⎜⎜
V
⎣⎢ ⎝ OUT × IOUT + PDCR
Efficiency loss due to DCR is minimal at light loads and
gains significance as the load is increased. Inductor
selection becomes a trade-off between efficiency and
size in this case.
V
1
IN
= 3.0V
V
IN
V
IN
= 3.6V
= 4.2V
0.1
0.01
L = 4.7µH
VOUT = 1.8V
C
HyperLight Load™ Mode
MIC23150 uses a minimum on and off time proprietary
control loop (patented by Micrel). When the output
voltage falls below the regulation threshold, the error
comparator begins a switching cycle that turns the
PMOS on and keeps it on for the duration of the
minimum-on-time. This increases the output voltage. If
the output voltage is over the regulation threshold, then
February 2009
SW Frequency
vs Output Current
0.001
1
OUT
= 4.7µF
10
100
1000 10000
OUTPUT CURRENT (mA)
Figure 3. SW Frequency vs. Output Current
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MIC23150
MIC23150 Typical Application Circuit
U1 MIC23150
L1
VIN
VIN
C1
EN
SW
2mm×2mm
ThinMLF SNS
VOUT
C2
EN
AGND
PGND
GND
GND
Bill of Materials
Item
Part Number
C1, C2
C1608X5R0J475K
VLS3010T-1R0N1R9
L1
VLS4012T-1R0N1R6
DO2010-102ML
U1
MIC23150-xYMT
Manufacturer
TDK(1)
TDK
(1)
TDK
(1)
Coilcraft
Description
Qty.
4.7µF Ceramic Capacitor, 6.3V, X5R, Size 0603
2
1µH, 1.9A, 60mΩ, L3.0mm x W3.0mm x H1.0mm
1
1µH, 2.8A, 50mΩ, L4.0mm x W4.0mm x H1.2mm
(2)
Micrel, Inc.(3)
1µH, 1.8A, 162mΩ, L2.0mm x W2.0mm x H1.0mm
4MHz 2A Buck Regulator with HyperLight Load™ Mode
1
Notes:
1. TDK: www.tdk.com
2. Coilcraft: www.coilcraft.com
3. Micrel, Inc.: www.micrel.com
February 2009
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MIC23150
PCB Layout Recommendations
Thin MILF Top Layer
Thin MLF Bottom Layer
February 2009
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MIC23150
Package Information
8-Pin 2mm x 2mm Thin MLF
MICREL, INC. 2180 FORTUNE DRIVE SAN JOSE, CA 95131 USA
TEL +1 (408) 944-0800 FAX +1 (408) 474-1000 WEB http://www.micrel.com
The information furnished by Micrel in this data sheet is believed to be accurate and reliable. However, no responsibility is assumed by Micrel for its
use. Micrel reserves the right to change circuitry and specifications at any time without notification to the customer.
Micrel Products are not designed or authorized for use as components in life support appliances, devices or systems where malfunction of a product
can reasonably be expected to result in personal injury. Life support devices or systems are devices or systems that (a) are intended for surgical implant
into the body or (b) support or sustain life, and whose failure to perform can be reasonably expected to result in a significant injury to the user. A
Purchaser’s use or sale of Micrel Products for use in life support appliances, devices or systems is a Purchaser’s own risk and Purchaser agrees to fully
indemnify Micrel for any damages resulting from such use or sale.
February 2009
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© 2008 Micrel, Incorporated.
M9999-082908-A
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