TI1 DRV632PW Directpathâ ¢, 2-vrms audio line driver with adjustable gain Datasheet

DRV632
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SLOS681A – JANUARY 2011 – REVISED JULY 2013
DirectPath™, 2-VRMS Audio Line Driver With Adjustable Gain
Check for Samples: DRV632
FEATURES
DESCRIPTION
•
The DRV632 is a 2-VRMS pop-free stereo line driver
designed to allow the removal of the output dcblocking capacitors for reduced component count and
cost. The device is ideal for single-supply electronics
where size and cost are critical design parameters.
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23
•
•
•
•
•
•
•
•
•
•
•
•
Stereo DirectPath™ Audio Line Driver
– 2 Vrms Into 10 kΩ With 3.3-V Supply
Low THD+N < 0.01% at 2 Vrms Into 10 kΩ
High SNR, >90 dB
600-Ω Output Load Compliant
Differential Input and Single-Ended Output
Adjustable Gain by External Gain-Setting
Resistors
Low DC Offset, <1 mV
Ground-Referenced Outputs Eliminate DCBlocking Capacitors
– Reduce Board Area
– Reduce Component Cost
– Improve THD+N Performance
– No Degradation of Low-Frequency
Response Due to Output Capacitors
Short-Circuit Protection
Click- and Pop-Reduction Circuitry
External Undervoltage Mute
Active Mute Control for Pop-Free Audio On/Off
Control
Space-Saving TSSOP Package
APPLICATIONS
•
•
•
•
•
•
Designed
using
TI’s
patented
DirectPath™
technology, The DRV632 is capable of driving 2 VRMS
into a 10-kΩ load with 3.3-V supply voltage. The
device has differential inputs and uses external gainsetting resistors to support a gain range of ±1 V/V to
±10 V/V, and gain can be configured individually for
each channel. Line outputs have ±8-kV IEC ESD
protection, requiring just a simple resistor-capacitor
ESD protection circuit. The DRV632 has built-in
active-mute control for pop-free audio on/off control.
The DRV632 has an external undervoltage detector
that mutes the output when the power supply is
removed, ensuring a pop-free shutdown.
Using the DRV632 in audio products can reduce
component count considerably compared to
traditional methods of generating a 2-VRMS output.
The DRV632 does not require a power supply greater
than 3.3 V to generate its 5.6-Vpp output, nor does it
require a split-rail power supply. The DRV632
integrates its own charge pump to generate a
negative supply rail that provides a clean, pop-free
ground-biased 2-VRMS output.
The DRV632 is available in a 14-pin TSSOP.
Set-Top Boxes
Blu-ray Disc™, DVD Players
LCD and PDP TV
Mini/Micro Combo Systems
Sound Cards
Laptops
1
2
3
Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of
Texas Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet.
DirectPath, FilterPro are trademarks of Texas Instruments.
Blu-ray Disc is a trademark of Blu-ray Disc Association.
PRODUCTION DATA information is current as of publication date.
Products conform to specifications per the terms of the Texas
Instruments standard warranty. Production processing does not
necessarily include testing of all parameters.
Copyright © 2011–2013, Texas Instruments Incorporated
DRV632
SLOS681A – JANUARY 2011 – REVISED JULY 2013
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These devices have limited built-in ESD protection. The leads should be shorted together or the device placed in conductive foam
during storage or handling to prevent electrostatic damage to the MOS gates.
ORDERING INFORMATION (1)
(1)
TA
PACKAGE
DESCRIPTION
–40°C to 85°C
DRV632PW
14-Pin
For the most current package and ordering information, see the Package Option Addendum at the end of this document, or see the TI
Web site at www.ti.com.
ABSOLUTE MAXIMUM RATINGS (1)
over operating free-air temperature range
Supply voltage, VDD to GND
VI
Input voltage
RL
Minimum load impedance – line outputs – OUTL, OUTR
Mute to GND, UVP to GND
VALUE
UNIT
–0.3 to 4
V
VSS – 0.3 to VDD + 0.3
V
600
Ω
–0.3 to VDD + 0.3
V
TJ
Maximum operating junction temperature range
–40 to 150
°C
Tstg
Storage temperature range
–40 to 150
°C
(1)
Stresses beyond those listed under Absolute Maximum Ratings may cause permanent damage to the device. These are stress ratings
only, and functional operation of the device at these or any other conditions beyond those indicated under Recommended Operating
Conditions is not implied. Exposure to absolute-maximum-rated conditions for extended periods may affect device reliability.
THERMAL INFORMATION
DRV632
THERMAL METRIC
(1)
PW
UNIT
14 PINS
Junction-to-ambient thermal resistance (2)
θJA
(3)
130
°C/W
θJCtop
Junction-to-case (top) thermal resistance
49
°C/W
θJB
Junction-to-board thermal resistance (4)
63
°C/W
ψJT
Junction-to-top characterization parameter (5)
3.6
°C/W
ψJB
Junction-to-board characterization parameter
(6)
62
°C/W
θJCbot
Junction-to-case (bottom) thermal resistance (7)
n/a
°C/W
(1)
(2)
(3)
(4)
(5)
(6)
(7)
2
For more information about traditional and new thermal metrics, see the IC Package Thermal Metrics application report, SPRA953.
The junction-to-ambient thermal resistance under natural convection is obtained in a simulation on a JEDEC-standard, high-K board, as
specified in JESD51-7, in an environment described in JESD51-2a.
The junction-to-case (top) thermal resistance is obtained by simulating a cold plate test on the package top. No specific JEDECstandard test exists, but a close description can be found in the ANSI SEMI standard G30-88.
The junction-to-board thermal resistance is obtained by simulating in an environment with a ring cold plate fixture to control the PCB
temperature, as described in JESD51-8.
The junction-to-top characterization parameter, ψJT, estimates the junction temperature of a device in a real system and is extracted
from the simulation data for obtaining θJA, using a procedure described in JESD51-2a (sections 6 and 7).
The junction-to-board characterization parameter, ψJB, estimates the junction temperature of a device in a real system and is extracted
from the simulation data for obtaining θJA , using a procedure described in JESD51-2a (sections 6 and 7).
The junction-to-case (bottom) thermal resistance is obtained by simulating a cold plate test on the exposed (power) pad. No specific
JEDEC standard test exists, but a close description can be found in the ANSI SEMI standard G30-88.
Spacer
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SLOS681A – JANUARY 2011 – REVISED JULY 2013
RECOMMENDED OPERATING CONDITIONS
VDD
Supply voltage
DC supply voltage
RL
Load impedance
VIL
Low-level input voltage
Mute
VIH
High-level input voltage
Mute
TA
Operating free-air temperature
MIN
NOM
MAX
3
3.3
3.6
UNIT
0.6
10
kΩ
40
% of VDD
V
60
–40
% of VDD
25
85
°C
ELECTRICAL CHARACTERISTICS
TA = 25°C (unless otherwise noted)
PARAMETER
TEST CONDITIONS
|VOS|
Output offset voltage
PSRR
Power-supply rejection ratio
VOH
High-level output voltage
VDD = 3.3 V
VOL
Low-level output voltage
VDD = 3.3 V
VUVP_
External UVP detect voltage
MIN
VDD = 3.3 V
TYP
MAX
0.5
1
80
UNIT
mV
dB
3.1
V
–3.05
V
1.25
V
5
µA
EX
VUVP_
External UVP detect hysteresis current
EX_HYS
TERESI
S
fCP
Charge pump switching frequency
400
kHz
|IIH|
High-level input current, Mute
VDD = 3.3 V, VIH = VDD
200
1
µA
|IIL|
Low-level input current, Mute
VDD = 3.3 V, VIL = 0 V
1
µA
IDD
Supply current
VDD = 3.3 V, no load, Mute = VDD
5
VDD = 3.3 V, no load, Mute = GND, disabled
300
14
25
14
mA
OPERATING CHARACTERISTICS
VDD = 3.3 V, RDL = 10 kΩ, RFB = 30 kΩ, RIN = 15 kΩ, TA = 25°C, Charge pump: CP = 1 µF (unless otherwise noted)
PARAMETER
TEST CONDITIONS
MIN
THD+N = 1%, VDD = 3.3 V, f = 1 kHz, RL = 10 kΩ
THD+N
Total harmonic distortion plus noise
VO = 2 VRMS, f = 1 kHz
SNR
Signal-to-noise ratio (1)
A-weighted
105
DNR
Dynamic range
A-weighted
105
dB
VN
Noise voltage
A-weighted
11
μV
ZO
Output Impedance when muted
Mute = GND
110
mΩ
Input-to-output attenuation when
muted
Mute = GND
80
dB
Crosstalk—L to R, R to L
VO = 1 Vrms
–110
dB
25
mA
(1)
Current limit
2.4
UNIT
Output voltage, outputs in phase
ILIMIT
2
TYP MAX
VO
Vrms
0.002%
dB
SNR is calculated relative to 2-Vrms output.
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SLOS681A – JANUARY 2011 – REVISED JULY 2013
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PW PACKAGE
(TOP VIEW)
+INR
1
14
+INL
–INR
2
13
–INL
OUTR
3
12
OUTL
11
UVP
External
UnderVoltage
Detector
GND
4
Mute
5
10
GND
VSS
6
9
VDD
CN
7
8
CP
Charge Pump
PIN FUNCTIONS
PIN
NAME
NO.
I/O (1)
DESCRIPTION
CN
7
I/O
Charge-pump flying capacitor negative connection
CP
8
I/O
Charge-pump flying capacitor positive connection
GND
4, 10
P
Ground
–INL
13
I
Left-channel OPAMP negative input
+INL
14
I
Left-channel OPAMP positive input
–INR
2
I
Right-channel OPAMP negative input
+INR
1
I
Right-channel OPAMP positive input
Mute
5
I
Mute, active-low
OUTL
12
O
Left-channel OPAMP output
OUTR
3
O
Right-channel OPAMP output
UVP
11
I
Undervoltage protection, internal pullup; unconnected if UVP function is unused.
VDD
9
P
Positive supply
VSS
6
P
Supply voltage
(1)
4
I = input, O = output, P = power
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SLOS681A – JANUARY 2011 – REVISED JULY 2013
FUNCTIONAL BLOCK DIAGRAM
+INL
+INR
Line
Driver
–INL
Line
Driver
–INR
OUTL
OUTR
GND
UVP
Click and Pop
Suppression
Short-Circuit
Protection
GND
Mute
VSS
Bias
Circuitry
CN
VDD
CP
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SLOS681A – JANUARY 2011 – REVISED JULY 2013
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TYPICAL CHARACTERISTICS
VDD = 3.3 V , TA = 25°C, C(PUMP) = C(VSS) = 1 µF , CIN = 2.2 µF, RIN = 15 kΩ, Rfb = 30 kΩ, ROUT = 32 Ω, COUT = 1 nF (unless
otherwise noted)
TOTAL HARMONIC DISTORTION + NOISE
vs
OUTPUT VOLTAGE
TOTAL HARMONIC DISTORTION + NOISE
vs
OUTPUT VOLTAGE
10
10
Active Filter
Gain = 2V/V
RL = 600Ω
1
1
0.1
0.1
THD+N (%)
THD+N (%)
Active Filter
Gain = 2V/V
RL = 10 kΩ
0.01
0.001
0.01
0.001
100 Hz
1 kHz
10 kHz
100 Hz
1 kHz
10 kHz
0.0001
0.1
1
0.0001
0.1
3
1
Output Voltage (V)
Figure 1.
Figure 2.
TOTAL HARMONIC DISTORTION + NOISE
vs
FREQUENCY
TOTAL HARMONIC DISTORTION + NOISE
vs
FREQUENCY
10
10
Active Filter
Gain = 2V/V
RL = 600 Ω
Ch1 1 Vrms
Ch1 2 Vrms
1
1
0.1
0.1
THD+N (%)
THD+N (%)
Active Filter
Gain = 2V/V
RL = 10 kΩ
0.01
0.001
0.0001
Ch1 1 Vrms
Ch1 2 Vrms
0.01
0.001
20
100
1k
Frequency (Hz)
10k
20k
0.0001
20
Figure 3.
6
3
Output Voltage (V)
100
1k
Frequency (Hz)
10k
20k
Figure 4.
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TYPICAL CHARACTERISTICS (continued)
VDD = 3.3 V , TA = 25°C, C(PUMP) = C(VSS) = 1 µF , CIN = 2.2 µF, RIN = 15 kΩ, Rfb = 30 kΩ, ROUT = 32 Ω, COUT = 1 nF (unless
otherwise noted)
CROSSTALK
vs
FREQUENCY
0
RL = 10 kΩ
VO = 1 Vrms
VREF = 1 V
−20
Left to Right
Right to Left
Crosstalk (dBrA)
−40
−60
−80
−100
−120
−140
20
100
1k
Frequency (Hz)
10k
20k
Figure 5.
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APPLICATION INFORMATION
LINE DRIVER AMPLIFIERS
Single-supply line-driver amplifiers typically require dc-blocking capacitors. The top drawing in Figure 6 illustrates
the conventional line-driver amplifier connection to the load and output signal. DC blocking capacitors are often
large in value. The line load (typical resistive values of 600 Ω to 10 kΩ) combines with the dc blocking capacitors
to form a high-pass filter. Equation 1 shows the relationship between the load impedance (RL), the capacitor
(CO), and the cutoff frequency (fC).
1
fc =
2p R L CO
(1)
CO can be determined using Equation 2, where the load impedance and the cutoff frequency are known.
1
CO =
2p R L f c
(2)
If fC is low, the capacitor must then have a large value because the load resistance is small. Large capacitance
values require large package sizes. Large package sizes consume PCB area, stand high above the PCB,
increase cost of assembly, and can reduce the fidelity of the audio output signal.
9 V–12 V
Conventional Solution
VDD
+
+
OPAMP
Mute Circuit
Co
+
Output
VDD/2
–
GND
Enable
3.3 V
DirectPath
DRV632 Solution
VDD
Mute Circuit
+
DRV632
Output
GND
–
VSS
Enable
Figure 6. Conventional and DirectPath Line Drivers
The DirectPath amplifier architecture operates from a single supply but makes use of an internal charge pump to
provide a negative voltage rail. Combining the user-provided positive rail and the negative rail generated by the
IC, the device operates in what is effectively a split-supply mode. The output voltages are now centered at zero
volts with the capability to swing to the positive rail or negative rail. Combining this with the built-in click and pop
reduction circuit, the DirectPath amplifier requires no output dc blocking capacitors. The bottom block diagram
and waveform of Figure 6 illustrate the ground-referenced line-driver architecture. This is the architecture of the
DRV632.
8
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CHARGE-PUMP FLYING CAPACITOR AND PVSS CAPACITOR
The charge-pump flying capacitor serves to transfer charge during the generation of the negative supply voltage.
The PVSS capacitor must be at least equal to the charge-pump capacitor in order to allow maximum charge
transfer. Low-ESR capacitors are an ideal selection, and a value of 1 μF is typical. Capacitor values that are
smaller than 1 μF can be used, but the maximum output voltage may be reduced and the device may not
operate to specifications. If the DRV632 is used in highly noise-sensitive circuits, it is recommended to add a
small LC filter on the VDD connection.
DECOUPLING CAPACITORS
The DRV632 is a DirectPath line-driver amplifier that requires adequate power supply decoupling to ensure that
the noise and total harmonic distortion (THD) are low. A good, low equivalent-series-resistance (ESR) ceramic
capacitor, typically 1 μF, placed as close as possible to the device VDD lead works best. Placing this decoupling
capacitor close to the DRV632 is important for the performance of the amplifier. For filtering lower-frequency
noise signals, a 10-μF or greater capacitor placed near the audio power amplifier would also help, but it is not
required in most applications because of the high PSRR of this device.
GAIN-SETTING RESISTOR RANGES
The gain-setting resistors, RIN and Rfb, must be chosen so that noise, stability, and input capacitor size of the
DRV632 are kept within acceptable limits. Voltage gain is defined as Rfb divided by RIN.
Selecting values that are too low demands a large input ac-coupling capacitor, CIN. Selecting values that are too
high increases the noise of the amplifier. Table 1 lists the recommended resistor values for different invertinginput gain settings.
Table 1. Recommended Resistor Values
GAIN
INPUT RESISTOR VALUE, RIN
FEEDBACK RESISTOR VALUE, Rfb
–1 V/V
10 kΩ
10 kΩ
–1.5 V/V
8.2 kΩ
12 kΩ
–2 V/V
15 kΩ
30 kΩ
–10 V/V
4.7 kΩ
47 kΩ
USING THE DRV632 AS A SECOND-ORDER FILTER
Several audio DACs used today require an external low-pass filter to remove out-of-band noise. This is possible
with the DRV632, as it can be used like a standard operational amplifier. Several filter topologies can be
implemented, both single-ended and differential. In Figure 7, multi-feedback (MFB) with differential input and
single-ended input are shown.
An ac-coupling capacitor to remove dc content from the source is shown; it serves to block any dc content from
the source and lowers the dc gain to 1, helping to reduce the output dc offset to a minimum.
The component values can be calculated with the help of the TI FilterPro™ program available on the TI Web site
at:
http://focus.ti.com/docs/toolsw/folders/print/filterpro.html.
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Inverting Input
Differential Input
R2
C3
R1
R2
C3
C1
R3
–IN
R1
R3
C1
–IN
–
DRV632
+
C2
C2
–
DRV632
+
+IN
C3
R1
R3
C1
R2
Figure 7. Second-Order Active Low-Pass Filter
The resistor values should have a low value for obtaining low noise, but should also have a high enough value to
get a small-size ac-coupling capacitor. With the proposed values of R1 = 15 kΩ, R2 = 30 kΩ, and R3 = 43 kΩ, a
dynamic range (DYR) of 106 dB can be achieved with a 1-μF input ac-coupling capacitor.
INPUT-BLOCKING CAPACITORS
DC input-blocking capacitors are required to be added in series with the audio signal into the input pins of the
DRV632. These capacitors block the dc portion of the audio source and allow the DRV632 inputs to be properly
biased to provide maximum performance.
These capacitors form a high-pass filter with the input resistor, RIN. The cutoff frequency is calculated using
Equation 3. For this calculation, the capacitance used is the input-blocking capacitor, and the resistance is the
input resistor chosen from Table 1; then the frequency and/or capacitance can be determined when one of the
two values is given.
It is recommended to use electrolytic capacitors or high-voltage-rated capacitors as input blocking capacitors to
ensure minimal variation in capacitance with input voltages. Such variation in capacitance with input voltages is
commonly seen in ceramic capacitors and can increase low-frequency audio distortion.
fcIN =
1
2p R INCIN
or
CIN =
1
2p fcIN R IN
(3)
DRV632 UVP OPERATION
The shutdown threshold at the UVP pin is 1.25 V. The customer must use a resistor divider to obtain the
shutdown threshold and hysteresis desired for a particular application. The customer-selected thresholds can be
determined as follows:
EXTERNAL UNDERVOLTAGE DETECTION
External undervoltage detection can be used to mute/shut down the DRV632 before an input device can
generate a pop.
The shutdown threshold at the UVP pin is 1.25 V. The user selects a resistor divider to obtain the shutdown
threshold and hysteresis for the specific application. The thresholds can be determined as follows:
VUVP = (1.25 – 6 μA × R3) × (R1 + R2) / R2
Hysteresis = 5 μA × R3 × (R1 + R2) / R2
For example, to obtain VUVP = 3.8 V and 1-V hysteresis, we can use R1 = 3 kΩ, R2 = 1 kΩ, and R3 = 50 kΩ.
10
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VSUP_MO
R1
R3
UVP
R2
LAYOUT RECOMMENDATIONS
A proposed layout for the DRV632 can be seen in the DRV632EVM User's Guide, and the Gerber files can be
downloaded from http://www.ti.com. To access this information, open the DRV632 product folder and look in the
Tools and Software folder.
GAIN-SETTING RESISTORS
The gain-setting resistors, RIN and Rfb, must be placed close to pins 13 and 17, respectively, to minimize
capacitive loading on these input pins and to ensure maximum stability of the DRV632. For the recommended
PCB layout, see the DRV632EVM User's Guide.
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APPLICATION CIRCUIT
R1
C3
C3
R1
R1
R3
R2
R2
C2
C3
R1
C2
R3
R3
+
C3
LEFT
– INPUT
+
RIGHT
– INPUT
R3
+
C1
C1
R2
R2
DRV632
+INR
–INR
+INL
Line
Driver
Line
Driver
–INL
C1
C1
RIGHT OUTPUT
OUTR
UVP
GND
Click and Pop
Suppression
Short-Circuit
Protection
R11
GND
EN
VSS
LEFT OUTPUT
OUTL
3.3-V Supply
Bias
Circuitry
R12
VDD
1mF
1mF
CN
CP
1mF
Linear
Low-Dropout
Regulator
System Supply
10 mF
R1 = 15 kΩ, R2 = 30 kΩ, R3 = 43 kΩ, C1 = 47 pF, C2 = 180 pF
Differential-input, single-ended output, second-order filter
12
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REVISION HISTORY
Changes from Original (January 2011) to Revision A
Page
•
Deleted min value for SNR and DNR in OPERATING CHARACTERISTICS table ............................................................. 3
•
Changed description of UVP in PIN FUNCTIONS table ....................................................................................................... 4
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PACKAGE OPTION ADDENDUM
www.ti.com
11-Apr-2013
PACKAGING INFORMATION
Orderable Device
Status
(1)
Package Type Package Pins Package
Drawing
Qty
Eco Plan
Lead/Ball Finish
(2)
MSL Peak Temp
Op Temp (°C)
Top-Side Markings
(3)
(4)
DRV632PW
ACTIVE
TSSOP
PW
14
90
Green (RoHS
& no Sb/Br)
CU NIPDAU
Level-2-260C-1 YEAR
-40 to 85
DRV632
DRV632PWR
ACTIVE
TSSOP
PW
14
2000
Green (RoHS
& no Sb/Br)
CU NIPDAU
Level-2-260C-1 YEAR
-40 to 85
DRV632
(1)
The marketing status values are defined as follows:
ACTIVE: Product device recommended for new designs.
LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.
NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design.
PREVIEW: Device has been announced but is not in production. Samples may or may not be available.
OBSOLETE: TI has discontinued the production of the device.
(2)
Eco Plan - The planned eco-friendly classification: Pb-Free (RoHS), Pb-Free (RoHS Exempt), or Green (RoHS & no Sb/Br) - please check http://www.ti.com/productcontent for the latest availability
information and additional product content details.
TBD: The Pb-Free/Green conversion plan has not been defined.
Pb-Free (RoHS): TI's terms "Lead-Free" or "Pb-Free" mean semiconductor products that are compatible with the current RoHS requirements for all 6 substances, including the requirement that
lead not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, TI Pb-Free products are suitable for use in specified lead-free processes.
Pb-Free (RoHS Exempt): This component has a RoHS exemption for either 1) lead-based flip-chip solder bumps used between the die and package, or 2) lead-based die adhesive used between
the die and leadframe. The component is otherwise considered Pb-Free (RoHS compatible) as defined above.
Green (RoHS & no Sb/Br): TI defines "Green" to mean Pb-Free (RoHS compatible), and free of Bromine (Br) and Antimony (Sb) based flame retardants (Br or Sb do not exceed 0.1% by weight
in homogeneous material)
(3)
MSL, Peak Temp. -- The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder temperature.
(4)
Multiple Top-Side Markings will be inside parentheses. Only one Top-Side Marking contained in parentheses and separated by a "~" will appear on a device. If a line is indented then it is a
continuation of the previous line and the two combined represent the entire Top-Side Marking for that device.
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In no event shall TI's liability arising out of such information exceed the total purchase price of the TI part(s) at issue in this document sold by TI to Customer on an annual basis.
Addendum-Page 1
Samples
PACKAGE MATERIALS INFORMATION
www.ti.com
14-Jul-2012
TAPE AND REEL INFORMATION
*All dimensions are nominal
Device
DRV632PWR
Package Package Pins
Type Drawing
TSSOP
PW
14
SPQ
Reel
Reel
A0
Diameter Width (mm)
(mm) W1 (mm)
2000
330.0
12.4
Pack Materials-Page 1
6.9
B0
(mm)
K0
(mm)
P1
(mm)
5.6
1.6
8.0
W
Pin1
(mm) Quadrant
12.0
Q1
PACKAGE MATERIALS INFORMATION
www.ti.com
14-Jul-2012
*All dimensions are nominal
Device
Package Type
Package Drawing
Pins
SPQ
Length (mm)
Width (mm)
Height (mm)
DRV632PWR
TSSOP
PW
14
2000
367.0
367.0
35.0
Pack Materials-Page 2
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