Order this document by MC13150/D NARROWBAND FM COILLESS DETECTOR IF SUBSYSTEM FOR CELLULAR AND ANALOG APPLICATIONS The MC13150 is a narrowband FM IF subsystem targeted at cellular and other analog applications. Excellent high frequency performance is achieved, with low cost, through use of Motorola’s MOSAIC 1.5 RF bipolar process. The MC13150 has an onboard Colpitts VCO for Crystal controlled second LO in dual conversion receivers. The mixer is a double balanced configuration with excellent third order intercept. It is useful to beyond 200 MHz. The IF amplifier is split to accommodate two low cost cascaded filters. RSSI output is derived by summing the output of both IF sections. The quadrature detector is a unique design eliminating the conventional tunable quadrature coil. Applications for the MC13150 include cellular, CT–1 900 MHz cordless telephone, data links and other radio systems utilizing narrowband FM modulation. • Linear Coilless Detector • • • • • • • • SEMICONDUCTOR TECHNICAL DATA 24 Adjustable Demodulator Bandwidth 1 FTA SUFFIX PLASTIC PACKAGE CASE 977 (LQFP–24) 2.5 to 6.0 Vdc Operation Low Drain Current: < 2.0 mA Typical Sensitivity of 2.0 µV for 12 dB SINAD IIP3, Input Third Order Intercept Point of 0 dBm RSSI Range of Greater Than 100 dB Internal 1.4 kΩ Terminations for 455 kHz Filters 32 Split IF for Improved Filtering and Extended RSSI Range 1 ORDERING INFORMATION Operating Temperature Range Device MC13150FTA LQFP–24 TA = –40 ° to +85°C MC13150FTB FTB SUFFIX PLASTIC PACKAGE CASE 873 (LQFP–32) Package LQFP–32 PIN CONNECTIONS VEE1 LOe LOb Enable RSSI Mix in VEE1 VCC (N/C) LOe LOb VCC (N/C) Enable RSSI LQFP–32 Mix in LQFP–24 24 23 22 21 20 19 32 31 29 28 27 26 25 MixOut 1 30 24 RSSIb Mixout 1 VCC1 2 17 DETout IFin 3 16 VEE2 IFin 4 21 VEE2 15 DET Gain IFd1 5 20 DETGain 18 RSSIb Mixer Mixer VCC1 2 IFd2 5 IFout 6 14 AFTFilt Limiter 13 AFT out VCC (N/C) 3 22 VEE (N/C) IF VCC (N/C) 6 IFd2 7 Detector 4 Detector IFd1 IF 23 DETout Limiter LIMd1 LIMd2 BWAdj FAdj 11 12 13 Motorola, Inc. 1997 MOTOROLA ANALOG IC DEVICE DATA 14 15 16 FAdj LIM in 10 BWAdj V CC2 9 LIM d2 VCC (N/C) 12 LIM d1 11 VCC (N/C) 10 LIM in 9 V CC2 8 18 AFTFilt 17 AFTout IFout 8 7 19 VEE (N/C) Rev 2 1 MC13150 MAXIMUM RATINGS ÁÁÁÁÁÁÁÁÁÁ ÁÁÁ ÁÁÁÁÁ ÁÁÁÁÁ ÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁ ÁÁÁ ÁÁÁÁÁ ÁÁÁÁÁ ÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁ ÁÁÁ ÁÁÁÁÁ ÁÁÁÁÁ ÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁ ÁÁÁ ÁÁÁÁÁ ÁÁÁÁÁ ÁÁÁÁ Pin Symbol Value Unit Power Supply Voltage Rating 2, 9 VCC(max) 6.5 Vdc Junction Temperature – TJmax +150 °C Storage Temperature Range – Tstg –65 to +150 °C NOTE: 1. Devices should not be operated at or outside these values. The ”Recommended Operating Limits” provide for actual device operation. 2. ESD data available upon request. RECOMMENDED OPERATING CONDITIONS ÁÁÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁ ÁÁÁÁÁÁ ÁÁÁÁÁÁ ÁÁÁÁ ÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁ ÁÁÁÁÁÁ ÁÁÁÁÁÁ ÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁ ÁÁÁÁÁÁ ÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁ ÁÁÁÁÁÁ ÁÁÁÁÁÁ ÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁ ÁÁÁÁÁÁ ÁÁÁÁÁÁ ÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁ ÁÁÁÁÁÁ ÁÁÁÁÁÁ ÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁ ÁÁÁÁÁÁ ÁÁÁÁÁÁ ÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁ ÁÁÁÁ ÁÁÁÁÁÁ ÁÁÁÁ ÁÁÁÁ ÁÁÁÁ ÁÁÁÁ ÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁ ÁÁÁÁ ÁÁÁÁÁÁ ÁÁÁÁ ÁÁÁÁ ÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁ ÁÁÁÁ ÁÁÁÁÁÁ ÁÁÁÁ ÁÁÁÁ ÁÁÁÁ ÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁ ÁÁÁÁ ÁÁÁÁÁÁ ÁÁÁÁ ÁÁÁÁ ÁÁÁÁ ÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁ ÁÁÁÁÁ ÁÁÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁÁ ÁÁÁ ÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁ ÁÁÁÁÁ ÁÁÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁÁ ÁÁÁ ÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁ ÁÁÁÁÁ ÁÁÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁÁ ÁÁÁ ÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁ ÁÁÁÁÁ ÁÁÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁÁ ÁÁÁ ÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁ ÁÁÁÁÁ ÁÁÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁÁ ÁÁÁ ÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁ ÁÁÁÁÁ ÁÁÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁÁ ÁÁÁ ÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁ ÁÁÁÁÁ ÁÁÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁÁ ÁÁÁ ÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁ ÁÁÁÁÁ ÁÁÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁÁ ÁÁÁ ÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁ ÁÁÁÁÁ ÁÁÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁÁ ÁÁÁ ÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁ ÁÁÁÁÁ ÁÁÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁÁ ÁÁÁ ÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁ ÁÁÁÁÁ ÁÁÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁÁ ÁÁÁ ÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁ ÁÁÁÁÁ ÁÁÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁÁ ÁÁÁ ÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁ ÁÁÁÁÁ ÁÁÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁÁ ÁÁÁ ÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁ ÁÁÁÁÁ ÁÁÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁÁ ÁÁÁ ÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁ ÁÁÁÁÁ ÁÁÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁÁ ÁÁÁ ÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁ ÁÁÁÁÁ ÁÁÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁÁ ÁÁÁ ÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁ ÁÁÁÁÁ ÁÁÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁÁ ÁÁÁ ÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁ ÁÁÁÁÁ ÁÁÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁÁ ÁÁÁ ÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁ ÁÁÁÁÁ ÁÁÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁÁ ÁÁÁ ÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁ ÁÁÁÁÁ ÁÁÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁÁ ÁÁÁ ÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁ ÁÁÁÁÁ ÁÁÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁÁ ÁÁÁ ÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁ ÁÁÁÁÁ ÁÁÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁÁ ÁÁÁ Rating Power Supply Voltage TA = 25°C –40°C ≤ TA ≤ 85°C Pin Symbol Value Unit 2, 9 21, 31 VCC VEE 2.5 to 6.0 0 Vdc 32 fin 10 to 500 MHz (See Figure 22) Input Frequency Ambient Temperature Range – TA –40 to +85 °C Input Signal Level 32 Vin 0 dBm DC ELECTRICAL CHARACTERISTICS (TA = 25°C, VCC1 = VCC2 = 3.0 Vdc, No Input Signal.) Characteristics Total Drain Current (See Figure 2) Condition Pin Symbol Min Typ Max Unit VS = 3.0 Vdc 2+9 ITOTAL – 1.7 3.0 mA – 2+9 – – 40 – nA Supply Current, Power Down (See Figure 3) AC ELECTRICAL CHARACTERISTICS (TA = 25°C, VS = 3.0 Vdc, fRF = 50 MHz, fLO = 50.455 MHz, LO Level = –10 dBm, see Figure 1 Test Circuit*, unless otherwise specified.) Characteristics Condition Pin Symbol Min Typ Max Unit fmod = 1.0 kHz; fdev = ±5.0 kHz 32 – – –100 – dBm RSSI Dynamic Range (See Figure 7) – 25 – – 100 – dB Input 1.0 dB Compression Point Input 3rd Order Intercept Point (See Figure 18) – – – – 1.0 dB C. Pt. IIP3 – – –11 –1.0 – – dBm Measured with No IF Filters – ∆BW adj – 26 – kHz/µA Pin = –30 dBm; PLO = –10 dBm 32 – – 10 – dB Single–Ended 32 – – 200 – Ω – 1 – – 1.5 – kΩ – 29 – 30 63 100 µA IF and Limiter RSSI Slope Figure 7 25 – – 0.4 – µA/dB IF Gain Figure 8 4, 8 – – 42 – dB IF Input & Output Impedance – 4, 8 – – 1.5 – kΩ Limiter Input Impedance – 10 – – 1.5 – kΩ Limiter Gain – – – – 96 – dB 12 dB SINAD Sensitivity (See Figure 15) Coilless Detector Bandwidth Adjust (See Figure 11) MIXER Conversion Voltage Gain (See Figure 5) Mixer Input Impedance Mixer Output Impedance LOCAL OSCILLATOR LO Emitter Current (See Figure 26) IF & LIMITING AMPLIFIERS SECTION * Figure 1 Test Circuit uses positive (VCC) Ground. 2 MOTOROLA ANALOG IC DEVICE DATA MC13150 AC ELECTRICAL CHARACTERISTICS (continued) (TA = 25°C, VS = 3.0 Vdc, fRF = 50 MHz, fLO = 50.455 MHz, LO Level = –10 dBm, see Figure 1 Test Circuit*, unless otherwise specified.) Characteristics Condition Pin Symbol Min Typ Max Unit Frequency Adjust Current Figure 9, fIF = 455 kHz 16 – 41 49 56 µA Frequency Adjust Voltage Figure 10, fIF = 455 kHz 16 – 600 650 700 mVdc Bandwidth Adjust Voltage Figure 12, I15 = 1.0 µA 15 – – 570 – mVdc – 23 – – 1.36 – Vdc fdev = ±3.0 kHz 23 – 85 122 175 mVrms DETECTOR Detector DC Output Voltage (See Figure 25) Recovered Audio Voltage * Figure 1 Test Circuit uses positive (VCC) Ground. Figure 1. Test Circuit LO Input VEE1 10 µ 220 n + 100 n 1:4 Z Xformer Mixer In Enable 49.9 RSSI 100 n 31 32 220 n Mixer Out 29 28 27 25 2 RSSI Buffer Mixer VCC1 Detector Output 23 Local Oscillator 100 p RSSI Buffer 3 IF In 26 24 1 1.5 k 30 VEE1 22 RL 100 k 220 n 49.9 4 VEE2 21 5 20 220 n 220 n (6) IF 220 n 7 IF Amp Out 220 n 8 17 VCC2 9 10 Limiter In 11 220 n 12 13 14 220 n 220 n 220 n 15 I15 10 µ + VEE2 18 Limiter 220 n 1.5 k 19 Detector 6 RS 100 k 100 k V18–V17 = 0; fIF = 455 kHz 16 I16 49.9 This device contains 292 active transistors. MOTOROLA ANALOG IC DEVICE DATA 3 MC13150 MC13150 CIRCUIT DESCRIPTION General The MC13150 is a very low power single conversion narrowband FM receiver incorporating a split IF. This device is designated for use as the backend in analog narrowband FM systems such as cellular, 900 MHz cordless phones and narrowband data links with data rates up to 9.6 k baud. It contains a mixer, oscillator, extended range received signal strength indicator (RSSI), RSSI buffer, IF amplifier, limiting IF, a unique coilless quadrature detector and a device enable function (see Package Pin Outs/Block Diagram). Low Current Operation The MC13150 is designed for battery and portable applications. Supply current is typically 1.7 mAdc at 3.0 Vdc. Figure 2 shows the supply current versus supply voltage. Enable The enable function is provided for battery powered operation. The enabled pin is pulled down to enable the regulators. Figure 3 shows the supply current versus enable voltage, Venable (relative to VCC) needed to enable the device. Note that the device is fully enabled at VCC – 1.3 Vdc. Figure 4 shows the relationship of enable current, Ienable to enable voltage, Venable. Mixer The mixer is a double–balanced four quadrant multiplier and is designed to work up to 500 MHz. It has a single ended input. Figure 5 shows the mixer gain and saturated output response as a function of input signal drive and for –10 dBm LO drive level. This is measured in the application circuit shown in Figure 15 in which a single LC matching network is used. Since the single–ended input impedance of the mixer is 200 Ω, an alternate solution uses a 1:4 impedance transformer to match the mixer to 50 Ω input impedance. The linear voltage gain of the mixer alone is approximately 4.0 dB (plus an additional 6.0 dB for the transformer). Figure 6 shows the mixer gain versus the LO input level for various mixer input levels at 50 MHz RF input. 4 The buffered output of the mixer is internally loaded, resulting in an output impedance of 1.5 kΩ. Local Oscillator The on–chip transistor operates with crystal and LC resonant elements up to 220 MHz. Series resonant, overtone crystals are used to achieve excellent local oscillator stability. 3rd overtone crystals are used through about 65 to 70 MHz. Operation from 70 MHz up to 200 MHz is feasible using the on–chip transistor with a 5th or 7th overtone crystal. To enhance operation using an overtone crystal, the internal transistor’s bias is increased by adding an external resistor from Pin 29 (in 32 pin QFP package) to VEE to keep the oscillator on continuously or it may be taken to the enable pin to shut it off when the receiver is disabled. –10 dBm of local oscillator drive is needed to adequately drive the mixer (Figure 6). The oscillator configurations specified above are described in the application section. RSSI The received signal strength indicator (RSSI) output is a current proportional to the log of the received signal amplitude. The RSSI current output is derived by summing the currents from the IF and limiting amplifier stages. An external resistor at Pin 25 (in 32 pin QFP package) sets the voltage range or swing of the RSSI output voltage. Linearity of the RSSI is optimized by using external ceramic bandpass filters which have an insertion loss of 4.0 dB. The RSSI circuit is designed to provide 100+ dB of dynamic range with temperature compensation (see Figures 7 and 23 which show the RSSI response of the applications circuit). RSSI Buffer The RSSI buffer has limitations in what loads it can drive. It can pull loads well towards the positive and negative supplies, but has problems pulling the load away from the supplies. The load should be biased at half supply to overcome this limitation. MOTOROLA ANALOG IC DEVICE DATA MC13150 Figure 2. Supply Current versus Supply Voltage 10–2 ISUPPLY, SUPPLY CURRENT (A) ISUPPLY, SUPPLY CURRENT (mA) 2.0 1.6 1.2 0.8 0.4 TA = 25°C 0 1.5 2.5 3.5 4.5 5.5 6.5 VCC = 3.0 Vdc TA = 25°C VENABLE Measured Relative to VCC 10–3 10–4 10–5 10–6 10–7 10–8 10–9 10–10 0.5 7.5 0.7 0.9 1.1 1.3 1.5 VENABLE, SUPPLY VOLTAGE (Vdc) VENABLE, ENABLE VOLTAGE (Vdc) Figure 4. Enable Current versus Enable Voltage Figure 5. Mixer IF Output Level versus RF Input Level 20 70 VCC = 3.0 Vdc TA = 25°C 60 MIXER IF OUTPUT LEVEL (dBm) IENABLE, ENABLE CURRENT ( µA) Figure 3. Supply Current versus Enable Voltage 50 40 30 20 10 0 0.4 0.8 1.2 1.6 0 –10 –20 fRF = 50 MHz; fLO = 50.455 MHz LO Input Level = –10 dBm (100 mVrms) (Rin = 50 Ω; Rout = 1.4 kΩ –30 –40 –50 –50 –10 0 VEE = –3.0 Vdc TA = 25°C 10 2.0 –40 –30 –20 –10 0 VENABLE, ENABLE VOLTAGE (Vdc) RF INPUT LEVEL (dBm) Figure 6. Mixer IF Output Level versus Local Oscillator Input Level Figure 7. RSSI Output Current versus Input Signal Level 20 10 20 –20 0 50 0 VEE = –3.0 Vdc TA = 25°C RSSI OUTPUT CURRENT (µA) MIXER IF OUTPUT LEVEL (dBm) RF In = 0 dBm –20 dBm –20 –40 dBm –40 –60 –80 –60 fRF = 50 MHz; fLO = 50.455 MHz Rin = 50 Ω; Rout = 1.4 kΩ 40 30 VCC = 3.0 Vdc f = 50 MHz fLO = 50.455 MHz 455 kHz Ceramic Filter See Figure 15 20 10 0 –50 –40 –30 –20 LO DRIVE (dBm) MOTOROLA ANALOG IC DEVICE DATA –10 0 –120 –100 –80 –60 –40 SIGNAL INPUT LEVEL (dBm) 5 MC13150 IF Amplifier The first IF amplifier section is composed of three differential stages. This section has internal dc feedback and external input decoupling for improved symmetry and stability. The total gain of the IF amplifier block is approximately 42 dB at 455 kHz. Figure 8 shows the gain of the IF amplifier as a function of the IF frequency. The fixed internal input impedance is 1.5 kΩ; it is designed for applications where a 455 kHz ceramic filter is used and no external output matching is necessary since the filter requires a 1.5 kΩ source and load impedance. Overall RSSI linearity is dependent on having total midband attenuation of 10 dB (4.0 dB insertion loss plus 6.0 dB impedance matching loss) for the filter. The output of the IF amplifier is buffered and the impedance is 1.5 kΩ. Limiter The limiter section is similar to the IF amplifier section except that six stages are used. The fixed internal input impedance is 1.5 kΩ. The total gain of the limiting amplifier section is approximately 96 dB. This IF limiting amplifier section internally drives the quadrature detector section. Figure 9. Fadj Current versus IF Frequency 50 120 45 100 Fadj CURRENT ( µA) IF AMP GAIN (dB) Figure 8. IF Amplifier Gain versus IF Frequency 40 35 Vin = 100 µV Rin = 50 Ω Rout = 1.4 kΩ BW (3.0 dB) = 2.4 MHz TA = 25°C 30 25 20 0.01 80 60 40 20 0 0.1 800 1.0 10 0 200 400 600 f, FREQUENCY (MHz) f, IF FREQUENCY (kHz) Figure 10. Fadj Voltage versus Fadj Current Figure 11. BWadj Current versus IF Frequency 800 1000 480 500 3.5 VCC = 3.0 Vdc TA = 25°C VCC = 3.0 Vdc BW 26 kHz/µA 3.0 750 BWadj CURRENT ( µA) Fadj VOLTAGE (mVdc) VCC = 3.0 Vdc Slope at 455 kHz = 9.26 kHz/µA 700 650 2.5 2.0 1.5 1.0 0.5 600 0 20 40 60 Fadj CURRENT (µA) 6 80 100 0 400 420 440 460 f, IF FREQUENCY (kHz) MOTOROLA ANALOG IC DEVICE DATA MC13150 Coilless Detector The quadrature detector is similar to a PLL. There is an internal oscillator running at the IF frequency and two detector outputs. One is used to deliver the audio signal and the other one is filtered and used to tune the oscillator. The oscillator frequency is set by an external resistor at the Fadj pin. Figure 9 shows the control current required for a particular frequency; Figure 10 shows the pin voltage at that current. From this the value of RF is chosen. For example, 455 kHz would require a current of around 50 µA. The pin voltage (Pin 16 in the 32 pin QFP package) is around 655mV giving a resistor of 13.1 kΩ. Choosing 12 kΩ as the nearest standard value gives a current of approximately 55 µA. The 5.0 µA difference can be taken up by the tuning resistor, RT. The best nominal frequency for the AFTout pin (Pin 17) would be half supply. A supply voltage of 3.0 Vdc suggests a resistor value of (1.5 – 0.655)V/5.0 µA = 169 kΩ. Choosing 150 kΩ would give a tuning current of 3/150 k = 20 µA. From Figure 9 this would give a tuning range of roughly 10 kHz/µA or ± 100 kHz which should be adequate. The bandwidth can be adjusted with the help of Figure 11. For example, 1.0 µA would give a bandwidth of ± 13 kHz. The 10–4 So, for example, 150 k and 1.0 µF give a 3.0 dB point of 4.5 Hz. The recovered audio is set by RL to give roughly 50mV per kHz deviation per 100 k of resistance. The dc level can be shifted by RS from the nominal 0.68 V by the following equation: Detector DC Output = ((RL + RS)/RS) 0.68 Vdc Thus, RS = RL sets the output at 2 x 0.68 = 1.36 V; RL = 2RS sets the output at 3 x 0.68 = 2.0 V. Figure 12. BWadj Current versus BWadj Voltage Figure 13. Demodulator Output versus Frequency 10 VCC = 3.0 Vdc TA = 25°C 10–5 10–6 10–7 2.3 RTCT = 0.68/f3dB. DEMODULATOR OUTPUT (dB) BWadj CURRENT (A) 10–3 voltage across the bandwidth resistor, RB from Figure 12 is VCC – 2.44 Vdc = 0.56 Vdc for VCC = 3.0 Vdc, so RB = 0.56V/1.0 µA = 560 kΩ. Actually the locking range will be ±13 kHz while the audio bandwidth will be approximately ±8.4 kHz due to an internal filter capacitor. This is verified in Figure 13. For some applications it may be desirable that the audio bandwidth is increased; this is done by reducing RB. Reducing RB widens the detector bandwidth and improves the distortion at high input levels at the expense of 12 dB SINAD sensitivity. The low frequency 3.0dB point is set by the tuning circuit such that the product 2.5 BWadj VOLTAGE (Vdc) MOTOROLA ANALOG IC DEVICE DATA 2.7 0 RB = 560 k –10 –20 –30 –40 –50 0.1 VCC = 3.0 Vdc TA = 25°C fRF = 50 MHz fLO = 50.455 MHz LO Level = –10 dBm No IF Bandpass Filters fdev = ±4.0 kHz 1.0 RB = 1.0 M 10 100 f, FREQUENCY (kHz) 7 MC13150 APPLICATIONS INFORMATION shown in Figures 27 and 28 for the application circuit in Figure 15 and for the 83.616 MHz crystal oscillator circuit in Figure 16. Evaluation PC Board The evaluation PCB is very versatile and is intended to be used across the entire useful frequency range of this device. The center section of the board provides an area for attaching all SMT components to the circuit side and radial leaded components to the component ground side (see Figures 29 and 30). Additionally, the peripheral area surrounding the RF core provides pads to add supporting and interface circuitry as a particular application dictates. There is an area dedicated for a LNA preamp. This evaluation board will be discussed and referenced in this section. Input Matching Components The input matching circuit shown in the application circuit schematic (Figure 15) is a series L, shunt C single L section which is used to match the mixer input to 50 Ω. An alternative input network may use 1:4 surface mount transformers or BALUNs. The 12 dB SINAD sensitivity using the 1:4 impedance transformer is typically –100 dBm for fmod = 1.0 kHz and fdev = ±5.0 kHz at fin = 50 MHz and fLO = 50.455 MHz (see Figure 14). It is desirable to use a SAW filter before the mixer to provide additional selectivity and adjacent channel rejection and improved sensitivity. SAW filters sourced from Toko (Part # SWS083GBWA) and Murata (Part # SAF83.16MA51X) are excellent choices to easily interface with the MC13150 mixer. They are packaged in a 12 pin low profile surface mount ceramic package. The center frequency is 83.161 MHz and the 3.0 dB bandwidth is 30 kHz. Component Selection The evaluation PC board is designed to accommodate specific components, while also being versatile enough to use components from various manufacturers and coil types. The applications circuit schematic (Figure 15) specifies particular components that were used to achieve the results shown in the typical curves but equivalent components should give similar results. Component placement views are Figure 14. S+N+D, N+D, N, 30% AMR versus Input Signal Level S+N+D, N+D, N, 30% AMR (dB) 20 10 S+N+D 0 –10 –20 –30 –40 –50 VCC = 3.0 Vdc fmod = 1.0 kHz fdev = ±5.0 kHz fin = 50 MHz N+D 30% AMR fLO = 50.455 MHz LO Level = –10 dBm See Figure 15 N –60 –120 –100 –80 –60 –40 INPUT SIGNAL (dBm) 8 MOTOROLA ANALOG IC DEVICE DATA MC13150 Figure 15. Application Circuit (3) LO Input (1) 180 nH RF/IF Input (4) Enable (5) RSSI 11 p 100 n 51 100 n 32 31 30 29 28 27 26 82 k 25 VEE1 (2) 455 kHz IF Ceramic Filter 2 RSSI Buffer 24 1 Mixer VCC1 Detector Output 23 RSSI Buffer 3 1.0 n 22 Local Oscillator VEE2 4 21 5 20 RL 150 k RS 150 k 100 n 100 n 6 IF 7 Limiter 1.0 n (6) 19 Detector 1.0 n 18 100 n 17 8 1.0 µ CT VCC2 9 10 11 12 13 14 15 16 150 k RT 100 n 455 kHz IF Ceramic Filter 100 n 10 µ 560 k RB 12 k RF (6) Coilless Detector Circuit + VCC NOTES: 1. Alternate solution is 1:4 impedance transformer (sources include Mini Circuits, Coilcraft and Toko). 2. 455 kHz ceramic filters (source Murata CFU455 series which are selected for various bandwidths). 3. For external LO source, a 51 Ω pull–up resistor is used to bias the base of the on–board transistor as shown in Figure 15. Designer may provide local oscillator with 3rd, 5th, or 7th overtone crystal oscillator circuit. The PC board is laid out to accommodate external components needed for a Butler emitter coupled crystal oscillator (see Figure 16). 4. Enable IC by switching the pin to VEE. 5. The resistor is chosen to set the range of RSSI voltage output swing. 6. Details regarding the external components to setup the coilless detector are provided in the application section. MOTOROLA ANALOG IC DEVICE DATA 9 MC13150 A series LC network to ac ground (which is VCC) is comprised of the inductance of the base lead of the on–chip transistor and PC board traces and tap capacitors. Parasitic oscillations often occur in the 200 to 800 MHz range. A small resistor is placed in series with the base (Pin 28) to cancel the negative resistance associated with this undesired mode of oscillation. Since the base input impedance is so large, a small resistor in the range of 27 to 68 Ω has very little effect on the desired Butler mode of oscillation. The crystal parallel capacitance, Co, provides a feedback path that is low enough in reactance at frequencies of 5th overtones or higher to cause trouble. Co has little effect near resonance because of the low impedance of the crystal motional arm (Rm–Lm–Cm). As the tunable inductor, which forms the resonant tank with the tap capacitors, is tuned off the crystal resonant frequency, it may be difficult to tell if the oscillation is under crystal control. Frequency jumps may occur as the inductor is tuned. In order to eliminate this behavior an inductor, Lo, is placed in parallel with the crystal. Lo is chosen to resonant with the crystal parallel capacitance, Co, at the desired operation frequency. The inductor provides a feedback path at frequencies well below resonance; however, the parallel tank network of the tap capacitors and tunable inductor prevent oscillation at these frequencies. Local Oscillators HF & VHF Applications In the application schematic, an external sourced local oscillator is utilized in which the base is biased via a 51 Ω resistor to VCC. However, the on–chip grounded collector transistor may be used for HF and VHF local oscillators with higher order overtone crystals. Figure 16 shows a 5th overtone oscillator at 83.616 MHz. The circuit uses a Butler overtone oscillator configuration. The amplifier is an emitter follower. The crystal is driven from the emitter and is coupled to the high impedance base through a capacitive tap network. Operation at the desired overtone frequency is ensured by the parallel resonant circuit formed by the variable inductor and the tap capacitors and parasitic capacitances of the on–chip transistor and PC board. The variable inductor specified in the schematic could be replaced with a high tolerance, high Q ceramic or air wound surface mount component if the other components have tight enough tolerances. A variable inductor provides an adjustment for gain and frequency of the resonant tank ensuring lock up and start–up of the crystal oscillator. The overtone crystal is chosen with ESR of typically 80 Ω and 120 Ω maximum; if the resistive loss in the crystal is too high the performance of oscillator may be impacted by lower gain margins. Figure 16. MC13150FTB Overtone Oscillator fRF = 83.16 MHz; fLO = 83.616 MHz 5th Overtone Crystal Oscillator (4) 0.135 µH MC13150 + 1.0 µ 33 Mixer 28 1.0 µH 39 p 39 p 29 (3) 27 k 5th OT XTAL VEE 10 n 31 VCC 10 MOTOROLA ANALOG IC DEVICE DATA MC13150 application circuit (Figure 15), the input 1.0 dB compression point is –10 dBm and the input third order intercept (IP3) performance of the system is approximately 0 dBm (see Figure 18). Receiver Design Considerations The curves of signal levels at various portions of the application receiver with respect to RF input level are shown in Figure 17. This information helps determine the network topology and gain blocks required ahead of the MC13150 to achieve the desired sensitivity and dynamic range of the receiver system. The PCB is laid out to accommodate a low noise preamp followed by the 83.16 MHz SAW filter. In the Typical Performance Over Temperature Figures 19–26 show the device performance over temperature. Figure 17. Signal Levels versus RF Input Signal Level 10 0 IF Output POWER (dBm) –10 –20 Limiter Input –30 RF Input at Transformer Input Mixer Output Mixer Input –40 IF Input –50 fRF = 50 MHz fLO = 50.455 MHz; LO Level = –10 dBm See Figure 15 –60 –70 –80 –70 –60 –50 –40 –30 –20 –10 0 RF INPUT SIGNAL LEVEL (dBm) MOTOROLA ANALOG IC DEVICE DATA 11 MC13150 Figure 18. 1.0 dB Compression Point and Input Third Order Intercept Point versus Input Power MIXER IF OUTPUT LEVEL (dBm) 20 1.0 dB Compression Point = –11 dBm VCC = 3.0 Vdc fRF1 = 50 MHz fRF2 = 50.01 MHz fLO = 50.455 MHz PLO = –10 dBm See Figure 15 0 IP3 = –0.5 dBm –20 –40 –60 –80 –60 –40 –20 0 20 RF INPUT POWER (dBm) TYPICAL PERFORMANCE OVER TEMPERATURE Figure 19. Supply Current, IVEE1 versus Signal Input Level Figure 20. Supply Current, IVEE2 versus Ambient Temperature 0.35 4.5 4.0 3.5 VCC = 3.0 Vdc fc = 50 MHz fdev = ±4.0 kHz IVEE2 , SUPPLY CURRENT (mA) IVEE1, SUPPLY CURRENT (mA) 5.0 3.0 2.5 TA = 85°C 2.0 1.5 1.0 0.5 0 –120 TA = 25°C 0.3 0.25 TA = –40°C 0.2 –105 –90 –75 –60 –45 SIGNAL INPUT LEVEL (dBm) 12 VCC = 3.0 Vdc –30 –15 0 –40 –20 0 20 40 60 80 TA, AMBIENT TEMPERATURE (°C) MOTOROLA ANALOG IC DEVICE DATA MC13150 TYPICAL PERFORMANCE OVER TEMPERATURE Figure 21. Total Supply Current versus Ambient Temperature Figure 22. Minimum Supply Voltage versus Ambient Temperature 3.0 1.75 MINIMUM SUPPLY VOLTAGE (Vdc) TOTAL SUPPLY CURRENT (mA) 1.8 VCC = 3.0 Vdc 1.7 1.65 1.6 1.55 1.5 1.45 1.4 –20 0 20 40 60 1.5 80 –40 –20 0 20 40 60 80 TA, AMBIENT TEMPERATURE (°C) TA, AMBIENT TEMPERATURE (°C) Figure 23. RSSI Current versus Ambient Temperature and Signal Level Figure 24. Recovered Audio versus Ambient Temperature 0.7 60 Vin = 40 0 dBm –20 dBm 30 –40 dBm 20 –60 dBm –80 dBm –100 dBm 10 RECOVERED AUDIO (Vpp ) VCC = 3.0 Vdc fRF = 50 MHz 50 RSSI CURRENT ( µA) 2.0 1.0 –40 –120 dBm 0 –40 –20 0 20 40 60 80 0.65 0.6 0.55 VCC = 3.0 Vdc RF In = –50 dBm fc = 50 MHz fLO = 50.455 MHz fdev = ±4.0 kHz 0.5 0.45 0.4 100 –40 –20 0 20 40 60 80 TA, AMBIENT TEMPERATURE (°C) TA, AMBIENT TEMPERATURE (°C) Figure 25. Demod DC Output Voltage versus Ambient Temperature Figure 26. LO Current versus Ambient Temperature 100 100 1.7 VCC = 3.0 Vdc RF In = –50 dBm fc = 50 MHz fLO = 50.455 MHz fdev = ±4.0 kHz 1.6 1.5 1.4 1.3 1.2 1.1 VCC = 3.0 Vdc RF In = –50 dBm fc = 50 MHz fLO = 50.455 MHz fdev = ±4.0 kHz 90 LO CURRENT ( µA) DEMOD DC OUTPUT VOLTAGE (Vdc) 2.5 80 70 60 1.0 0.9 –40 50 –20 0 20 40 60 TA, AMBIENT TEMPERATURE (°C) MOTOROLA ANALOG IC DEVICE DATA 80 –40 –20 0 20 40 60 80 TA, AMBIENT TEMPERATURE (°C) 13 MC13150 Figure 27. Component Placement View – Circuit Side 100 n 10 n 50 Ω Semi–Rigid Coax 39 p 33 39 p 27 k 82 k 1n 11 p 180 n 150 k MC13150FTB 150 k 100 n 100 n 1n 1n 1 µ 1n 150 k 100 n 560 k 1n 12 k + 100 n 10 µ GND 14 VCC MOTOROLA ANALOG IC DEVICE DATA MC13150 Figure 28. Component Placement View – Ground Side VCC BW_adj F_adj DET_out GND 455 kHz Ceramic Filter 455 kHz Ceramic Filter RSSI AFT_adj 455 kHz Ceramic Filter 455 kHz Ceramic Filter 1 µH 83.616 MHz ENABLE Xtal 135 nH LO Tuning SMA LO IN RF1 IN RF2 IN 3.8″ MOTOROLA ANALOG IC DEVICE DATA 15 MC13150 Figure 29. PCB Circuit Side View GND VCC MC13150 Rev 0 3/95 3.8″ 16 MOTOROLA ANALOG IC DEVICE DATA MC13150 Figure 30. PCB Ground Side View VCC BW_adj F_adj DET_out GND 455 kHz Ceramic Filter RSSI AFT_adj 455 kHz Ceramic Filter ENABLE Xtal LO Tuning LO IN RF1 IN RF2 IN 3.8″ MOTOROLA ANALOG IC DEVICE DATA 17 MC13150 OUTLINE DIMENSIONS FTA SUFFIX PLASTIC PACKAGE CASE 977–01 (LQFP–24) ISSUE O 4X 9 NOTES: 1 DIMENSIONING AND TOLERANCING PER ANSI Y14.5M, 1982. 2 CONTROLLING DIMENSION: MILLIMETER. 3 DATUM PLANE –AB– IS LOCATED AT BOTTOM OF LEAD AND IS COINCIDENT WITH THE LEAD WHERE THE LEAD EXITS THE PLASTIC BODY AT THE BOTTOM OF THE PARTING LINE. 4 DATUMS –T–, –U–, AND –Z– TO BE DETERMINED AT DATUM PLANE –AB–. 5 DIMENSIONS S AND V TO BE DETERMINED AT DATUM PLANE –AC–. 6 DIMENSIONS A AND B DO NOT INCLUDE MOLD PROTRUSION. ALLOWABLE PROTRUSION IS 0.250 (0.010) PER SIDE. DIMENSIONS A AND B DO INCLUDE MOLD MISMATCH AND ARE DETERMINED AT DATUM PLANE –AB–. 7 DIMENSION D DOES NOT INCLUDE DAMBAR PROTRUSION. DAMBAR PROTRUSION SHALL NOT CAUSE THE D DIMENSION TO EXCEED 0.350 (0.014). 8 MINIMUM SOLDER PLATE THICKNESS SHALL BE 0.0076 (0.0003). 9 EXACT SHAPE OF EACH CORNER IS OPTIONAL. 0.200 (0.008) AB T–U Z A A1 24 –T– DETAIL Y 19 1 18 –U– V B V1 13 6 7 B1 12 –Z– S1 S 4X 0.200 (0.008) AB T–U Z DETAIL AD DIM A A1 B B1 C D E F G H J K M N P Q R S S1 V V1 W X MILLIMETERS MIN MAX 4.000 BSC 2.000 BSC 4.000 BSC 2.000 BSC 1.400 1.600 0.170 0.270 1.350 1.450 0.170 0.230 0.500 BSC 0.050 0.150 0.090 0.200 0.500 0.700 12_REF 0.090 0.160 0.250 BSC 1_ 5_ 0.150 0.250 6.000 BSC 3.000 BSC 6.000 BSC 3.000 BSC 0.200 REF 1.000 REF INCHES MIN MAX 0.157 BSC 0.079 BSC 0.157 BSC 0.079 BSC 0.055 0.063 0.007 0.011 0.053 0.057 0.007 0.009 0.020 BSC 0.002 0.006 0.004 0.008 0.020 0.028 12 _REF 0.004 0.006 0.010 BSC 1_ 5_ 0.006 0.010 0.236 BSC 0.118 BSC 0.236 BSC 0.118 BSC 0.008 REF 0.039 REF –AB– –AC– 0.080 (0.003) AC M_ TOP & BOTTOM –T–, –U–, –Z– J R C E AE AE ÇÇÇ ÉÉÉ ÉÉÉ ÇÇÇ ÉÉÉ ÇÇÇ N F D 0.080 (0.003) W H K X DETAIL AD 18 Q_ GAUGE PLANE 0.250 (0.010) P S AC T–U S Z S SECTION AE–AE G DETAIL Y MOTOROLA ANALOG IC DEVICE DATA MC13150 OUTLINE DIMENSIONS FTB SUFFIX PLASTIC PACKAGE CASE 873–01 (LQFP–32) ISSUE A L B 24 S D S S H A–B DETAIL A 32 V M B -A-,-B-,-DDETAIL A J 9 1 F BASE METAL 0.20 (0.008) L S -B- -A- D 16 0.20 (0.008) M C A–B 0.05 (0.002) A–B 25 P B 17 N 8 D -D- 0.20 (0.008) M C A–B S D A 0.20 (0.008) M C A–B 0.05 (0.002) A–B D S SECTION B-B S VIEW ROTATED 90° CLOCKWISE S 0.20 (0.008) M H A–B D S S C E -H- -CSEATING PLANE DETAIL C M H M G U T R -HDATUM PLANE K X DETAIL C MOTOROLA ANALOG IC DEVICE DATA Q DATUM PLANE 0.01 (0.004) NOTES: 1. DIMENSIONING AND TOLERANCING PER ANSI Y14.5M, 1982. 2. CONTROLLING DIMENSION: MILLIMETER. 3. DATUM PLANE -H- IS LOCATED AT BOTTOM OF LEAD AND IS COINCIDENT WITH THE LEAD WHERE THE LEAD EXITS THE PLASTIC BODY AT THE BOTTOM OF THE PARTING LINE. 4. DATUMS -A-, -B- AND -D- TO BE DETERMINED AT DATUM PLANE -H-. 5. DIMENSIONS S AND V TO BE DETERMINED AT SEATING PLANE -C-. 6. DIMENSIONS A AND B DO NOT INCLUDE MOLD PROTRUSION. ALLOWABLE PROTRUSION IS 0.25 (0.010) PER SIDE. DIMENSIONS A AND B DO INCLUDE MOLD MISMATCH AND ARE DETERMINED AT DATUM PLANE -H-. 7. DIMENSION D DOES NOT INCLUDE DAMBAR PROTRUSION. ALLOWABLE DAMBAR PROTRUSION SHALL BE 0.08 (0.003) TOTAL IN EXCESS OF THE D DIMENSION AT MAXIMUM MATERIAL CONDITION. DAMBAR CANNOT BE LOCATED ON THE LOWER RADIUS OR THE FOOT. DIM A B C D E F G H J K L M N P Q R S T U V X MILLIMETERS MIN MAX 7.10 6.95 7.10 6.95 1.60 1.40 0.273 0.373 1.50 1.30 — 0.273 0.80 BSC 0.20 — 0.119 0.197 0.57 0.33 5.6 REF 8° 6° 0.119 0.135 0.40 BSC 5° 10° 0.15 0.25 8.85 9.15 0.15 0.25 5° 11° 8.85 9.15 1.0 REF INCHES MIN MAX 0.274 0.280 0.274 0.280 0.055 0.063 0.010 0.015 0.051 0.059 — 0.010 0.031 BSC 0.008 — 0.005 0.008 0.013 0.022 0.220 REF 8° 6° 0.005 0.005 0.016 BSC 5° 10° 0.006 0.010 0.348 0.360 0.006 0.010 5° 11° 0.348 0.360 0.039 REF 19 S MC13150 Motorola reserves the right to make changes without further notice to any products herein. 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Mfax is a trademark of Motorola, Inc. How to reach us: USA / EUROPE / Locations Not Listed: Motorola Literature Distribution; P.O. Box 5405, Denver, Colorado 80217. 1–303–675–2140 or 1–800–441–2447 JAPAN: Nippon Motorola Ltd.: SPD, Strategic Planning Office, 4–32–1, Nishi–Gotanda, Shinagawa–ku, Tokyo 141, Japan. 81–3–5487–8488 Customer Focus Center: 1–800–521–6274 Mfax: [email protected] – TOUCHTONE 1–602–244–6609 ASIA/PACIFIC: Motorola Semiconductors H.K. Ltd.; 8B Tai Ping Industrial Park, Motorola Fax Back System – US & Canada ONLY 1–800–774–1848 51 Ting Kok Road, Tai Po, N.T., Hong Kong. 852–26629298 – http://sps.motorola.com/mfax/ HOME PAGE: http://motorola.com/sps/ 20 ◊ MC13150/D MOTOROLA ANALOG IC DEVICE DATA