TI TPS60132PWP

TPS60130, TPS60131, TPS60132, TPS60133
REGULATED 5-V, 300 mA HIGH EFFICIENCY CHARGE PUMP
DC/DC CONVERTERS
SLVS258A – NOVEMBER 1999 – REVISED DECEMBER 1999
features
D
D
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D
D
D
D
D
D
D
applications
Up to 90% Efficiency From 2.7-V to 5.4-V
Input Voltage Range Because of Special
Switching Topology
Up to 300-mA Output Current (TPS60130
and TPS60131)
No Inductors Required, Low EMI
Regulated 5-V ±4% Output
Only Four External Components Required
60-µA Quiescent Supply Current
0.05-µA Shutdown Current
Load Disconnected in Shutdown
Space-Saving, Thermally-Enhanced
PowerPADt Package
Evaluation Module Available
(TPS60130EVM–143)
D
D
D
D
D
D
D
D
D
D
Battery-Powered Applications
Three Battery Cells to 5-V Conversion or
Point-of-Use 3.3 V to 5-V Conversion
Lilon Battery to 5-V Conversion
Portable Instruments
Battery-Powered Microprocessor Systems
Backup-Battery Boost Converters
PDA’s, Organizers, Laptops
Handheld Instrumentation
Medical Instruments (e.g., Glucose Meters)
PCMCIA and 5-V Smart Card Supply
description
The TPS6013x step-up, regulated charge pumps generate a 5-V ±4% output voltage from a 2.7-V to 5.4-V input
voltage (three alkaline, NiCd, or NiMH batteries or one Lithium or Lilon battery). The output current is 300 mA
for the TPS60130/ TPS60131 and 150 mA for the TPS60132/ TPS60133, all from a 3-V input. Only four external
capacitors are needed to build a complete high efficiency dc/dc charge pump converter. To achieve the high
efficiency over a wide input voltage range, the charge pump automatically selects between a 1.5x or doubler
conversion mode. From a 3-V input, all ICs can start with full load current.
efficiency (TPS60130, TPS60131)
100
typical operating circuit
IO = 66 mA
Input
2.7 V to 5.4 V
90
IO = 216 mA
80
Ci
15 µF
Efficiency – %
70
60
TPS60130
IO = 108 mA
R1
IN
OUT
IN
OUT
LBI
IO = 300 mA
R2
C1
2.2 µF
30
20
OFF/ON
Co
33 µF
R3
LBO
50
40
FB
Output
5 V, 300 mA
C1+
C2+
C1–
C2–
C2
2.2 µF
ENABLE
PGND GND
10
0
2.6
3
4.6
3.4
3.8
4.2
VI – Input Voltage – V
5
5.4
Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of
Texas Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet.
PowerPAD is a trademark of Texas Instruments Incorporated.
Copyright  1999, Texas Instruments Incorporated
PRODUCTION DATA information is current as of publication date.
Products conform to specifications per the terms of Texas Instruments
standard warranty. Production processing does not necessarily include
testing of all parameters.
POST OFFICE BOX 655303
• DALLAS, TEXAS 75265
1
TPS60130, TPS60131, TPS60132, TPS60133
REGULATED 5-V, 300 mA HIGH EFFICIENCY CHARGE PUMP
DC/DC CONVERTERS
SLVS258A – NOVEMBER 1999 – REVISED DECEMBER 1999
description (continued)
The devices feature the power-saving pulse-skip mode to extend battery life at light loads. TPS60130 and
TPS60132 include a low-battery comparator; TPS60131 and TPS60133 feature a power-good output. The logic
shut-down function reduces the supply current to 1 µA (max) and disconnects the load from the input. Special
current-control circuitry prevents excessive current from being drawn from the battery during startup. This dc/dc
converter requires no inductors and therefore EMI is of low concern. It is available in the small, thermally
enhanced 20-pin PowerPAD package (PWP).
t
PWP PACKAGE
(TPS60130/TPS60132)
(TOP VIEW)
GND
GND
ENABLE
FB
OUT
C1+
IN
C1–
PGND
PGND
1
2
3
4
5
6
7
8
9
10
20
19
18
17
16
15
14
13
12
11
PWP PACKAGE
(TPS60131/TPS60133)
(TOP VIEW)
GND
GND
ENABLE
FB
OUT
C1+
IN
C1–
PGND
PGND
GND
GND
LBI
LBO
OUT
C2+
IN
C2–
PGND
PGND
1
2
3
4
5
6
7
8
9
10
20
19
18
17
16
15
14
13
12
11
GND
GND
NC
PG
OUT
C2+
IN
C2–
PGND
PGND
Thermal Pad
AVAILABLE OPTIONS
TA
PART NUMBER†
PACKAGE
TPS60130PWP
– 40°C to 85°C
TPS60131PWP
TPS60132PWP
PWP
20-Pin thermally
y
enhanced TSSOP
TPS60133PWP
DEVICE FEATURES
3 cell to 5 V,
V 300 mA
3-cell
3-cell to 5 V,
V 150 mA
Low battery detector
Power good detector
Low battery detector
Power good detector
† The PWP package is available taped and reeled. Add R suffix to device type (e.g. TPS60130PWPR) to order quanities of 2000
devices per reel.
2
POST OFFICE BOX 655303
• DALLAS, TEXAS 75265
TPS60130, TPS60131, TPS60132, TPS60133
REGULATED 5-V, 300 mA HIGH EFFICIENCY CHARGE PUMP
DC/DC CONVERTERS
SLVS258A – NOVEMBER 1999 – REVISED DECEMBER 1999
functional block diagram
TPS60130/TPS60132
IN
C1+
Oscillator
C1F
ENABLE
Charge Pump
Power Stages
Control
Circuit
C1–
OUT
PGND
IN
C2+
C2F
_
C2–
OUT
PGND
+
+
VREF –
Shutdown/
Start-Up
Control
FB
_
_
+
LBI
+
+
–
0.8 VI
+
VREF –
GND
LBO
TPS60131/TPS60133
IN
C1+
Oscillator
C1F
C1–
OUT
ENABLE
Charge Pump
Power Stages
Control
Circuit
PGND
IN
C2+
C2F
_
C2–
+
VREF
Shutdown/
Start-Up Control
OUT
PGND
+
–
FB
_
_
+
+
+
–
0.8 VI
GND
POST OFFICE BOX 655303
VREF
+
–
PG
• DALLAS, TEXAS 75265
3
TPS60130, TPS60131, TPS60132, TPS60133
REGULATED 5-V, 300 mA HIGH EFFICIENCY CHARGE PUMP
DC/DC CONVERTERS
SLVS258A – NOVEMBER 1999 – REVISED DECEMBER 1999
Terminal Functions
TERMINAL
NAME
C1+
NO.
I/O
DESCRIPTION
6
Positive terminal of the flying capacitor C1
C1–
8
Negative terminal of the flying capacitor C1
C2+
15
Positive terminal of the flying capacitor C2
C2–
13
Negative terminal of the flying capacitor C2
ENABLE
3
I
Enable input. Connect ENABLE to IN for normal operation. When ENABLE is a logic low, the device turns off and
the supply current decreases to 0.05 µA. The output is disconnected from the input when the device is disabled.
FB
4
I
Feedback input. Connect FB to OUT as close to the load as possible to achieve best regulation. A resistive divider
is on the chip to match internal reference voltage of 1.21 V.
GND
1, 2,
19, 20
IN
Ground. Analog ground for internal reference and control circuitry. Connect to PGND terminals through a short
trace.
7,14
I
Supply input. Bypass IN to PGND with a capacitor that has half of the capacitance of the output capacitor. Connect
both IN terminals together through a short trace.
LBO/PG
17
O
Low battery detector output (TPS60130 and TPS60132) or power good output (TPS60131 and TPS60133). Open
drain output of the low battery or power good comparator. It can sink 1 mA. A 100-kΩ to 1-MΩ pullup resistor to OUT
is recommended. Leave the terminal unconnected if the low battery or power good detector is not used.
LBI/NC
18
I
Low battery detector input (TPS60130 and TPS60132 only). The voltage at this input is compared to the internal
1.21 V reference voltage. Connect this terminal to ground if the low-battery detection function is not used. On the
TPS60131 and TPS60133, this terminal is not connected.
OUT
5, 16
O
Regulated 5-V power output. Connect both OUT terminals through a short trace and bypass OUT to GND with the
output filter capacitor CO.
PGND
9–12
Power ground. Charge-pump current flows through this pin. Connect all PGND terminals together.
detailed description
operating principle
The TPS6013x charge pumps provide a regulated 5-V output from a 2.7-V to 5.4-V input. They deliver a
maximum load current of 300 mA or 150 mA, respectively. Designed specifically for space-critical, batterypowered applications, the complete charge pump circuit requires four external capacitors. The circuit is
optimized for efficiency over a wide input voltage range.
The TPS6013x charge pumps consist of an oscillator, a 1.21-V bandgap reference, an internal resistive
feedback circuit, an error amplifier, high current MOSFET switches, a shutdown/startup circuit, a low-battery
or power-good comparator, and a control circuit (see functional block diagrams).
The device consists of two single-ended charge pumps. These charge pumps are automatically configured to
amplify the input voltage with a conversion factor of 1.5 or 2. The conversion ratio is dependent on the input
voltage and load current. This assures high efficiency over a wide input voltage range and is further described
in the adaptive mode switching section below.
adaptive mode switching
The ON-resistance of the MOSFETs that are in the charge path of the flying capacitors is regulated when the
charge pump operates in voltage doubler mode. It is changed depending on the output voltage that is fed back
into the control loop. This way, the time-constant during the charging phase can be modified and increased
versus a time-constant for fully switched-on MOSFETs. The ON-resistance of both switches and the
capacitance of the flying capacitor define the time constant. The MOSFET switches in the discharge path of the
charge pump are always fully switched on to their minimum rDS(on). With the time-constant during charge phase
being bigger than the time constant in discharge phase, the voltage on the flying capacitors stabilizes to the
lowest possible value necessary to get a stable VO.
4
POST OFFICE BOX 655303
• DALLAS, TEXAS 75265
TPS60130, TPS60131, TPS60132, TPS60133
REGULATED 5-V, 300 mA HIGH EFFICIENCY CHARGE PUMP
DC/DC CONVERTERS
SLVS258A – NOVEMBER 1999 – REVISED DECEMBER 1999
adaptive mode switching (continued)
The voltage on the flying capacitors is measured and compared with the supply voltage VI. If the voltage across
the flying capacitors is smaller than half of the supply voltage, then the charge pump switches into the
1.5x conversion-mode. The charge pump switches back from a 1.5x conversion-mode to a voltage doubler
mode if the load current in 1.5x conversion-mode can no more be delivered.
With this control mode the device runs in doubler -mode at low VI and in 1.5x conversion-mode at high VI to
optimize the efficiency. The most desirable transfer mode is automatically selected depending on both VI and
IL. This means that at light loads the device selects the 1.5x conversion-mode already at smaller supply voltages
than at heavy loads.
The TPS60130 output voltage is regulated using the ACTIVE-CYCLE-regulation. An active cycle controlled
charge pump utilizes two methods to control the output voltage. At high load currents it varies the on-resistances
of the internal switches and keeps the ratio ON/OFF time (=frequency) constant. That means the charge pump
runs at a fixed frequency. It also keeps the output voltage ripple as low as in linear-mode. At light loads the
internal resistance and also the amount of energy transferred per pulse is fixed and the charge pump regulates
the voltage by means of a variable ratio of ON-to-OFF time. In this operating point it runs like a skip mode
controlled charge pump with a very high internal resistance, which also enables a low ripple in this operation
mode. Since the charge pump does effectively switch at lower frequencies at light loads, it achieves a low
quiescent current.
pulse-skip mode
In pulse-skip mode the error amplifier disables switching of the power stages when it detects an output higher
than 5 V. The oscillator halts and the IC then skips switching cycles until the output voltage drops below 5 V.
The error amplifier reactivates the oscillator and starts switching the power stages again. The pulse-skip
regulation mode minimizes operating current because it does not switch continuously and deactivates all
functions except bandgap reference, error amplifier, and low-battery/power-good comparator when the output
is higher than 5 V. When switching is disabled from the error amplifier, the load is also isolated from the input.
In pulse-skip mode, a special current control circuitry, limits the peak current. This assures moderate output
voltage ripple and also prevents the device from drawing excessive current spikes out of the battery.
start-up procedure
During start-up, i.e. when ENABLE is set from logic low to logic high, the output capacitor is charged up, with
a limited current, until the output voltage VO reaches 0.8 × VI. When the start-up comparator detects this voltage
limit, the IC begins switching. This start-up charging of the output capacitor assures a short start-up time and
eliminates the need of a Schottky diode between IN and OUT. The IC starts with a maximum load, which is
defined by a 16-Ω or 33-Ω resistor, respectively.
shutdown
Driving ENABLE low places the device in shutdown mode. This disables all switches, the oscillator, and control
logic. The device typically draws 0.05 µA (1 µA max) of supply current in this mode. Leakage current drawn from
the output is as low as 1 µA max. The device exits shutdown once ENABLE is set to a high level. The typical
no-load shutdown exit time is 10 µs. When the device is in shutdown, the load is isolated from the input.
undervoltage lockout
The TPS6013x devices have an undervoltage lockout feature that deactivates the device and places it in
shutdown mode when the input voltage falls below 1.6 V.
low-battery detector (TPS60130 and TPS60132)
The internal low-battery comparator trips at 1.21 V ±5% when the voltage on pin LBI ramps down. The battery
voltage at which the comparator initiates a low battery warning at the LBO output can easily be programmed
with a resistive divider as shown in Figure 3. The sum of resistors R1 and R2 is recommended to be in the 100-kΩ
to 1-MΩ range.
POST OFFICE BOX 655303
• DALLAS, TEXAS 75265
5
TPS60130, TPS60131, TPS60132, TPS60133
REGULATED 5-V, 300 mA HIGH EFFICIENCY CHARGE PUMP
DC/DC CONVERTERS
SLVS258A – NOVEMBER 1999 – REVISED DECEMBER 1999
low-battery detector (TPS60130 and TPS60132) (continued)
LBO is an open drain output. An external pullup resistor to OUT, in the 100-kΩ to 1-MΩ range is recommended.
During start-up, the LBO output signal is invalid for the first 500 µs. LBO is high impedance when the device
is disabled.
If the low-battery comparator function is not used, connect LBI to ground and leave LBO unconnected.
VOUT
IN
VBAT
R3
R1
LBO
V
LBI
_
+
VREF
TRIP
+ 1.21 V
ǒ) Ǔ
1
R1
R2
R2
+
–
Figure 1. Programming of the Low-Battery Comparator Trip Voltage
Formulas to calculate the resistive divider for low battery detection, with VLBI = 1.15 V – 1.27 V:
R2
R1
+ 1 MW
V
V
LBI
BAT
+ 1 MW * R2
Formulas to calculate the minimum and maximum battery voltage that triggers the low battery detector:
V
V
+ VLBI(min)
BAT(min)
+ VLBI(max)
BAT(max)
R1
(min)
R2
R1
) R2(max)
(max)
(max)
R2
) R2(min)
(min)
Table 1. Recommended Values for the Resistive Divider from the E96 Series (±1%),
VLBI = 1.15 V – 1.27 V
VBAT/V
R1/kΩ
R2/kΩ
VBAT(MIN)/V
VBAT(MAX)/V
2.7
562
453
2.548
–5.61%
2.877
6.57%
2.8
576
442
2.619
–6.47%
2.958
5.66%
2.9
590
422
2.726
–6.00%
3.081
6.26%
3.0
590
402
2.804
–6.53%
3.172
5.72%
3.1
604
383
2.928
–5.56%
3.313
6.88%
3.2
619
374
3.016
–5.76%
3.414
6.70%
3.3
649
374
3.106
–5.88%
3.518
6.62%
A 100 nF bypass capacitor should be connected in parallel to R2 if large line transients are expected. These
voltage drops can inadvertently trigger the low-battery comparator and produce a wrong low-battery warning
signal at the LBO pin.
6
POST OFFICE BOX 655303
• DALLAS, TEXAS 75265
TPS60130, TPS60131, TPS60132, TPS60133
REGULATED 5-V, 300 mA HIGH EFFICIENCY CHARGE PUMP
DC/DC CONVERTERS
SLVS258A – NOVEMBER 1999 – REVISED DECEMBER 1999
Power-Good detector (TPS60131 and TPS60133)
The PG pin is an open-drain output that is pulled low when the output is out of regulation. When the output
voltage rises to about 90% of its nominal voltage, power-good output is released. PG is high impedance when
the device is disabled. An external pullup resistor must be connected between PG and OUT. The pullup resistor
should be in the 100 kΩ to 1 MΩ range. If the power-good function is not used, the PG-pin should remain
unconnected.
TPS60131
Input
2.7 V to 5.4 V
Ci
15 µF
IN
OUT
IN
OUT
NC
FB
Output
5 V, 300 mA
R1
1 MΩ
Co
33 µF
PG
C1
2.2 µF
C1+
C2+
C1–
C2–
Power-Good Output
C2
2.2 µF
ENABLE
PGND GND
Off/On
Figure 2. Typical Operating Circuit Using Power-Good Comparator
absolute maximum ratings (see Note 1)†
Input voltage range, VI (IN, OUT, ENABLE, FB, LBI, LBO/PG) . . . . . . . . . . . . . . . . . . . . . . . . . . . –0.3 V to 5.5 V
Differential input voltage, VID (C1+, C2+ to GND) . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . –0.3 V to (VO + 0.3 V)
Differential input voltage, VID (C1–, C2– to GND) . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . –0.3 V to (VI + 0.3 V)
Continuous total power dissipation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . See Dissipation Rating Table
Continuous output current: TPS60130, TPS60131 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 400 mA
TPS60132, TPS60133 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 200 mA
Storage temperature range, Tstg . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . –55°C to 150°C
Lead temperature 1,6 mm (1/16 inch) from case for 10s . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 260°C
Maximum junction temperature, TJ . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 150°C
† Stresses beyond those listed under “absolute maximum ratings” may cause permanent damage to the device. These are stress ratings only, and
functional operation of the device at these or any other conditions beyond those indicated under “recommended operating conditions” is not
implied. Exposure to absolute-maximum-rated conditions for extended periods may affect device reliability.
NOTE 1: V(ENABLE), V(LBI) and V(LBO/PG) can exceed VI up to the maximum rated voltage without increasing the leakage current drawn by these
inputs.
DISSIPATION RATING TABLE FREE-AIR TEMPERATURE (see Figure 1)
PACKAGE
TA ≤ 25°C
POWER RATING
DERATING FACTOR
ABOVE TA = 25°C
TA = 70°C
POWER RATING
TA = 85°C
POWER RATING
PWP
700 mW
5.6 mW/°C
448 mW
364 mW
DISSIPATION RATING TABLE CASE TEMPERATURE (see Figure 2)
PACKAGE
TC ≤ 62.5°C
POWER RATING
DERATING FACTOR
ABOVE TC = 62.5°C
TC = 70°C
POWER RATING
TC = 85°C
POWER RATING
PWP
25 mW
285.7 mW/°C
22.9 mW
18.5 mW
POST OFFICE BOX 655303
• DALLAS, TEXAS 75265
7
TPS60130, TPS60131, TPS60132, TPS60133
REGULATED 5-V, 300 mA HIGH EFFICIENCY CHARGE PUMP
DC/DC CONVERTERS
SLVS258A – NOVEMBER 1999 – REVISED DECEMBER 1999
DISSIPATION DERATING CURVE†
vs
FREE-AIR TEMPERATURE
MAXIMUM CONTINUOUS DISSIPATION†
vs
CASE TEMPERATURE
30
PD – Maximum Continuous Dissipation – W
PD– Maximum Continuous Dissipation – mW
1400
1200
1000
800
PWP Package
RθJA = 178°C/W
600
400
200
0
25
50
75
100
125
TA – Free-Air Temperature – °C
150
25
20
PWP package
15
10
Measured with the exposed thermal pad
coupled to an infinite heat sink with a
thermally conductive compound (the thermal
conductivity of the compound is 0.815 W/m°C)
The RθJC is 3.5°C/W
5
0
25
Figure 3
125
50
75
100
TC – Case Temperature – °C
150
Figure 4
† Dissipation rating tables and figures are provided for maintenance of junction temperature at or below absolute maximum temperature of 150°C.
It is recommended not to exceed a junction temperature of 125°C.
recommended operating conditions
Input voltage, VI
Output current,
current IO
MAX
2.7
5.4
TPS60130 and TPS60131
300
TPS60132 and TPS60133
150
Operating junction temperature, TJ
8
MIN
125
POST OFFICE BOX 655303
• DALLAS, TEXAS 75265
UNIT
V
mA
°C
TPS60130, TPS60131, TPS60132, TPS60133
REGULATED 5-V, 300 mA HIGH EFFICIENCY CHARGE PUMP
DC/DC CONVERTERS
SLVS258A – NOVEMBER 1999 – REVISED DECEMBER 1999
electrical characteristics at CI = 15 µF, C1F = C2F = 2.2 µF, CO = 33 µF, TC = –40°C to 85°C, VI = 3 V,
V(FB) = VO and V(ENABLE) = VI (unless otherwise noted)
PARAMETER
VI
V(UVLO)
IO(MAX)
VO
TEST CONDITIONS
Input voltage
TYP
2.7
Input undervoltage lockout threshold
Maximum output
current
MIN
TC = 25°C
1.6
MAX
UNIT
5.4
V
1.8
V
TPS60130/TPS60131
300
mA
TPS60132/TPS60133
150
mA
2.7 V < VI < 3 V,
0 < IO < IO(MAX)/2,
TC = 0°C to 70°C
3 V < VI < 5 V,
0 < IO < IO(MAX)
Output voltage
5 V < VI < 5.4 V,
0 < IO < IO(MAX)
Ilkg(OUT)
IQ
Output leakage current
VI = 3.6 V,
VI = 3.6 V
V(ENABLE) = 0 V
Quiescent current (no-load input current)
IQ(SDN)
fOSC(INT)
Shutdown supply current
VI = 3.6 V,
V(ENABLE) = 0 V
VIL
VIH
Enable input voltage low
Ilkg(ENABLE)
Enable input leakage current
4.8
5.2
V
4.8
5.2
V
4.8
5.25
V
1
µA
100
µA
60
Internal switching frequency
210
VI = 2.7 V
VI = 5.4 V
Enable input voltage high
1
µA
320
450
kHz
0.3 x VI
V
0.1
µA
0.7 x VI
V(ENABLE) = VGND or VI
VI = 3.8 V, 1 mA < IO(max)
TC = 25°C
Output load regulation
0.05
V
0.01
0.002%
mA
Output line regulation
3 V < VI < 5 V, IO = 150 mA,
TC = 25°C
0.2
%/V
Short circuit current limit
VI = 3.6 V, VO = 0 V, TC = 25°C
115
mA
V(LBITRIP)
LBI trip voltage
TPS60130/TPS60132
II(LBI)
LBI input current
TPS60130/TPS60132
VI = 2.7 V to 3.3 V,
Hysteresis 0.8% for rising LBI,
TC = 0°C to 70°C
V(LBI) = 1.3 V
VO(LBO)
LBO output voltage
low (see Note 2)
TPS60130/TPS60132
V(LBI) = 0 V, I(LBO)(SINK) = 1 mA
Ilkg(LBO)
LBO leakage
current
TPS60130/TPS60132
V(LBI) = 1.3 V, V(LBO) = 5 V
V(PGTRIP)
Power-good trip
voltage
TPS60131/TPS60133
TC = 0°C to 70°C
Vhys(PG)
Power–good trip
voltage hysteresis
TPS60131/TPS60133
VO ramping negative,
TC = 0°C to 70°C
VO(PG)
Power-good output
voltage low
(see Note 2)
TPS60131/TPS60133
VO = 0 V,
Ilkg(PG)
Power-good
leakage current
TPS60131/TPS60133
VO = 5 V, V(PG) = 5 V
1.15
0.86 ×
VO
1.21
1.27
V
100
nA
0.4
V
0.01
0.1
µA
0.9 ×
VO
0.94 ×
VO
V
0.4
V
0.1
µA
0.8%
I(PG)(SINK) = 1 mA
0.01
NOTE 2: During start-up the LBO and PG output signal is invalid for the first 500 µs.
POST OFFICE BOX 655303
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9
TPS60130, TPS60131, TPS60132, TPS60133
REGULATED 5-V, 300 mA HIGH EFFICIENCY CHARGE PUMP
DC/DC CONVERTERS
SLVS258A – NOVEMBER 1999 – REVISED DECEMBER 1999
PARAMETER MEASUREMENT INFORMATION
TPS60130
Ci
4.7 µF + 15µF
R1
IN
OUT
IN
OUT
LBI
FB
R3
R2
C1
2.2 µF
OFF/ON
Co
3 x 10 µF
Used capacitor types:
Ci: Ceramic, X7R
Co: Ceramic, X7R
C1, C2: Ceramic, X7R
LBO
C1+
C2+
C1–
C2–
C2
2.2 µF
ENABLE
PGND GND
Figure 5. Circuit Used For Typical Characteristics Measurements
TYPICAL CHARACTERISTICS
Table of Graphs
FIGURE
6, 7
vs Input Voltage (TPS60130 and TPS60132)
8, 9
η
Efficiency
I
Supply Current
vs Input Voltage
VO
VO
Output Voltage
vs Output Current (TPS60130 and TPS60132)
11, 12
Output Voltage
vs Input Voltage (TPS60130 and TPS60132)
13, 14
VO
VPP
Output Voltage Ripple
vs Time
15 – 17
Output Voltage Ripple Amplitude
vs Input Voltage
18
f(OSC)
Oscillator Frequency
vs Input Voltage
19
VO
10
vs Output Current (TPS60130 and TPS60132)
10
Load Transient Response
20
Line Transient Response
21
Output Voltage
vs Time (Start-Up Timing)
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TPS60130, TPS60131, TPS60132, TPS60133
REGULATED 5-V, 300 mA HIGH EFFICIENCY CHARGE PUMP
DC/DC CONVERTERS
SLVS258A – NOVEMBER 1999 – REVISED DECEMBER 1999
TYPICAL CHARACTERISTICS
TPS60130
TPS60132
EFFICIENCY
vs
OUTPUT CURRENT
EFFICIENCY
vs
OUTPUT CURRENT
100
90
90
80
80
70
70
Efficiency – %
100
Efficiency – %
60
50
40
VI = 2.7 V
60
50
VI = 2.7 V
40
30
30
20
VI = 3.6 V
20
VI = 3.6 V
10
10
0
0.1
10
1
10
100
0
0.1
10
1000
1
IO – Output Current – mA
TPS60130
TPS60132
EFFICIENCY
vs
INPUT VOLTAGE
100
IO = 66 mA
90
IO = 216 mA
80
70
70
IO = 108 mA
Efficiency – %
Efficiency – %
IO = 66 mA
90
80
IO = 300 mA
50
40
60
40
30
20
20
10
10
3
3.4
3.8 4.2 4.6
VI – Input Voltage – V
5
5.4
IO = 108 mA
50
30
0
2.6
1000
Figure 7
EFFICIENCY
vs
INPUT VOLTAGE
60
100
IO – Output Current – mA
Figure 6
100
10
0
2.6
3
Figure 8
3.4
3.8 4.2 4.6
VI – Input Voltage – V
5
5.4
Figure 9
POST OFFICE BOX 655303
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11
TPS60130, TPS60131, TPS60132, TPS60133
REGULATED 5-V, 300 mA HIGH EFFICIENCY CHARGE PUMP
DC/DC CONVERTERS
SLVS258A – NOVEMBER 1999 – REVISED DECEMBER 1999
TYPICAL CHARACTERISTICS
TPS60132
OUTPUT VOLTAGE
vs
OUTPUT CURRENT
SUPPLY CURRENT
vs
INPUT VOLTAGE
80
5.10
IO = 0 mA
70
5.05
60
5.00
VO – Output Voltage – V
Supply Current – µ A
VI = 3.6 V
50
40
30
4.95
4.90
4.80
10
4.75
3.0
3.3
3.6
3.9
4.2
4.5
4.8
5.1
VI = 2.7 V
4.85
20
0
2.7
4.70
0.1
10
5.4
VI = 5.4 V
1
VI – Input Voltage – V
10
100
1000
IO – Output Current – mA
Figure 10
Figure 11
TPS60130
TPS60132
OUTPUT VOLTAGE
vs
INPUT VOLTAGE
OUTPUT VOLTAGE
vs
OUTPUT CURRENT
5.00
5.10
4.98
VI = 5.4 V
5.05
VO – Output Voltage – V
VO – Output Voltage – V
VI = 3.6 V
5.00
4.95
4.90
VI = 2.7 V
4.85
4.96
IO = 300 mA
4.90
4.88
4.75
4.86
1
10
100
1000
4.84
2.7
3.0
3.3
3.6
3.9
4.2
Figure 12
Figure 13
POST OFFICE BOX 655303
4.5
VI – Input Voltage – V
IO – Output Current – mA
12
IO = 1 mA
4.92
4.80
4.70
0.1
10
IO = 150 mA
4.94
• DALLAS, TEXAS 75265
4.8
5.1
5.4
TPS60130, TPS60131, TPS60132, TPS60133
REGULATED 5-V, 300 mA HIGH EFFICIENCY CHARGE PUMP
DC/DC CONVERTERS
SLVS258A – NOVEMBER 1999 – REVISED DECEMBER 1999
TYPICAL CHARACTERISTICS
TPS60132
OUTPUT VOLTAGE
vs
INPUT VOLTAGE
OUTPUT VOLTAGE RIPPLE
vs
TIME
5.00
5.000
IO 1 mA
4.98
4.990
4.97
4.985
4.96
IO 75 mA
IO 150 mA
4.95
4.94
4.93
4.980
4.975
4.970
4.965
4.92
4.960
4.91
4.955
4.90
2.7
VI = 3.6 V
IO = 1 mA
4.995
VO – Output Voltage – V
VO – Output Voltage – V
4.99
4.950
3.2
3.7
4.2
4.7
5.2
0
50 100 150 200 250 300 350 400 450 500
t – Time – µs
VI – Input Voltage – V
Figure 14
Figure 15
OUTPUT VOLTAGE RIPPLE
vs
TIME
OUTPUT VOLTAGE RIPPLE
vs
TIME
5.05
5.02
VI = 3.6 V
IO = 150 mA
5.03
VO – Output Voltage – V
VO – Output Voltage – V
5.00
VI = 3.6 V
IO = 300 mA
5.04
4.98
4.96
4.94
5.02
5.01
5.00
4.99
4.98
4.97
4.92
4.96
4.95
4.90
0
2
4
6
8
10
12
14
16
18
20
0
2
4
t – TIME – µs
6
8
10
12
14
16
18
20
t – TIME – µs
Figure 17
Figure 16
POST OFFICE BOX 655303
• DALLAS, TEXAS 75265
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TPS60130, TPS60131, TPS60132, TPS60133
REGULATED 5-V, 300 mA HIGH EFFICIENCY CHARGE PUMP
DC/DC CONVERTERS
SLVS258A – NOVEMBER 1999 – REVISED DECEMBER 1999
TYPICAL CHARACTERISTICS
OUTPUT VOLTAGE RIPPLE AMPLITUDE
vs
INPUT VOLTAGE
OSCILLATOR FREQUENCY
vs
INPUT VOLTAGE
330
120
100
80
60
IO = 75 mA
40
T = 85 °C
325
IO = 150 mA
f – Frequency – kHz
VO – Output Voltage Ripple Amplitude – mV
140
T = –40 °C
320
315
310
T = 25 °C
305
20
300
IO = 1 mA
0
2.7
3.0
3.3
3.6
3.9
4.2
4.5
4.8
5.1
295
2.7
5.4
3.0
3.3
VI – Input Voltage – V
3.6
Figure 18
VO – Output Voltage – V
4.50
4.98
4.96
300
0
6
8
10 12
t – Time – ms
14
16
18
20
V I – Input Voltage – V
VO – Output Voltage – V
I O – Output Current – mA
VI = 3.6 V
4
4.8
5.1
5.4
IO = 150 mA
5.02
5.00
4.98
4.96
3.9
3.4
0
2
Figure 20
14
4.5
LINE TRANSIENT RESPONSE
4.52
2
4.2
Figure 19
LOAD TRANSIENT RESPONSE
0
3.9
VI – Input Voltage – V
4
6
8
10 12
t – Time – ms
Figure 21
POST OFFICE BOX 655303
• DALLAS, TEXAS 75265
14
16
18
20
TPS60130, TPS60131, TPS60132, TPS60133
REGULATED 5-V, 300 mA HIGH EFFICIENCY CHARGE PUMP
DC/DC CONVERTERS
SLVS258A – NOVEMBER 1999 – REVISED DECEMBER 1999
TYPICAL CHARACTERISTICS
OUTPUT VOLTAGE
vs
TIME
(START-UP TIMING)
5.5
– Output Voltage and Enable – V
5.0
VI = 3.6 V
RLOAD = 16.7 Ω
4.5
ENABLE – V
4.0
3.5
3.0
2.5
2.0
1.5
VO – V
1.0
VO
0.5
0.0
–0.5
–0.2
0.0
0.2
0.4
0.6
0.8
1.0
1.2
t – Time – ms
Figure 22
APPLICATION INFORMATION
capacitor selection
The TPS6013x charge pumps require only four external capacitors as shown in the basic application circuit.
Their capacitance values and types are closely linked to the output current and output noise/ripple
requirements. For lowest noise and ripple, low ESR (< 0.1 Ω) capacitors should be used for input and output
capacitors.
The input capacitor improves system efficiency by reducing the input impedance. It also stabilizes the input
current of the power source. The input capacitor should be chosen according to the power supply used and the
distance from power source to the converter IC. The input capacitor also has an impact on the output voltage
ripple. The lower the ESR of the input capacitor Ci, the lower is the output ripple. Ci is recommended to be about
two to four times as large as C(xF).
The output capacitor Co can be selected from 5-times to 50-times larger than C(xF), depending on the ripple
tolerance. The larger Co, the lower will be the output voltage ripple. Ci and Co can be either ceramic or low-ESR
tantalum; aluminum capacitors are not recommended.
Generally, the flying capacitors C(xF) will be the smallest. Only ceramic capacitors are recommended, due to
their low ESR and because they retain their capacitance at the switching frequency. Because the device
regulates the output voltage using the pulse-skip technique, a larger flying capacitor will lead to a higher output
voltage ripple if the size of the output capacitor is not increased. Be aware that, depending on the material used
to manufacture them, ceramic capacitors might lose their capacitance over temperature. Ceramic capacitors
of type X7R or X5R material will keep their capacitance over temperature and voltage, whereas Z5U or Y5V-type
capacitors will decrease in capacitance. Table 2 lists recommended capacitor values.
POST OFFICE BOX 655303
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TPS60130, TPS60131, TPS60132, TPS60133
REGULATED 5-V, 300 mA HIGH EFFICIENCY CHARGE PUMP
DC/DC CONVERTERS
SLVS258A – NOVEMBER 1999 – REVISED DECEMBER 1999
capacitor selection (continued)
Table 2. Recommended Capicator Values
PART
TPS60130
TPS60131
VI
(V)
Ci
(µF)
CERAMIC
(X7R)
C(xF)
(µF))
(µ
CERAMIC
(X7R)
225
10
22
2.2
300
10
2.2
IO
(mA)
TANTALUM
3.6
TANTALUM
22
4.7
90
22
60
4.7
120
22 and 10 in
parallel
45
33
150
4.7
4.7
2.2
VPP(TYP)
(V)
CERAMIC
(X7R)
3.6
75
TPS60132
TPS60133
Co
(µF)
10
1
4.7
15
22
100
22
90
The TPS6013x devices are charge pumps that regulate the output voltage using pulse-skip regulation mode.
The output voltage ripple is therefore dependent on the values and the ESR of the input, output and flying
capacitors. The only possibility to reduce the output voltage ripple is to choose the appropriate capacitors. The
lowest output voltage ripple can be achieved using ceramic capacitors because of their low ESR and their
frequency characteristic.
Ceramic capacitors typically have an ESR that is more than 10 times lower than tantalum capacitors and they
retain their capacitance at frequencies more than 10 times higher than tantalum. Many different tantalum
capacitors act as an inductance for frequencies higher than 200 kHz. This behavior increases the output voltage
ripple. Therefore the best choice for a minimized ripple is the ceramic capacitor. For applications that do not
need a higher performance in output voltage ripple, tantalum capacitors with a low ESR are a possibility for input
and output capacitor, but a ceramic capacitor should be connected in parallel. Be aware that the ESR of tantalum
capacitors is indirectly proportional to the physical size of the capacitor.
Table 2 is a good starting point for choosing the capacitors. If the output voltage ripple is too high for the
application, it can be improved by selecting the appropriate capacitors. The first step is to increase the
capacitance at the output. If the ripple is still too high, the second step would be to increase the capacitance
at the input.
For the TPS60130 and TPS60131, the smallest board space can be achieved using Sprague’s 595D-series
tantalum capacitors for input and output. However, high capacitance ceramic capacitors will become
competitive in package size soon.
The smallest size for the lower-current devices TPS60132 and TPS60133 can be achieved using the suggested
ceramic capacitors.
16
POST OFFICE BOX 655303
• DALLAS, TEXAS 75265
TPS60130, TPS60131, TPS60132, TPS60133
REGULATED 5-V, 300 mA HIGH EFFICIENCY CHARGE PUMP
DC/DC CONVERTERS
SLVS258A – NOVEMBER 1999 – REVISED DECEMBER 1999
APPLICATION INFORMATION
capacitor selection (continued)
Tables 3 and 4 lists the manufacturers of recommended capacitors. In most applications surface-mount
tantalum capacitors will be the right choice. However, ceramic capacitors provide the lowest output voltage
ripple due to their typically lower ESR.
Table 3. Recommended Capacitors
MANUFACTURER
Taiyo Yuden
AVX
Sprague
Kemet
PART NUMBER
CAPACITANCE
CASE SIZE
TYPE
LMK212BJ105KG–T
1 µF
0805
Ceramic
LMK212BJ225MG–T
2.2 µF
0805
Ceramic
LMK316BJ475KL–T
4.7 µF
1206
Ceramic
LMK325BJ106MN–T
10 µF
1210
Ceramic
LMK432BJ226MM–T
22 µF
1812
Ceramic
0805ZC105KAT2A
1 µF
0805
Ceramic
1206ZC225KAT2A
2.2 µF
1206
Ceramic
TPSC475035R0600
4.7 µF
Case C
Tantalum
TPSC156025R0500
15 µF
Case C
Tantalum
TPSC336010R0375
33 µF
Case C
Tantalum
595D156X0016B2T
15 µF
Case B
Tantalum
595D226X0016B2T
22 µF
Case B
Tantalum
595D336X0016B2T
33 µF
Case B
Tantalum
595D336X0016C2T
33 µF
Case C
Tantalum
T494C156K010AS
15 µF
Case C
Tantalum
T494C226K010AS
22 µF
Case C
Tantalum
T494C336K010AS
33 µF
Case C
Tantalum
NOTE: Case code compatibility with EIA 535BAAC and CECC30801 molded chips.
Table 4. Recommended Capacitor Manufacturers
MANUFACTURER
CAPACITOR TYPE
INTERNET SITE
Taiyo Yuden
X7R/X5R ceramic
http://www.t–yuden.com/
AVX
X7R/X5R ceramic
TPS-series tantalum
http://www.avxcorp.com/
Sprague
595D-series tantalum
593D-series tantalum
http://www.vishay.com/
Kemet
T494-series tantalum
http://www.kemet.com/
power dissipation
The power dissipated in the TPS6013x depends on output current and the mode of operation (1.5x or doubler
voltage conversion mode). It is described by the following equation:
1
PDISS = ǒh –1Ǔ VO × IO (Efficiency η mainly depends on VI and also on IO. See efficiency graphs.)
PDISS must be less than that allowed by the package rating. See the absolute maximum ratings for 20-pin PWP
package power-dissipation limits and deratings.
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TPS60130, TPS60131, TPS60132, TPS60133
REGULATED 5-V, 300 mA HIGH EFFICIENCY CHARGE PUMP
DC/DC CONVERTERS
SLVS258A – NOVEMBER 1999 – REVISED DECEMBER 1999
APPLICATION INFORMATION
board layout
Careful board layout is necessary due to the high transient currents and switching frequency of the converter.
All capacitors should be soldered in close proximity to the IC. Connect ground and power ground pins through
a short, low-impedance trace. A PCB layout proposal for a two-layer board is given in Figure 23. The bottom
layer of the board carries only ground potential for best performance. The layout also provides improved thermal
performance as the exposed lead frame is soldered to the PCB.
An evaluation module for the TPS60130 is available and can be ordered under product code
TPS60130EVM-143. The EVM uses the layout shown in Figure 23.
Figure 23. Recommended PCB Layout for
TPS6013X
Figure 24. Component Placement for
TPS6013X EVM
Table 5. Component Identification
IC1
TPS6013x
C1, C2
Flying capacitors
C3, C6
Input capacitors
C4, C5
Onput capacitors
C7
Stabilization capacitor for LBI
R1, R2
Resistive divider for LBI
R3
Pullup resistor for LBO
The best performance of the converter is achieved with the additional bypass capacitors C5 and C6 at input and
output. Capacitor C7 should be included if the large line transients are expected. The capacitors are not
required. They can be omitted in most applications.
18
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TPS60130, TPS60131, TPS60132, TPS60133
REGULATED 5-V, 300 mA HIGH EFFICIENCY CHARGE PUMP
DC/DC CONVERTERS
SLVS258A – NOVEMBER 1999 – REVISED DECEMBER 1999
APPLICATION INFORMATION
application proposals
paralleling of two TPS6013x to deliver 600 mA total output current
Two TPS60130x devices can be connected in parallel to yield higher load currents. The circuit of Figure 25 can
deliver up to 600 mA at an output voltage of 5 V. The devices can share the output capacitors, but each one
requires its own transfer capacitors and input capacitor. If both a TPS60130 and a TPS60131 are used, it is
possible to monitor the battery voltage with the TPS60130 using the low-battery comparator function and to
supervise the output voltage with the TPS60131 using the power-good comparator. Make the layout of the
charge pumps as similar as possible, and position the output capacitor the same distance from both devices.
Input
2.7 V to 5.4 V
TPS60130
IN
Ci
15 µF
IN
R1
562 kΩ
LBI
R2
453 kΩ
C1–
Off/On
OUT
LBO
C1+
C1
2.2 µF
OUT
FB
R3
1 MΩ
Ci
15 µF
IN
OUT
IN
OUT
NC
Low Battery
Warning
C2+
C2–
Output
5 V, 600 mA
TPS60131
C2
2.2 µF
FB
R4
1 MΩ
Power-Good
Signal
PG
C1
2.2 µF
ENABLE
PGND GND
C1+
C2+
C1–
C2–
Co
47 µF
C2
2.2 µF
ENABLE
PGND GND
Figure 25. Paralleling of Two TPS6013x Charge Pumps
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TPS60130, TPS60131, TPS60132, TPS60133
REGULATED 5-V, 300 mA HIGH EFFICIENCY CHARGE PUMP
DC/DC CONVERTERS
SLVS258A – NOVEMBER 1999 – REVISED DECEMBER 1999
APPLICATION INFORMATION
TPS6013x operated with ultra-low quiescent current
Because the output of the TPS6013x is isolated from the input when the devices are disabled, and because the
internal resistive divider is disconnected in shutdown, an ultra-low quiescent current mode can be implemented.
In this mode, the output voltage is sustained because the converter is periodically enabled to refresh the output
capacitor. The necessary external control signal that is applied to the ENABLE-pin is generated from a
microcontroller. For a necessary supply current for the system of 1 mA and a minimum supply voltage of 4.5
V with a 33-µF output capacitor, the refresh has to be done after 9 ms. Longer refresh periods can be achieved
with a larger output capacitor.
Input
2.7 V to 5.4 V
Ci
15 µF
R1
IN
OUT
IN
OUT
LBI
R2
C1
2.2 µF
ON
OFF
Output
5 V, 150 mA
TPS60132
C2
33 µF
FB
R3
1 MΩ
LBO
C1+
C1–
C3
1 µF
I
R4
1 MΩ
C2+
µC
O
C2
2.2 µF
C2–
ENABLE
PGND GND
Figure 26. TPS60132 in Ultra-Low Quiescent Current Mode
regulated discharge of the output capacitors after disabling of the TPS6013x
During shutdown of the charge pump TPS6013x the output is isolated from the input. Therefore the discharging
of the output capacitor depends on the load and on the leakage current of the capacitor. In certain applications
it is necessary to completely remove the supply voltage from the load in shutdown mode. That means the output
capacitor of the charge pump has to be actively discharged when the charge pump is disabled. Figure 10 shows
one solution to this problem.
IN
IN
OUT
OUT
TPS601xx
ENABLE
+
CO
ENABLE
GND
VCC
SN74AHC1G04
A
BSS138
Y
GND
GND
Figure 27. Block Diagram of the Regulated Discharge of the Output Capacitor
20
POST OFFICE BOX 655303
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TPS60130, TPS60131, TPS60132, TPS60133
REGULATED 5-V, 300 mA HIGH EFFICIENCY CHARGE PUMP
DC/DC CONVERTERS
SLVS258A – NOVEMBER 1999 – REVISED DECEMBER 1999
APPLICATION INFORMATION
related information
application reports
For more application information see:
D
D
D
PowerPAD Application Report, Literature Number SLMA002
TPS6010x/TPS6011x Charge Pump Application Report, Literature Number SLVA070
Powering the TMS320C5420 Using the TPS60100, TPS76918, and the TPS3305-18, Literature Number
SLVA082.
device family products
Other devices in this family are:
PART NUMBER
DATASHEET
LITERATURE
CODE
TPS60100
SLVS213B
Regulated 3.3-V, 200-mA low-noise charge pump dc-dc converter
TPS60101
SLVS214A
Regulated 3.3-V, 100-mA low-noise charge pump dc-dc converter
TPS60110
SLVS215A
Regulated 5-V, 300-mA low-noise charge pump dc-dc converter
Regulated 5-V, 150-mA low-noise charge pump dc-dc converter
DESCRIPTION
TPS60111
SLVS216A
TPS60120
SLVS257
Regulated 3.3-V, 200-mA high efficiency charge pump dc-dc converter with low-battery comparator
TPS60121
SLVS257
Regulated 3.3-V, 200-mA high efficiency charge pump dc-dc converter with power-good comparator
TPS60122
SLVS257
Regulated 3.3-V, 100-mA high efficiency charge pump dc-dc converter with low-battery comparator
TPS60123
SLVS257
Regulated 3.3-V, 100-mA high efficiency charge pump dc-dc converter with power-good comparator
POST OFFICE BOX 655303
• DALLAS, TEXAS 75265
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TPS60130, TPS60131, TPS60132, TPS60133
REGULATED 5-V, 300 mA HIGH EFFICIENCY CHARGE PUMP
DC/DC CONVERTERS
SLVS258A – NOVEMBER 1999 – REVISED DECEMBER 1999
MECHANICAL DATA
PWP (R-PDSO-G**)
PowerPAD PLASTIC SMALL-OUTLINE
20 PINS SHOWN
0,30
0,19
0,65
20
0,10 M
11
Thermal Pad
(See Note D)
4,50
4,30
0,15 NOM
6,60
6,20
Gage Plane
1
10
0,25
A
0°– 8°
0,75
0,50
Seating Plane
0,15
0,05
1,20 MAX
PINS **
0,10
14
16
20
24
28
A MAX
5,10
5,10
6,60
7,90
9,80
A MIN
4,90
4,90
6,40
7,70
9,60
DIM
4073225/F 10/98
NOTES: A.
B.
C.
D.
All linear dimensions are in millimeters.
This drawing is subject to change without notice.
Body dimensions do not include mold flash or protrusions.
The package thermal performance may be enhanced by bonding the thermal pad to an external thermal plane.
This pad is electrically and thermally connected to the backside of the die and possibly selected leads.
E. Falls within JEDEC MO-153
PowerPAD is a trademark of Texas Instruments Incorporated.
22
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