CHERRY CS8321YDP3

CS8321
CS8321
Micropower 5V, 150mA Low Dropout
Linear Regulator
Features
Description
The CS8321 is a precision 5V
micropower voltage regulator with
very low quiescent current (140µA
typ at 1mA load). The 5V output is
accurate within ±2% and supplies
150mA of load current with a typical dropout voltage of only 300mV.
This combination of low quiescent
current and outstanding regulator
performance makes the CS8321
ideal for any battery operated
equipment.
The regulator is protected against
reverse battery and short circuit
conditions. The device can withstand 45V load dump transients
making it suitable for use in automotive environments.
Absolute Maximum Ratings
Transient Input Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .-15V, 45V
Output Current . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .Internally Limited
ESD Susceptibility (Human Body Model) . . . . . . . . . . . . . . . . . . . . . . . . . .2kV
Junction Temperature . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .-40¡C to 150¡C
Storage Temperature . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .-65C to 150¡C
Lead Temperature Soldering
Wave Solder (through hole styles only) . . . . . . . .10 sec. max, 260¡C peak
Reflow (SMD styles only) . . . . . . . .60 sec. max above 183¡C, 230¡C peak
■ 5V ±2% Output
■ Low 140µA (typ)
Quiescent Current
■ 150mA Output Current
Capability
■ Fault Protection
-15V Reverse Voltage
Output Current Limit
■ Low Reverse Current
(Output to Input)
Package Options
3L TO-220
Block Diagram
VOUT
VIN
1. VIN
QP
Current Source
(Circuit Bias)
2. Gnd
R
3. VOUT
QN
Current Limit
Sense
1
VOUTSense*
+
3L D2PAK
- Error
Amplifier
1. VIN
R1
2. Gnd
3. VOUT
1
Bandgap
Reference
R2
Gnd
*Note: Lead shorted to VOUT in 3 pin applications
Other Packages: 16L SO, 16L PDIP,
8L SO, 8L PDIP, (consult factory)
Cherry Semiconductor Corporation
2000 South County Trail, East Greenwich, RI 02818
Tel: (401)885-3600 Fax: (401)885-5786
Email: info@cherry-semi.com
Web Site: www.cherry-semi.com
Rev. 11/25/96
1
A
¨
Company
CS8321
Electrical Characteristics: 6V < VIN < 26V, IOUT=1mA, -40¡C ² TA ² 125¡C, -40¡C ² TJ ² 150¡C unless otherwise specified.
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX
UNIT
4.90
5.00
5.10
V
0.3
0.5
0.6
V
V
200
µA
■ Output Stage
Output Voltage, VOUT
9V < VIN < 16V,
100µA ² IOUT ² 150mA
Dropout Voltage (VIN-VOUT)
IOUT = 150mA, -40¡C ² TA ² 85¡C
IOUT = 150mA, TA = 125¡C
Quiescent Current, (IQ)
IOUT = 1mA @ VIN = 13V
IOUT < 50mA @ VIN = 13V
IOUT < 150mA @ VIN = 13V
4
15
6
25
mA
mA
Load Regulation
VIN = 14V, 100µA < IOUT < 150mA
5
50
mV
Line Regulation
6V < V < 26V, IOUT = 1mA
5
50
mV
Ripple Rejection
7 Ð VIN Ð 17V, IOUT = 150mA,
f = 120Hz
Current Limit
Short Circuit Output Current
VOUT = 0V
Reverse Current
VOUT = 5V, VIN = 0V
60
75
dB
175
250
mA
60
200
mA
140
200
µA
Package Lead Description
PACKAGE LEAD #
LEAD SYMBOL
FUNCTION
3L D2PAK
3L TO-220
1
1
VIN
Input Voltage
2
2
Gnd
Ground. All Gnd leads must be connected to Ground.
3
3
VOUT
5V, ±2%, 150mA Output.
Circuit Description and Application Notes
Antisaturation Protection
An antisaturation control circuit has also been added to
prevent the pass transistor from going into deep saturation, which would cause excessive power dissipation due
to large bias currents lost to the substrate via a parasitic
PNP transistor, as shown in Figure 1.
Voltage Reference and Output Circuitry
The CS8321 is a series pass voltage regulator. It consists of
an error amplifier, bandgap voltage reference, PNP pass
transistor with antisaturation control, and current limit.
As the voltage at the input, VIN, is increased, QN is forward biased via R. QN provides base drive for QP. As QP
becomes forward biased, the output voltage, VOUT, begins
to rise as QPÕs output current charges the output capacitor.
Once VOUT rises to a certain level, the error amplifier
becomes biased and provides the appropriate amount of
base current to QP. The error amplifier monitors the scaled
output voltage via an internal voltage divider, R1 and R2,
and compares it to the bandgap voltage reference. The
error amplifierÕs output is a current which is equal to the
error amplifierÕs differential input voltage times its
transconductance. Therefore, the error amplifier varies the
base drive current to QN, which provides bias to QP, based
on the difference between the reference voltage and the
scaled output voltage, VOUT.
VIN
QP
QParasitic
VOUT
Substrate
Figure 1. The parasitic PNP transistor which is part of the pass transistor (QP) structure.
2
ity. The aluminum electrolytic capacitor is the least expensive solution, but, if the circuit operates at low temperatures (-25¡C to -40¡C), both the value and ESR of the
capacitor will vary considerably. The capacitor manufacturers data sheet usually provides this information.
The value for the output capacitor COUT shown in Figure 3
should work for most applications, however it is not necessarily the best solution.
To determine an acceptable value for COUT for a particular
application, start with a tantalum capacitor of the recommended value and work towards a less expensive alternative part.
Step 1: Place the completed circuit with a tantalum capacitor of the recommended value in an environmental chamber at the lowest specified operating temperature and
monitor the outputs with an oscilloscope. A decade box
connected in series with the capacitor will simulate the
higher ESR of an aluminum capacitor. Leave the decade
box outside the chamber, the small resistance added by
the longer leads is negligible.
Step 2: With the input voltage at its maximum value,
increase the load current slowly from zero to full load
while observing the output for any oscillations. If no oscillations are observed, the capacitor is large enough to
ensure a stable design under steady state conditions.
Step 3: Increase the ESR of the capacitor from zero using
the decade box and vary the load current until oscillations
appear. Record the values of load current and ESR that
cause the greatest oscillation. This represents the worst
case load conditions for the regulator at low temperature.
Step 4: Maintain the worst case load conditions set in step
3 and vary the input voltage until the oscillations increase.
This point represents the worst case input voltage conditions.
Step 5: If the capacitor is adequate, repeat steps 3 and 4
with the next smaller valued capacitor. A smaller capacitor will usually cost less and occupy less board space. If
the output oscillates within the range of expected operating conditions, repeat steps 3 and 4 with the next larger
standard capacitor value.
Step 6: Test the load transient response by switching in
various loads at several frequencies to simulate its real
working environment. Vary the ESR to reduce ringing.
Step 7: Remove the unit from the environmental chamber
and heat the IC with a heat gun. Vary the load current as
instructed in step 5 to test for any oscillations.
Once the minimum capacitor value with the maximum
ESR is found, a safety factor should be added to allow for
the tolerance of the capacitor and any variations in regulator performance. Most good quality aluminum electrolytic
capacitors have a tolerance of ± 20% so the minimum value
found should be increased by at least 50% to allow for this
tolerance plus the variation which will occur at low temperatures. The ESR of the capacitor should be less than 50%
of the maximum allowable ESR found in step 3 above.
Current Limit Limit
The output stage is protected against short circuit conditions. As shown in Figure 2, the output current will fold
back when the faulted load is continually increased. This
technique has been incorporated to limit the total power
dissipation across the device during a short circuit condition, since the device does not contain overtemperature
shutdown.
0.34257
0.30831
0.27405
Load Current
0.23980
0.20554
0.17128
0.13703
0.10277
0.06851
* Curve will vary with temperature and process variation.
0.03426
0.00000
0.00
0.51
1.02
1.52
2.03
2.54
3.05
3.56
4.06
4.57
5.08
Output Voltage
Figure 2. Typical current limit and fold back waveform.
Stability Considerations
The output or compensation capacitor helps determine
three main characteristics of a linear regulator: start-up
delay, load transient response and loop stability.
VIN
VOUT
CIN*
0.1mF
COUT**
CS8321
10mF
VOUTSense***
* CIN required if regulator is located far from the power supply filter.
** COUT required for stability. Capacitor must operate at minimum
temperature expected.
*** Pin internally shorted to VOUT in 3 pin applications.
Figure 3: Test and application circuit showing output compensation.
The capacitor value and type should be based on cost,
availability, size and temperature constraints. A tantalum
or aluminum electrolytic capacitor is best, since a film or
ceramic capacitor with almost zero ESR can cause instabil-
3
CS8321
Circuit Description and Application Notes: continued
CS8321
Circuit Description and Application Notes: continued
Heatsinks
Calculating Power Dissipation
in a Single Output Linear Regulator
A heatsink effectively increases the surface area of the
package to improve the flow of heat away from the IC and
into the surrounding air.
The maximum power dissipation for a single output regulator (Figure 3) is:
PD(max)=(VIN(max)ÐVOUT(min))IOUT(max)+VIN(max)IQ
Each material in the heat flow path between the IC and the
outside environment will have a thermal resistance. Like
series electrical resistances, these resistances are summed
to determine the value of RQJA:
(1)
where:
VIN(max) is the maximum input voltage,
VOUT(min) is the minimum output voltage,
IOUT(max) is the maximum output current for the application, and
IQ is the quiescent current the regulator consumes at
IOUT(max).
RQJA = RQJC + RQCS + RQSA
where:
RQJC = the junctionÐtoÐcase thermal resistance,
RQCS = the caseÐtoÐheatsink thermal resistance, and
RQSA = the heatsinkÐtoÐambient thermal resistance.
RQJC appears in the package section of the data sheet. Like
RQJA, it too is a function of package type. RQCS and RQSA
are functions of the package type, heatsink and the interface between them. These values appear in heatsink data
sheets of heatsink manufacturers.
Once the value of PD(max) is known, the maximum permissible value of RQJA can be calculated:
RQJA =
150¡C - TA
PD
(2)
The value of RQJA can then be compared with those in
the package section of the data sheet. Those packages
with RQJA's less than the calculated value in equation 2
will keep the die temperature below 150¡C.
In some cases, none of the packages will be sufficient to
dissipate the heat generated by the IC, and an external
heatsink will be required.
IIN
IOUT
VIN
(3)
VOUT
CS8321
IQ
Figure 4: Single output regulator with key performance parameters
labeled.
4
CS8321
Package Specification
PACKAGE DIMENSIONS IN mm(INCHES)
PACKAGE THERMAL DATA
3L
TO-220
3.5
50
Thermal Data
RQJC
typ
RQJA
typ
3L
D2PAK
1.0*
10 - 50**
ûC/W
ûC/W
*Depending on die area
**Depending on thermal properties of substrate. RQJA = RQJC + RQCA
3 Lead TO-220 (T) Straight
4.83 (.190)
4.06 (.160)
10.54 (.415)
9.78 (.385)
6.55 (.258)
5.94 (.234)
1.40 (.055)
1.14 (.045)
3.96 (.156)
3.71 (.146)
2.87 (.113)
2.62 (.103)
14.99 (.590)
14.22 (.560)
1.52 (.060)
1.14 (.045)
14.22 (.560)
13.72 (.540)
6.17 (.243) REF
1.40 (.055)
1.14 (.045)
1.02 (.040)
0.63 (.025)
0.56 (.022)
0.38 (.014)
2.79 (.110)
2.29 (.090)
5.33 (.210)
4.83 (.190)
2.92 (.115)
2.29 (.090)
5
CS8321
Package Specification: continued
3 Lead D2PAK (DP)
10.31 (.406)
10.05 (.396)
1.40 (.055)
1.14 (.045)
1.68 (.066)
1.40 (.055)
8.53 (.336)
8.28 (.326)
15.75 (.620)
14.73 (.580)
2.74(.108)
2.49(.098)
1.40 (.055)
1.14 (.045)
2.79 (.110)
2.29 (.090)
0.91 (.036)
0.66 (.026)
2.54 (.100) REF
.254 (.010) REF
0.10 (.004)
0.00 (.000)
4.57 (.180)
4.31 (.170)
Ordering Information
Part Number
CS8321YT3
CS8321YDP3
CS8321YDPR3
Rev. 11/25/96
Description
3L TO-220 Straight
3L D2PAK
3L D2PAK (tape & reel)
Cherry Semiconductor Corporation reserves the right to
make changes to the specifications without notice. Please
contact Cherry Semiconductor Corporation for the latest
available information.
6
© 1999 Cherry Semiconductor Corporation