ELANTEC EL2360C

Triple 130 MHz Current Feedback Amplifier
Features
General Description
# Triple amplifier topology
# 130 MHz b 3 dB bandwidth
(AV e a 2)
# 180 MHz b 3 dB bandwidth
(AV e a 1)
# Wide supply range, g 2V to
g 15V
# 80 mA output current (peak)
# Low cost
# 1500 V/ms slew rate
# Input common mode range to
within 1.5V of supplies
# 35 ns settling time to 0.1%
# Available in single (EL2160C),
dual (EL2260C), and quad
(EL2460C) form
The EL2360C is a triple current-feedback operational amplifier
which achieves a b 3 dB bandwidth of 130 MHz at a gain of
a 2. Built using the Elantec proprietary monolithic complementary bipolar process, these amplifiers use current mode
feedback to achieve more bandwidth at a given gain than a
conventional voltage feedback amplifier.
Applications
#
#
#
#
#
#
RGB amplifiers
Video amplifiers
Cable driver
Test equipment amplifiers
Current to voltage converters
Video broadcast equipment
EL2360C
EL2360C
The EL2360C is designed to drive a double terminated 75X coax
cable to video levels. It’s fast slew rate of 1500 V/ms, combined
with the triple amplifier topology, makes its ideal for RGB video applications.
This amplifier can operate on any supply voltage from 4V
( g 2V) to 33V ( g 16.5V), yet consume only 8 mA per amplifier
at any supply voltage. The EL2360C is available in 16-pin
PDIP and SOIC packages.
For Single, Dual, or Quad applications, consider the EL2160C,
EL2260C, or EL2460C all in industry standard pin outs. For
Single applications with a power down feature, consider the
EL2166C.
Connection Diagram
EL2360C SOIC, P-DIP
Packages
Ordering Information
Part No.
Temp. Range
Package
Outline Ý
EL2360CN b 40§ C to a 85§ C 16 b Pin PDIP MDP0031
EL2360CS b 40§ C to a 85§ C 16 b Pin SOIC MDP0027
Note: All information contained in this data sheet has been carefully checked and is believed to be accurate as of the date of publication; however, this data sheet cannot be a ‘‘controlled document’’. Current revisions, if any, to these
specifications are maintained at the factory and are available upon your request. We recommend checking the revision level before finalization of your design documentation.
© 1996 Elantec, Inc.
June 1996 Rev A
2360 – 1
Top View
EL2360C
Triple 130 MHz Current Feedback Amplifier
Absolute Maximum Ratings (TA e 25§ C)
Voltage between VS a and VSb
Common-Mode Input Voltage
Differential Input Voltage
Current into a IN or bIN
Internal Power Dissipation
a 33V
VSb to VS a
g 6V
g 10 mA
See Curves
g 50 mA
Output Current (continuous)
Operating Ambient Temperature Range
Operating Junction Temperature
Storage Temperature Range
b 40§ C to a 85§ C
150§ C
b 65§ C to a 150§ C
Important Note:
All parameters having Min/Max specifications are guaranteed. The Test Level column indicates the specific device testing actually
performed during production and Quality inspection. Elantec performs most electrical tests using modern high-speed automatic test
equipment, specifically the LTX77 Series system. Unless otherwise noted, all tests are pulsed tests, therefore TJ e TC e TA.
Test Level
I
II
III
IV
V
Test Procedure
100% production tested and QA sample tested per QA test plan QCX0002.
100% production tested at TA e 25§ C and QA sample tested at TA e 25§ C ,
TMAX and TMIN per QA test plan QCX0002.
QA sample tested per QA test plan QCX0002.
Parameter is guaranteed (but not tested) by Design and Characterization Data.
Parameter is typical value at TA e 25§ C for information purposes only.
Parameter
Typ
Max
Test
Level
Units
VS e g 5V, g 15V
2
10
I
mV
Description
Conditions
Min
VOS
Input Offset Voltage
TCVOS
Average Input Offset Voltage Drift, (Note 1)
V
mV/§ C
a IIN
a Input Current
VS e g 5V, g 15V
0.5
3
I
mA
b IIN
b Input Current
VS e g 5V, g 15V
5
25
I
mA
CMRR
Common Mode Rejection Ratio, (Note 2)
VS e g 5V, g 15V
I
dB
b ICMR
b Input Current Common
VS e g 5V, g 15V
I
mA/V
I
dB
I
mA/V
10
50
0.2
Mode Rejection, (Note 2)
PSRR
Power Supply Rejection Ratio, (Note 3)
b IPSR
b Input Current Power
75
Transimpedance, (Note 4)
a RIN
a Input Resistance
a CIN
a Input Capacitance
CMIR
Note
Note
Note
Note
Common Mode Input Range
5
95
0.2
Supply Rejection, (Note 3)
ROL
55
5
VS e g 15V, RL e 400X
500
2000
I
kX
VS e g 15V, RL e 150X
500
1800
I
kX
MX
3
I
PDIP package
1.5
1.5
V
pF
SOIC package
1
V
pF
VS e g 15V
g 13.5
V
V
VS e g 5V
g 3.5
V
V
1: Measured from TMIN to TMAX.
2: VCM e g 10V for VS e g 15V, VCM e g 3V for VS e g 5V.
3: The supplies are moved from g 2.5V to g 15V.
4: VOUT e g 7V for VS e g 15V, VOUT e g 2V for VS e g 5V.
2
TD is 3.4in
DC Electrical Characteristics VS e g 15V, RL e 150X, TA e 25§ C unless otherwise specified
EL2360C
Triple 130 MHz Current Feedback Amplifier
Parameter
VO
Description
Output Voltage Swing
Test
Level
Units
g 13.5
I
V
g 12
V
V
Conditions
Min
Typ
VS e g 15V, RL e 400X
g 12
VS e g 15V, RL e 150X
VS e g 5V, RL e 150X
Max
g 3.0
g 3.7
I
V
60
100
150
I
mA
VS e g 15V
8.0
11.3
I
mA
VS e g 5V
5.7
8.8
I
mA
ISC
Output Short Circuit Current, (Note 5)
VS e g 5V, g 15V
IS
Supply Current (per amplifier)
TD is 1.5in
DC Electrical Characteristics VS e g 15V, RL e 150X, TA e 25§ C unless otherwise specified Ð Contd.
Note 5: A heat sink is required to keep junction temperature below absolute maximum when an output is shorted.
AC Electrical Characteristics (Note 8), VS e g 15V, AV e a 2, RF e RG e 560X, RL e 150X, TA e 25§ C
Parameter
BW
SR
Description
b 3 dB Bandwidth
Slew Rate (Note 6)
Conditions
VS e g 15V, AV e a 2
Rise Time, Fall Time
Typ
130
Max
Test
Level
Units
V
MHz
VS e g 15V, AV e a 1
180
V
MHz
VS e g 5V, AV e a 2
100
V
MHz
VS e g 5V, AV e a 1
110
V
MHz
1500
IV
V/ms
1500
V
V/ms
VOUT e g 500 mV
2.7
V
ns
RL e 400X
1000
RF e 1 kX, RG e 110X, RL e 400X
tr, tf
Min
tPD
Propagation Delay
VOUT e g 500 mV
3.2
V
ns
OS
Overshoot
VOUT e g 500 mV
0
V
%
tS
0.1% Settling Time
VOUT e g 2.5V, AV e b1
35
V
ns
dG
Differential Gain (Note 7)
RL e 150X
0.025
V
%
RL e 500X
0.006
V
%
RL e 150X
0.1
V
§
RL e 500X
0.005
V
§
dP
Differential Phase (Note 7)
Note 6: Slew Rate is with VOUT from a 10V to b10V and measured at a 5V and b5V.
Note 7: DC offset from b0.714V to a 0.714V, AC amplitude 286 mVPbP, f e 3.58 MHz.
Note 8: All AC tests are performed on a ‘‘warmed up’’ part, except Slew Rate, which is pulse tested.
3
TD is 3.0in
unless otherwise specified.
EL2360C
Triple 130 MHz Current Feedback Amplifier
Typical Performance Curves
Non-Inverting Frequency
Response (Gain)
Inverting Frequency
Response (Gain)
3 dB Bandwidth vs Supply
Voltage for AV e b 1
Non-Inverting Frequency
Response (Phase)
Inverting Frequency
Response (Phase)
Peaking vs Supply Voltage
for AV e b 1
Frequency Response
for Various RL
Frequency Response for
Various RF and RG
3 dB Bandwidth vs
Temperature for AV e b 1
2360 – 2
4
EL2360C
Triple 130 MHz Current Feedback Amplifier
Typical Performance Curves Ð Contd.
3 dB Bandwidth vs Supply
Voltage for AV e a 1
Peaking vs Supply Voltage
for AV e a 1
3 dB Bandwidth vs Temperature
for AV e a 1
3 dB Bandwidth vs Supply
Voltage for AV e a 2
Peaking vs Supply Voltage
for AV e a 2
3 dB Bandwidth vs Temperature
for AV e a 2
3 dB Bandwidth vs Supply
Voltage for AV e a 10
Peaking vs Supply Voltage
for AV e a 10
3 dB Bandwidth vs Temperature
for AV e a 10
2360 – 3
5
EL2360C
Triple 130 MHz Current Feedback Amplifier
Typical Performance Curves Ð Contd.
Frequency Response
for Various CL
Frequency Response
for Various CIN b
Channel to Channel
Isolation vs Frequency
PSRR and CMRR
vs Frequency
2nd and 3rd Harmonic
Distortion vs Frequency
Transimpedance (ROL)
vs Frequency
Voltage and Current Noise
vs Frequency
Closed-Loop Output
Impedance vs Frequency
Transimpedance (ROL)
vs Die Temperature
2360 – 4
6
EL2360C
Triple 130 MHz Current Feedback Amplifier
Typical Performance Curves Ð Contd.
Offset Voltage
vs Die Temperature
(4 Samples)
Supply Current
vs Die Temperature
(Per Amplifier)
Supply Current
vs Supply Voltage
(Per Amplifier)
a Input Resistance
vs Die Temperature
Input Current
vs Die Temperature
a Input Bias Current
vs Input Voltage
Output Voltage Swing
vs Die Temperature
Short Circuit Current
vs Die Temperature
PSRR & CMRR
vs Die Temperature
2360 – 5
7
EL2360C
Triple 130 MHz Current Feedback Amplifier
Typical Performance Curves Ð Contd.
Differential Gain
vs DC Input Voltage,
RL e 150
Differential Phase
vs DC Input Voltage,
RL e 150
Small Signal
Pulse Response
Differential Gain
vs DC Input Voltage,
RL e 500
Differential Phase
vs DC Input Voltage,
RL e 500
Large Signal
Pulse Response
Slew Rate
vs Supply Voltage
Slew Rate
vs Temperature
2360 – 6
8
EL2360C
Triple 130 MHz Current Feedback Amplifier
Typical Performance Curves Ð Contd.
Settling Time vs
Settling Accuracy
Long Term Settling Error
2360 – 16
2360 – 15
16-Lead Plastic SO
Maximum Power Dissipation
vs Ambient Temperature
16-Lead Plastic DIP
Maximum Power Dissipation
vs Ambient Temperature
2360 – 7
2360 – 8
9
EL2360C
Triple 130 MHz Current Feedback Amplifier
Differential Gain And Phase Test Circuit
2360 – 9
Simplified Schematic (One Amplifier)
2360 – 10
10
EL2360C
Triple 130 MHz Current Feedback Amplifier
Applications Information
Product Description
Capacitance at the Inverting Input
The EL2360C is a triple current feedback amplifier that offers wide bandwidth and good video
specifications at moderately low supply currents.
It is built using Elantec’s proprietary complimentary bipolar process and is offered in both a
16 pin PDIP and SOIC packages. Due to the current feedback architecture, the EL2360C closed b loop b 3 dB bandwidth is dependent on the
value of the feedback resistor. First the desired
bandwidth is selected by choosing the feedback
resistor, RF, and then the gain is set by picking a
gain resistor, RG. The curves at the beginning of
the Typical Performance Curves section show the
effect of varying both RF and RG. The b 3 dB
bandwidth is somewhat dependent on the power
supply voltage. As the supply voltage is decreased, internal junction capacitances increase,
causing a reduction in the closed loop bandwidth.
To compensate for this, smaller values of feedback resistor can be used at lower supply voltages.
Any manufacturer’s high-speed voltage- or current-feedback amplifier can be affected by stray
capacitance at the inverting input. The characteristic curve of gain vs. frequency with variations
in CIN b emphasizes this effect. The curve illustrates how the bandwidth can be extended to beyond 200 MHz with some additional peaking
with an additional 2pF of capacitance at the
VIN b pin. For inverting gains, this parasitic capacitance has little effect because the inverting
input is a virtual ground, but for non-inverting
gains, this capacitance (in conjunction with the
feedback and gain resistors) creates a pole in the
feedback path of the amplifier. This pole, if low
enough in frequency, has the same destabilizing
effect as a zero in the forward open-loop response. The use of large value feedback and gain
resistors further exacerbates the problem by further lowering the pole frequency.
Feedback Resistor Values
The EL2360C has been designed and specified at
a gain of a 2 with RF e 560X. This value of
feedback resistor yields relatively flat frequency
response with little to no peaking out to 130
MHz. Since the EL2360C is a current-feedback
amplifier, it is also possible to change the value
of RF to get more bandwidth. As seen in the
curve of Frequency Response For Various RF
and RG, bandwidth and peaking can be easily
modified by varying the value of the feedback
resistor. For example, by reducing RF to 430X,
bandwidth can be extended to 170 MHz with under 1 dB of peaking. Further reduction of RF to
360X increases the bandwidth to 195 MHz with
about 2.5 dB of peaking.
Power Supply Bypassing and Printed
Circuit Board Layout
As with any high-frequency device, good printed
circuit board layout is necessary for optimum
performance. Ground plane construction is highly recommended. Lead lengths should be as short
as possible, preferably below (/4’’. The power supply pins must be well bypassed to reduce the risk
of oscillation. The combination of a 1.0 mF tantalum capacitor in parallel with a 0.01 mF ceramic
capacitor has been shown to work well when
placed at each supply pin.
For good AC performance, parasitic capacitance
should be kept to a minimum especially at the
inverting input (see the Capacitance at the Inverting Input section). This implies keeping the
ground plane away from this pin. Carbon or Metal-Film resistors are acceptable with the MetalFilm resistors giving slightly less peaking and
bandwidth because of their additional series inductance. Use of sockets, particularly for the SO
package should be avoided if possible. Sockets
add parasitic inductance and capacitance which
will result in some additional peaking and overshoot.
Bandwidth vs Temperature
Whereas many amplifier’s supply current and
consequently b 3 dB bandwidth drop off at high
temperature, the EL2360C was designed to have
little supply current variation with temperature.
An immediate benefit from this is that the b 3
dB bandwidth does not drop off drastically with
temperature. With VS e g 15V and AV e a 2,
the bandwidth varies only from 150 MHz to 110
MHz over the entire die junction temperature
range of b 50§ C k T k 150§ C.
11
EL2360C
Triple 130 MHz Current Feedback Amplifier
Applications Information Ð Contd.
caused by a power dissipation differential (before
and after the voltage step). For AV e b 1, due to
the inverting mode configuration, this tail does
not appear since the input stage does not experience the large voltage change as in the non-inverting mode. With AV e b 1, 0.01% settling
time is slightly greater than 100 ns.
Supply Voltage Range and Single Supply
Operation
The EL2360C has been designed to operate with
supply voltages from g 2V to g 15V. Optimum
bandwidth, slew rate, and video characteristics
are obtained at higher supply voltages. However,
at g 2V supplies, the b 3 dB bandwidth at AV e
a 2 is a respectable 70 MHz. The following figure
is an oscilloscope plot of the EL2360C at g 2V
supplies, AV e a 2, RF e RG e 560X, driving a
load of 150X, showing a clean g 600 mV signal at
the output.
Power Dissipation
The EL2360C amplifier combines both high
speed and large output current capability at a
moderate supply current in very small packages.
It is possible to exceed the maximum junction
temperature allowed under certain supply voltage, temperature, and loading conditions. To ensure that the EL2360C remains within it’s absolute maximum ratings, the following discussion
will help to avoid exceeding the maximum junction temperature.
The maximum power dissipation allowed in a
package is determined according to [1] :
PDMAX e
2360 – 11
TJMAX b TAMAX
[1]
iJA
where:
If a single supply is desired, values from a 4V to
a 30V can be used as long as the input common
mode range is not exceeded. When using a single
supply, be sure to either 1) DC bias the inputs at
an appropriate common mode voltage and AC
couple the signal, or 2) ensure the driving signal
is within the common mode range of the
EL2360C, which is typically 1.5V from each supply rail.
TJMAX e Maximum Junction Temperature
TAMAX e Maximum Ambient Temperature
iJA e Thermal Resistance of the Package
PDMAX e Maximum Power Dissipation
in the Package.
The maximum power dissipation actually produced by an IC is the total quiescent supply current times the total power supply voltage, plus
the power in the IC due to the load, or [2]
Settling Characteristics
PDMAX e N*(VS * ISMAX a (VS bVOUT) *
The EL2360C offers superb settling characteristics to 0.1%, typically in the 35 ns to 40 ns range.
There are no aberrations created from the input
stage which often cause longer settling times in
other current feedback amplifiers. The EL2360C
is not slew rate limited, therefore any size step up
to g 10V gives approximately the same settling
time.
VOUT
RL
)
[2]
where:
Ne
Number of amplifiers
VS e
Total Supply Voltage
ISMAX e Maximum Supply Current per amplifier
VOUT e Maximum Output Voltage of the Application
RL e
Load Resistance tied to Ground
As can be seen from the Long Term Settling Error curve, for AV e a 1, there is approximately a
0.035% residual which tails away to 0.01% in
about 40 ms. This is a thermal settling error
12
EL2360C
Triple 130 MHz Current Feedback Amplifier
Applications Information Ð Contd.
If we set the two PDMAX equations, [1] and [2] ,
equal to each other, and solve for VS, we can get a
family of curves for various loads and output
voltages according to [3] :
RL*(TJMAX b TAMAX)
VS e
N*iJA
Current Limit
The EL2360C has internal current limits that
protect the circuit in the event of an output being
shorted to ground. This limit is set at 100 mA
nominally and reduces with the junction temperature. At TJ e 150§ C, the current limits at about
65 mA. If any one output is shorted to ground,
the power dissipation could be well over 1W, and
much greater if all outputs are shorted. Heat removal is required in order for the EL2360C to
survive an indefinite short.
a (VOUT)2
(IS*RL) a VOUT
[3]
The figures below show total supply voltage VS
vs RL for various output voltage swings for the
PDIP and SOIC packages. The curves assume
WORST CASE conditions of TA e a 85§ C and
IS e 11.3 mA per amplifier. The curves do not
include heat removal or forcing air, or the simple
fact that the package will be attached to a circuit
board, which can also provide some form of heat
removal. Larger temperature and voltage ranges
are possible with heat removal and forcing air
past the part.
Driving Cables and Capacitive Loads
When used as a cable driver, double termination
is always recommended for reflection-free performance. For those applications, the back-termination series resistor will de-couple the EL2360C
from the cable and allow extensive capacitive
drive. However, other applications may have
high capacitive loads without a back-termination
resistor. In these applications, a small series resistor (usually between 5X and 50X) can be placed
in series with the output to eliminate most peaking. The gain resistor (RG) can then be chosen to
make up for any gain loss which may be created
by this additional resistor at the output. In many
cases it is also possible to simply increase the value of the feedback resistor (RF) to reduce the
peaking.
Supply Voltage vs RL
for Various VOUT (PDIP Package)
2360 – 12
Supply Voltage vs RL
for Various VOUT (SOIC Package)
2360 – 13
13
EL2360C
Triple 130 MHz Current Feedback Amplifier
*
Transimpedance Stage
*
g1 0 18 17 0 1.0
rol 18 0 2Meg
cdp 18 0 2.285pF
*
*
Output Stage
*
q1 4 18 19 qp
q2 7 18 20 qn
q3 7 19 21 qn
q4 4 20 22 qp
r7 21 6 4
r8 22 6 4
ios1 7 19 2mA
ios2 20 4 2mA
*
*
Supply Current
*
ips 7 4 2.5mA
*
*
Error Terms
*
ivos 0 23 2mA
vxx 23 0 0V
e4 24 0 3 0 1.0
e5 25 0 7 0 1.0
e6 26 0 4 0 b1.0
r9 24 23 562
r10 25 23 1K
r11 26 23 1K
*
*
Models
*
.model qn npn(is e 5eb15 bf e 100 tf e 0.1 ns)
.model qp pnp(is e 5eb15 bf e 100 tf e 0.1 ns)
.model dclamp d(is e 1eb30 ibv e 0.266
a bv e 2.24v n e 4)
.ends
*
EL2360C Macromodel
*
Revision A, June 1996
*
AC characteristics used: Rf e Rg e 560 ohms
*
Pin numbers reflect a standard single opamp
a input
*
Connections:
b input
*
l
a Vsupply
*
l
l
b Vsupply
*
l
l
l
*
output
l
l
l
l
*
l
l
l
l
l
.subckt EL2360/EL
3
2
7
4
6
*
*
Input Stage
*
e1 10 0 3 0 1.0
vis 10 9 0V
h2 9 12 vxx 1.0
r1 2 11 130
l1 11 12 25nH
iinp 3 0 0.5mA
iinm 2 0 5mA
r12 3 0 2 Meg
*
*
Slew Rate Limiting
*
h1 13 0 vis 600
r2 13 14 1K
d1 14 0 dclamp
d2 0 14 dclamp
*
*
High Frequency Pole
*
e2 30 0 14 0 0.00166666666
l3 30 17 0.43mH
c5 17 0 0.27pF
r5 17 0 500
*
14
TD is 5.1in
TD is 4.8in
EL2360C Macromodel
EL2360C
Triple 130 MHz Current Feedback Amplifier
EL2360C Macromodel Ð Contd.
2360 – 14
15
EL2360C
EL2360C
Triple 130 MHz Current Feedback Amplifier
General Disclaimer
Specifications contained in this data sheet are in effect as of the publication date shown. Elantec, Inc. reserves the right to make changes
in the circuitry or specifications contained herein at any time without notice. Elantec, Inc. assumes no responsibility for the use of any
circuits described herein and makes no representations that they are free from patent infringement.
June 1996 Rev A
WARNING Ð Life Support Policy
Elantec, Inc. products are not authorized for and should not be
used within Life Support Systems without the specific written
consent of Elantec, Inc. Life Support systems are equipment intended to support or sustain life and whose failure to perform
when properly used in accordance with instructions provided can
be reasonably expected to result in significant personal injury or
death. Users contemplating application of Elantec, Inc. products
in Life Support Systems are requested to contact Elantec, Inc.
factory headquarters to establish suitable terms & conditions for
these applications. Elantec, Inc.’s warranty is limited to replacement of defective components and does not cover injury to persons or property or other consequential damages.
Elantec, Inc.
1996 Tarob Court
Milpitas, CA 95035
Telephone: (408) 945-1323
(800) 333-6314
Fax: (408) 945-9305
European Office: 44-71-482-4596
16
Printed in U.S.A.