TPS65058 www.ti.com ........................................................................................................................................................................................................ SLVS851 – MAY 2008 2.25 MHz Dual STEP DOWN CONVERTER WITH 3 LOW-INPUT VOLTAGE LDOs FEATURES APPLICATIONS • Up To 95% Efficiency • Output Current for DC/DC Converters: – DCDC1 = 0.6A; DCDC2 = 1A • VIN Range for DC/DC Converters From 2.5V to 6V • Dynamic Voltage Switching for Processor Core Supply Supported • 2.25MHz Fixed Frequency Operation • Power Save Mode at Light Load Current • 180° Out-of-Phase Operation • Output Voltage Accuracy in PWM mode ±1% • Total Typical 32µA Quiescent Current for Both DC/DC Converters • 100% Duty Cycle for Lowest Dropout • One General-Purpose 400mA LDO • Two General-Purpose 200mA LDOs • VIN Range for LDOs from 1.5V to 6.5V • Reset Generator and Power Monitor • Available in a 4 mm x 4 mm 24-Pin QFN Package • 1 2 Satellite Radio Modules TPS 65058 10 W VIN VINDCDC1/2 VCC ENABLE 2.2 mH EN_DCDC1 DCDC1(I/O) STEP-DOWN CONVERTER MODE L1 DCDC2(core) EN_DCDC2 DEF_DCDC2 STEP-DOWN CONVERTER 3.3 V FB_DCDC 10uF PGND1 PGOOD1 ENABLE Voltage Switching (1/0) VIN 22 mF 1 mF 2.2 mH 1.8 V / 1.2 V L2 FB_DCDC2 10 mF PGND2 PGOOD2 VIN 2.2 mF ENABLE Voltage Switching (1/0) VIN_LDO1 EN_LDO1 VLDO1 VLDO1 4.7 mF 400 mA LDO DEF_LDO VIN_LDO2/ VIN VLDO2 2.2 mF ENABLE 3.3 V / 3.3 V EN_LDO2 VLDO2 1.8 V / 1.2 V 2.2 mF 200 mA LDO EN_LDO3 VLDO3 ENABLE VLDO3 1.8 V / 1.3 V 2.2 mF 200 mA LDO RESET I/O Voltage R19 RESET AGND NOTE: Other voltage options available upon request. Contact your Texas Instruments representative. DESCRIPTION The TPS65058 is an integrated Power Management IC for applications powered by one Li-Ion or Li-Polymer cell, which require multiple power rails. The TPS65058 provides two highly efficient, 2.25MHz step down converters targeted at providing the core voltage and I/O voltage in a processor based system. Both step-down converters enter a low power mode at light load for maximum efficiency across the widest possible range of load currents. For low noise applications, the devices can be forced into fixed frequency PWM mode by pulling the MODE pin high. Both converters allow the use of small inductors and capacitors to achieve a small solution size. TPS65058 provides an output current of up to 0.6A on the DCDC1 converter, and up to 1A on the DCDC2 converter. The TPS65058 also integrates one 400mA LDO and two 200mA LDO voltage regulators, which can be turned on/off using separate enable pins on each LDO. Each LDO operates with an input voltage range between 1.5V and 6.5V allowing them to be supplied from one of the step down converters or directly from the main battery. The TPS65058 comes in a small 24-pin leadless package (4mm × 4mm QFN) with a 0,5mm pitch. 1 2 Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of Texas Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet. PowerPAD is a trademark of Texas Instruments. PRODUCTION DATA information is current as of publication date. Products conform to specifications per the terms of the Texas Instruments standard warranty. Production processing does not necessarily include testing of all parameters. Copyright © 2008, Texas Instruments Incorporated TPS65058 SLVS851 – MAY 2008 ........................................................................................................................................................................................................ www.ti.com These devices have limited built-in ESD protection. The leads should be shorted together or the device placed in conductive foam during storage or handling to prevent electrostatic damage to the MOS gates. ORDERING INFORMATION (1) (1) (2) TA PART NUMBER QFN (2) PACKAGE PACKAGE MARKING –40°C to 85°C TPS65058 RGE 65058 For the most current package and ordering information, see the Package Option Addendum at the end of this document, or see the TI web site at www.ti.com. The RGE package is available in tape and reel. Add R suffix (TPS65058RGER) to order quantities of 3000 parts per reel. Add T suffix (TPS65058RGET) to order quantities of 250 parts per reel. ABSOLUTE MAXIMUM RATINGS over operating free-air temperature range (unless otherwise noted) (1) UNITS VI II Input voltage range on all pins except AGND, PGND, and EN_LDO1 pins with respect to AGND –0.3 V to 7 V Input voltage range on EN_LDO1 pin with respect to AGND –0.3 V to VCC + 0.5 V Current at VINDCDC1/2, L1, PGND1, L2, PGND2 1800 mA Current at all other pins 1000 mA Continuous total power dissipation See Dissipation Rating Table TA Operating free-air temperature –40°C to 85°C TJ Maximum junction temperature 125°C Tstg Storage temperature range (1) –65°C to 150°C Stresses beyond those listed under absolute maximum ratings may cause permanent damage to the device. These are stress ratings only and functional operation of the device at these or any other conditions beyond those indicated under recommended operating conditions is not implied. Exposure to absolute-maximum-rated conditions for extended periods may affect device reliability. DISSIPATION RATINGS 2 PACKAGE RθJA TA ≤ 25°C POWER RATING DERATING FACTOR ABOVE TA = 25°C TA = 70°C POWER RATING TA = 85°C POWER RATING RGE 35 K/W 2.8 W 28 mW/K 1.57 W 1.14 W Submit Documentation Feedback Copyright © 2008, Texas Instruments Incorporated Product Folder Link(s) :TPS65058 TPS65058 www.ti.com ........................................................................................................................................................................................................ SLVS851 – MAY 2008 RECOMMENDED OPERATING CONDITIONS MIN NOM 2.5 MAX 6 UNIT VINDCDC1/2 Input voltage range for step-down converters VDCDC1 Output voltage range for VDCDC1 step-down converter VDCDC2 Output voltage range for VDCDC2 step-down converter (DEF_DCDC2 = 1/0) VINLDO1, VINLDO2/3 Input voltage range for LDOs VLDO1 Output voltage range for LDO1 (DEF_LDO = 1/0) 3.3/3.3 V VLDO2 Output voltage range for LDO2 (DEF_LDO = 1/0) 1.8/1.2 V VLDO3 Output voltage for LDO3 (DEF_LDO = 1/0) 1.8/1.3 IOUTDCDC1 Output current at L1 L1 Inductor at L1 (1) V 1.8/1.2 V 1.5 6.5 1.5 V V 600 (1) V 3.3 mA µH 2.2 µF CINDCDC1/2 Input capacitor at VINDCDC1/2 COUTDCDC1 Output capacitor at VDCDC1 (1) 22 IOUTDCDC2 Output current at L2 L2 Inductor at L2 (1) 1.5 2.2 µH COUTDCDC2 Output capacitor at VDCDC2 (1) 10 22 µF CVCC Input capacitor at VCC (1) 10 µF 22 1000 (1) mA 1 µF 2.2 µF Cin1-2 Input capacitor at VINLDO1, VINLDO2/3 COUT1-2 Output capacitor at VLDO1-3 ILDO1 Output current at VLDO1 400 mA ILDO2,3 Output current at VLDO2,3 200 mA TA Operating ambient temperature range –40 85 °C TJ Operating junction temperature range –40 125 °C RCC Resistor from battery voltage to VCC used for filtering (2) 10 Ω (1) (2) (1) µF 2.2 1 See the Application Information section of this data sheet for more details. Up to 2 mA can flow into VCC when both converters are running in PWM, this resistor causes the UVLO threshold to be shifted accordingly. Submit Documentation Feedback Copyright © 2008, Texas Instruments Incorporated Product Folder Link(s) :TPS65058 3 TPS65058 SLVS851 – MAY 2008 ........................................................................................................................................................................................................ www.ti.com ELECTRICAL CHARACTERISTICS Vcc = VINDCDC1/2 = 3.6V, EN = Vcc, MODE = GND, L = 2.2µH, COUT = 22µF, TA = –40°C to 85°C typical values are at TA = 25°C (unless otherwise noted). PARAMETER TEST CONDITIONS MIN TYP MAX UNIT SUPPLY CURRENT Vcc IQ IQ Input voltage range 2.5 Operating quiescent current Total current into VCC, VINDCDC1/2, VINLDO1, VINLDO2/3 Operating quiescent current into VCC 6. V 20 30 µA 32 40 µA One converter, IOUT = 0 mA, PFM mode enabled (Mode = GND) device not switching, EN_DCDC1 = Vin OR EN_DCDC2 = Vin; EN_LDO1 = EN_LDO2 = EN_LDO3 = Vin 145 210 µA One converter, IOUT = 0 mA, Switching with no load (Mode = Vin), PWM operation EN_DCDC1 = Vin OR EN_DCDC2 = Vin; EN_LDO1 = EN_LDO2 = EN_LDO3 = GND 0.85 mA Two converters, IOUT = 0 mA, Switching with no load (Mode = Vin), PWM operation EN_DCDC1 = Vin AND EN_DCDC2 = Vin; EN_LDO1 = EN_LDO2 = EN_LDO3 = GND 1.25 mA One converter, IOUT = 0 mA.PFM mode enabled (Mode = GND) device not switching, EN_DCDC1 = Vin OR EN_DCDC2 = Vin; EN_LDO1= EN_LDO2 = EN_LDO3 = GND Two converters, IOUT = 0 mA, PFM mode enabled (Mode = 0) device not switching, EN_DCDC1 = Vin AND EN_DCDC2 = Vin; EN_LDO1 = EN_LDO2 = EN_LDO3 = GND I(SD) Shutdown current EN_DCDC1 = EN_DCDC2 = GND EN_LDO1 = EN_LDO2 = EN_LDO3 = GND V(UVLO) Undervoltage lockout threshold for DCDC converters and LDOs Voltage at VCC 9 12 µA 1.8 2 V EN_DCDC1, EN_DCDC2, EN_LDO1, EN_LDO2, EN_LDO3, MODE VIH High-level input voltage MODE, EN_DCDC1, EN_DCDC2, EN_LDO1, EN_LDO2, EN_LDO3, DEF,DEF_LDO,DEF_DCDC2 1.2 VCC V VIL Low-level input voltage MODE, EN_DCDC1, EN_DCDC2, EN_LDO1, EN_LDO2, EN_LDO3, DEF_LDO, DEF_DCDC2 0 0.4 V IIN Input bias current MODE, EN_DCDC1, EN_DCDC2, EN_LDO1, EN_LDO2, EN_LDO3, DEF_LDO, DEF_DCDC2 µA MODE = GND or VIN 0.01 1 VINDCDC1/2 = 3.6V 250 350 VINDCDC1/2 = 2.5V 380 500 250 POWER SWITCH rDS(on) P-channel MOSFET on resistance DCDC1, DCDC2 ILD_PMOS P-channel leakage current V(DS) = 6V rDS(on) N-channel MOSFET on resistance VINDCDC1/2 = 3.6V 180 VINDCDC1/2 = 2.5V 250 ILK_NMOS N-channel leakage current I(LIMF) Forward Current Limit PMOS (High-Side) and NMOS (Low side) TSD Thermal shutdown Increasing junction temperature 150 °C Thermal shutdown hysteresis Decreasing junction temperature 20 °C DCDC1, DCDC2 1 V(DS) = 6V DCDC1 DCDC2 2.5V ≤ VIN ≤ 6V 7 10 1.19 1.4 1.65 0.85 1.0 1.15 mΩ µA mΩ µA A OSCILLATOR fSW 4 Oscillator frequency 2.025 Submit Documentation Feedback 2.25 2.475 MHz Copyright © 2008, Texas Instruments Incorporated Product Folder Link(s) :TPS65058 TPS65058 www.ti.com ........................................................................................................................................................................................................ SLVS851 – MAY 2008 ELECTRICAL CHARACTERISTICS (continued) Vcc = VINDCDC1/2 = 3.6V, EN = Vcc, MODE = GND, L = 2.2µH, COUT = 22µF, TA = –40°C to 85°C typical values are at TA = 25°C (unless otherwise noted). PARAMETER TEST CONDITIONS MIN TYP MAX VIN = 2.5V to 6V, Mode = GND, PFM operation, 0 mA < IOUT < IOUTMAX -2% 0 2% VIN = 2.5V to 6V, Mode = VIN, PWM operation, 0 mA < IOUT < IOUTMAX –1% 0 1% UNIT OUTPUT VOUT DC output voltage accuracy DCDC1, DCDC2 ΔVOUT Power save mode ripple voltage IOUT = 1mA, Mode = GND, VO = 1.3V, Bandwidth = 20MHz 25 mVPP tStart Start-up time Time from active EN to Start switching 170 µs tRamp VOUT Ramp up Time Time to ramp from 5% to 95% of VOUT 750 RESET delay time Input voltage at threshold pin rising RESET output low voltage IOL = 1mA VOL 80 100 µs 120 0.2 RESET sink current RESET output leakage current ms V 1 mA 10 nA VLDO1, VLDO2, VLDO3 LOW DROPOUT REGULATORS VINLDO Input voltage range for LDO1, LDO2, LDO3 VLDO1 LDO1 output voltage range (DEF_LDO = 1/0) 3.3/3.3 V VLDO2 LDO2 output voltage range(DEF_LDO = 1/0) 1.8/1.2 V VLDO3 LDO3 output voltage (DEF_LDO = 1/0) 1.8/1.3 V V(FB) Feedback voltage for FB_LDO1, FB_LDO2 1 V IO 1.5 6.5 V Maximum output current for LDO1 400 mA Maximum output current for LDO2, LDO3 200 mA LDO1 short-circuit current limit VLDO1 = GND 850 mA LDO2 & LDO3 short-circuit current limit VLDO2 = GND, VLDO3 = GND 420 mA Dropout voltage at LDO1 IO = 400mA, VINLDO1 = 1.8V 280 mV Dropout voltage at LDO2, LDO3 IO = 200mA, VINLDO = 1.8V 280 mV Output voltage accuracy for LDO1, LDO2, LDO3 IO = 10mA –2% 1% Line regulation for LDO1, LDO2, LDO3 VINLDO1,2 = VLDO1,2 + 0.5V (min. 2.5V) to 6.5V, IO = 10 mA –1% 1% Load regulation for LDO1, LDO2, LDO3 IO = 0mA to 400mA for LDO1 IO = 0mA to 200mA for LDO2, LDO3 –1% 1% Regulation time for LDO1, LDO2, LDO3 Load change from 10% to 90% 10 µs PSRR Power supply rejection ratio f = 10kHz; IO = 50mA; VI = VO + 1 V 70 dB R(DIS) Internal discharge resistor at VLDO1, VLDO2, VLDO3 Active when LDO is disabled 300 Ω TSD Thermal shutdown Increasing junction temperature 140 °C Thermal shutdown hysteresis Decreasing junction temperature 20 °C I(SC) Submit Documentation Feedback Copyright © 2008, Texas Instruments Incorporated Product Folder Link(s) :TPS65058 5 TPS65058 SLVS851 – MAY 2008 ........................................................................................................................................................................................................ www.ti.com PIN ASSIGNMENTS FB_DCDC2 PGND1 L1 VINDCDC1/2 L2 PGND2 RGE PACKAGE (TOP VIEW) 18 17 16 15 14 13 FB_DCDC1 EN_DCDC1 EN_DCDC2 EN_LDO1 MODE AGND 12 11 10 9 8 7 19 20 21 22 23 24 EN_LDO3 EN_LDO2 RESET VLDO3 VINLDO2/3 VINLDO2 VCC VIN_LDO1 VLDO1 DEF_LDO DEF_DCDC2 VCC 1 2 3 4 5 6 TERMINAL FUNCTIONS TERMINAL I/O DESCRIPTION NAME NO. VCC 1, 6 I Power supply for digital and analog circuitry of DCDC1, DCDC2 and LDOs. This pin must be connected to the same voltage supply as VINDCDC1/2. FB_DCDC1 19 I Feedback input for DCDC1 MODE 23 I Select between Power Safe Mode and forced PWM Mode for DCDC1 and DCDC2. In Power Safe Mode PFM is used at light loads, PWM for higher loads. If PIN is set to high level, forced PWM Mode is selected. If Pin has low level, then Device operates in Power Safe Mode. VINDCDC1/2 16 I Input voltage for VDCDC1 and VDCDC2 step-down converter. This must be connected to the same voltage supply as VCC. FB_DCDC2 13 I Feedback input for DCDC1 L1 17 O Switch pin of converter 1. Connected to Inductor PGND1 18 I GND for converter 1 PGND2 14 I GND for converter 2 AGND 24 I Analog GND, connect to PGND and PowerPAD™ L2 15 O Switch Pin of converter 2. Connected to Inductor. EN_DCDC1 20 I Enable Input for converter 1, active high EN_DCDC2 21 I Enable Input for converter 2, active high VINLDO1 2 I Input voltage for LDO1 VINLDO2/3 8 I Input voltage for LDO2 and LDO3 VLDO1 3 O Output voltage of LDO1 VLDO2 7 O Output voltage of LDO2 VLDO3 9 O Output voltage of LDO3 DEF_DCDC2 5 I Switches output voltages at DCDC2, logic high = 1.8V, logic low = 1.2V DEF_LDO 4 I Switches output voltages at LDO1, logic high = 3.3V, logic low = 3.3V Switches output voltages at LDO2, logic high = 1.8V, logic low = 1.2V Switches output voltages at LDO3, logic high = 1.8V, logic low = 1.3V EN_LDO1 22 I Enable input for LDO1. Logic high enables the LDO, logic low disables the LDO. EN_LDO2 11 I Enable input for LDO2. Logic high enables the LDO, logic low disables the LDO. EN_LDO3 12 I Enable input for LDO3. Logic high enables the LDO, logic low disables the LDO. 6 Submit Documentation Feedback Copyright © 2008, Texas Instruments Incorporated Product Folder Link(s) :TPS65058 TPS65058 www.ti.com ........................................................................................................................................................................................................ SLVS851 – MAY 2008 TERMINAL FUNCTIONS (continued) TERMINAL NAME NO. RESET 10 PowerPAD™ – I/O DESCRIPTION O Open drain active low reset output, 100ms reset delay time after both DCDC1 and DCDC2 are within 95% of nominal output voltage (see Reset Generation and Output Monitoring section) Connect to GND FUNCTIONAL BLOCK DIAGRAM 10 W VINDCDC1/2 VCC VIN 22 mF 1 mF ENABLE VIN 2.2 mH EN_DCDC1 DCDC1 (I/O) STEP-DOWN CONVERTER 600 mA MODE L1 3.3 V FB_DCDC1 10 mF PGND1 PGOOD1 2.2 mF DCDC2 (core) ENABLE Voltage Switching (1/0) EN_DCDC2 DEF_DCDC2 1.8V / 1.2V L2 FB_DCDC2 STEP-DOWN CONVERTER 1A 10 mF PGND2 PGOOD2 VIN 2.2 mF ENABLE Voltage Switching (1/0) VIN 2.2 mF ENABLE ENABLE VLDO1 VIN_LDO1 3.3 V / 3.3 V VLDO1 4.7 mF EN_LDO1 400 mA LDO DEF_LDO VIN_LDO2/3 VLDO2 EN_LDO2 VLDO2 1.8 V / 1.2 V 2.2 mF 200 mA LDO EN_LDO3 VLDO3 VLDO3 1.8 V / 1.3 V 2.2 mF 200 mA LDO I/O Voltage RESET R19 RESET AGND Submit Documentation Feedback Copyright © 2008, Texas Instruments Incorporated Product Folder Link(s) :TPS65058 7 TPS65058 SLVS851 – MAY 2008 ........................................................................................................................................................................................................ www.ti.com TYPICAL CHARACTERISTICS Table of Graphs FIGURE Efficiency converter 1 vs Load current PWM/PFM mode Figure 1 Efficiency converter 1 vs Load current PWM mode Figure 2 Efficiency converter 2 vs Load current PWM/PFM mode Figure 3 Efficiency converter 2 vs Load current PWM mode Figure 4 Output voltage ripple in PFM mode vs Input voltage Figure 5 Output voltage ripple in PWM mode Scope plot Figure 6 Startup converter 1 and 2 Scope plot Figure 7 Startup LDO1 to 3 Scope plot Figure 8 Load transient response converter 2 in PWM mode Scope plot Figure 9 Load transient response converter 2 in PFM mode Scope plot Figure 10 Line transient response converter 1 Scope plot Figure 11 Line transient response converter 2 Scope plot Figure 12 Load transient response LDO 1 Scope plot Figure 13 Load transient response LDO 2 and LDO 3 Scope plot Figure 14 Line transient response LDO 1 Scope plot Figure 15 Power supply rejection ratio LDO 1 vs Frequency Figure 16 EFFICIENCY CONVERTER 1 vs LOAD CURRENT PWM/PFM MODE EFFICIENCY CONVERTER 1 vs LOAD CURRENT PWM MODE 100 100 3.8 V VO = 3.3 V, 90 T = 25°C, A PFM Mode 80 90 80 60 5V 3.4 V 3.8 V 70 Efficiency - % Efficiency - % 70 4.2 V 50 40 30 60 3.4 V 50 40 5V 30 4.2 V 20 10 0 0.0001 20 VO = 3.3 V, TA = 25°C, PFM Mode 0.001 0.01 0.1 IO - Output Current - A 10 1 0 0.0001 Figure 1. 8 0.001 0.01 0.1 IO - Output Current - A 1 Figure 2. Submit Documentation Feedback Copyright © 2008, Texas Instruments Incorporated Product Folder Link(s) :TPS65058 TPS65058 www.ti.com ........................................................................................................................................................................................................ SLVS851 – MAY 2008 EFFICIENCY CONVERTER 2 vs LOAD CURRENT PWM/PFM MODE EFFICIENCY CONVERTER 2 vs LOAD CURRENT PWM MODE 100 100 90 90 3.4 V 80 80 VO = 1.2 V, TA = 25°C, PWM Mode 3.4 V 5V 70 4.2 V Efficiency - % Efficiency - % 70 60 3.8 V 50 40 30 4.2 V 50 40 5V 30 20 20 VO = 1.2 V, TA = 25°C, PFM/PWM Mode 10 0 0.0001 0.001 0.01 0.1 IO - Output Current - A 1 10 0 0.0001 10 0.001 0.01 0.1 IO - Output Current - A 1 Figure 3. Figure 4. OUTPUT VOLTAGE RIPPLE PFM MODE OUTPUT VOLTAGE RIPPLE PWM MODE 10 CH1 (VDCDC1 = 3.3 V) 20 mV/div 20 mV/div 3.8 V 60 Mode = Low, VI = 4.2 V, CH1 (VDCDC1 = 3.3 V) Mode = High, VI = 4.2 V, TA = 25oC CH2 (VDCDC2 = 1.2 V) 20 mV/div CH4 (IL DCDC1 = 80 mA) CH3 (IL DCDC1 = 600 mA) 100 mA/div 100 mA/div 200 mA/div 200 mA/div CH3 (IL DCDC2 = 80 mA) CH2 (VDCDC2 = 1.2 V) 20 mV/div o TA = 25 C CH4 (IL DCDC2 = 600 mA) t − Time = 400 ns/div t − Time = 2 ms/div Figure 5. Figure 6. Submit Documentation Feedback Copyright © 2008, Texas Instruments Incorporated Product Folder Link(s) :TPS65058 9 TPS65058 SLVS851 – MAY 2008 ........................................................................................................................................................................................................ www.ti.com Mode = Low, VI = 3.6 V, TA = 25oC 1 V/div CH1 (EN_DCDC1 / 2 EN_LDO1) 5 V/div STARTUP LDO1 TO LDO3 1 V/div CH1 (EN_LDO1 / 2 / 3) DEF_LDO1 = 1, VI = 3.6 V, TA = 25oC CH2 (VLDO1) VDCDC1 = 3.3 V, VDCDC2 = 1.2 V, DCDC1 IO = 600 mA DCDC2 IO = 600 mA 1 V/div CH3 (VDCDC2) 1 V/div 1 V/div CH2 (VDCDC) CH3 (VLDO2) LDO1 IO = 100 mA, LDO2 IO = 600 mA, 1 V/div 5 V/div STARTUP CONVERTER 1 AND 2 LDO3 IO = 600 mA CH4 (VLDO1) CH4 (VLDO3) t − Time = 200 ms/div LOAD TRANSIENT RESPONSE CONVERTER 2 IN PWM MODE LOAD TRANSIENT RESPONSE CONVERTER 2 IN PFM MODE 50 mV/div CH2 (IO DCDC2) Mode = High VI = 3.6 V, VO DCDC2 = 1.2 V, DCDC2 IO = 60 mA to 540 mA TA = 25oC 200 mA/div 50 mV/div Figure 8. CH1 (VO DCDC2) 200 mA/div t − Time = 40 ms/div Figure 7. CH1 (VO DCDC2) Mode = Low VI = 3.6 V, CH2 (IO DCDC2) o TA = 25 C t − Time = 100 ms/div t − Time = 100 ms/div Figure 9. 10 VO DCDC2 = 1.2 V, DCDC2 IO = 600 mA to 540 mA Figure 10. Submit Documentation Feedback Copyright © 2008, Texas Instruments Incorporated Product Folder Link(s) :TPS65058 TPS65058 www.ti.com ........................................................................................................................................................................................................ SLVS851 – MAY 2008 500 mV/div LINE TRANSIENT RESPONSE CONVERTER 2 CH1 (VI DCDC1) CH1 (VI) Mode = High VI = 3.6 V to 4.5 V to 3.6 V, Mode = High VI = 3.6 V to 4.5 V to 3.6 V, CDC1 IO = 600 mA, CDC1 IO = 600 mA, o TA = 25 C 20 mA/div 20 mA/div 500 mV/div LINE TRANSIENT RESPONSE CONVERTER 1 CH2 (VO DCDC1) TA = 25oC CH2 (VO) t − Time = 100 ms/div t − Time = 100 ms/div Figure 11. Figure 12. LOAD TRANSIENT RESPONSE LDO1 LOAD TRANSIENT RESPONSE LDO2 AND LDO3 VI = 3.6 V VI = 3.6 V VO LDO3 = 3.3 V, VO LDO3 = 1.83 V, LDO3 IO = 20 mA to 180 mA, TA = 25oC LDO1 IO = 40 mA to 360 mA, 50 mV/div TA = 25 C CH1 (VO LDO1) 200 mA/div 200 mA/div 50 mV/div o CH2 (IO LDO1) CH1 (VO DCDC2) CH2 (IO DCDC2) t − Time = 100 ms/div t − Time = 100 ms/div Figure 13. Figure 14. Submit Documentation Feedback Copyright © 2008, Texas Instruments Incorporated Product Folder Link(s) :TPS65058 11 TPS65058 SLVS851 – MAY 2008 ........................................................................................................................................................................................................ www.ti.com POWER SUPPLY REJECTION RATIO, LDO1 vs FREQUENCY LINE TRANSIENT RESPONSE LDO1 100 VI = 3.6 V to 4.2 V to 3.6 V LDO IO = 100 mA, 80 Rejection Ratio - dB 20 mA/div 500 mV/div TA = 25oC CH1 (VI LDO1) VIN = 3.8 V, VOUT = 3.3 V, IOUT = 10 mA, TA = 25°C, 90 CIN = 2.2 mF, 70 COUT = 4.7 mF 60 50 40 30 20 CH2 (VO LDO1) 10 t − Time = 100 ms/div 0 10 Figure 15. 12 100 1k 10 k 100 k f - Frequency - Hz 1M 10 M Figure 16. Submit Documentation Feedback Copyright © 2008, Texas Instruments Incorporated Product Folder Link(s) :TPS65058 TPS65058 www.ti.com ........................................................................................................................................................................................................ SLVS851 – MAY 2008 DETAILED DESCRIPTION OPERATION The TPS65058 includes two synchronous step-down converters. The converters operate with 2.25MHz fixed frequency pulse width modulation (PWM) at moderate to heavy load currents. At light load currents, the converters automatically enter Power Save Mode and operate with PFM (Pulse Frequency Modulation). During PWM operation, the converters use a unique fast response voltage mode controller scheme with input voltage feed-forward to achieve good line and load regulation allowing the use of small ceramic input and output capacitors. At the beginning of each clock cycle initiated by the clock signal, the P-channel MOSFET switch is turned on and the inductor current ramps up until the comparator trips and the control logic turns off the switch. The current limit comparator will also turn off the switch in case the current limit of the P-channel switch is exceeded. After the adaptive dead time prevents shoot through current, the N-channel MOSFET rectifier is turned on and the inductor current ramps down. The next cycle is initiated by the clock signal again turning off the N-channel rectifier and turning on the P-channel switch. The two DC-DC converters operate synchronized to each other, with converter 1 as the master. A 180° phase shift between Converter 1 and Converter 2 decreases the input RMS current. Therefore smaller input capacitors can be used. The converters output voltage is set by an external resistor divider connected to FB_DCDC1 or FB_DCDC2, respectively. See application section for more details. POWER SAVE MODE The Power Save Mode is enabled with Mode Pin set to low. If the load current decreases, the converters will enter Power Save Mode operation automatically. During Power Save Mode the converters operate with reduced switching frequency in PFM mode and with a minimum quiescent current to maintain high efficiency. The converter will position the output voltage typically 1% above the nominal output voltage. This voltage positioning feature minimizes voltage drops caused by a sudden load step. In order to optimize the converter efficiency at light load the average current is monitored and if in PWM mode the inductor current remains below a certain threshold, then Power Save Mode is entered. The typical threshold can be calculated according to: Equation 1: Average output current threshold to enter PFM mode. VINDCDC I PFM_enter + 32 W (1) Equation 2: Average output current threshold to leave PFM mode. VINDCDC I PFM_leave + 24 W (2) During the Power Save Mode the output voltage is monitored with a comparator. As the output voltage falls below the skip comparator threshold (skip comp) of VOUTnominal +1%, the P-channel switch will turn on and the converter effectively delivers a constant current as defined above. If the load is below the delivered current then the output voltage will rise until the same threshold is crossed again, whereupon all switching activity ceases, hence reducing the quiescent current to a minimum until the output voltage has dropped below the threshold again. If the load current is greater than the delivered current then the output voltage will fall until it crosses the skip comparator low (Skip Comp Low) threshold set to 1% below nominal Vout, whereupon Power Save Mode is exited and the converter returns to PWM mode. These control methods reduce the quiescent current typically to 12µA per converter and the switching frequency to a minimum thereby achieving the highest converter efficiency. The PFM mode operates with very low output voltage ripple. The ripple depends on the comparator delay and the size of the output capacitor; increasing capacitor values will make the output ripple tend to zero. The Power Save Mode can be disabled by driving the MODE pin high. Both converters will operate in fixed PWM mode. Power Save Mode Enable/Disable applies to both converters. Submit Documentation Feedback Copyright © 2008, Texas Instruments Incorporated Product Folder Link(s) :TPS65058 13 TPS65058 SLVS851 – MAY 2008 ........................................................................................................................................................................................................ www.ti.com Dynamic Voltage Positioning This feature reduces the voltage under/overshoots at load steps from light to heavy load and vice versa. It is activated in Power Save Mode operation when the converter runs in PFM Mode. It provides more headroom for both the voltage drop at a load step increase and the voltage increase at a load throw-off. This improves load transient behavior. At light loads, in which the converters operate in PFM Mode, the output voltage is regulated typically 1% higher than the nominal value. In case of a load transient from light load to heavy load, the output voltage will drop until it reaches the skip comparator low threshold set to –1% below the nominal value and enters PWM mode. During a load throw off from heavy load to light load, the voltage overshoot is also minimized due to active regulation turning on the N-channel switch. Smooth increased load +1% PFM Mode light load Fast load transient PFM Mode light load VOUT_NOM PWM Mode medium/heavy load PWM Mode medium/heavy load -1% COMP_LOW threshold Figure 17. Dynamic Voltage Positioning Soft Start The two converters have an internal soft start circuit that limits the inrush current during start-up. During soft start, the output voltage ramp up is controlled as shown in Figure 18. EN 95% 5% VOUT tStart tRAMP Figure 18. Soft Start 14 Submit Documentation Feedback Copyright © 2008, Texas Instruments Incorporated Product Folder Link(s) :TPS65058 TPS65058 www.ti.com ........................................................................................................................................................................................................ SLVS851 – MAY 2008 100% Duty Cycle Low Dropout Operation The converters offer a low input to output voltage difference while still maintaining operation with the use of the 100% duty cycle mode. In this mode the P-channel switch is constantly turned on. This is particularly useful in battery-powered applications to achieve longest operation time by taking full advantage of the whole battery voltage range, i.e. The minimum input voltage to maintain regulation depends on the load current and output voltage and can be calculated as: VImin = VOUTmax + IOUTmax × (RDS(on)max + RL) with: IOUTmax = maximum output current plus inductor ripple current RDS(on)max = maximum P-channel switch rDS(on) RL = DC resistance of the inductor VOUTmax = nominal output voltage plus maximum output voltage tolerance With decreasing load current, the device automatically switches into pulse skipping operation in which the power stage operates intermittently based on load demand. By running cycles periodically the switching losses are minimized and the device runs with a minimum quiescent current maintaining high efficiency. In power save mode, the converter only operates when the output voltage trips below its nominal output voltage. It ramps up the output voltage with several pulses and goes again into power save mode once the output voltage exceeds the nominal output voltage. Undervoltage Lockout The undervoltage lockout circuit prevents the device from malfunctioning by disabling the converter at low input voltages and from excessive discharge of the battery. The undervoltage lockout threshold is typically 1.8 V, max 2 V. MODE SELECTION The MODE pin allows mode selection between forced PWM Mode and power Save Mode for both converters. Connecting this pin to GND enables the automatic PWM and power save mode operation. The converters operate in fixed frequency PWM mode at moderate to heavy loads and in the PFM mode during light loads, maintaining high efficiency over a wide load current range. Pulling the MODE pin high forces both converters to operate constantly in the PWM mode even at light load currents. The advantage is the converters operate with a fixed frequency that allows simple filtering of the switching frequency for noise sensitive applications. In this mode, the efficiency is lower compared to the power save mode during light loads. For additional flexibility it is possible to switch from power save mode to forced PWM mode during operation. This allows efficient power management by adjusting the operation of the converter to the specific system requirements. ENABLE The device has a separate enable pin for each dcdc converter and for each LDO to start up each converter independently. If EN_DCDC1, EN_DCDC2, EN_LDO1, EN_LDO2, EN_LDO3 are set to high, the corresponding converter starts up with soft start as previously described. Pulling the enable pin low forces the device into shutdown, with a shutdown quiescent current as defined in the electrical characteristics. In this mode, the P and N-Channel MOSFETs are turned-off, the and the entire internal control circuitry is switched-off. If disabled, the outputs of the LDOs are pulled low by internal 300Ω resistors, actively discharging the output capacitor. For proper operation, the enable pins must be terminated and must not be left unconnected. OUTPUT VOLTAGE SELECTION The output voltage of the DCDC Converter 2 can be selected by a logic level on pin DEF_DCDC2. The output voltage can be changed dynamically during operation. The slew rate of the change of output voltage is controlled on DCDC2 to be 9.6mV/µs. The output voltages on the LDOs can also be changed dynamically between two voltages by changing the logic level on pin DEF_LDO. Submit Documentation Feedback Copyright © 2008, Texas Instruments Incorporated Product Folder Link(s) :TPS65058 15 TPS65058 SLVS851 – MAY 2008 ........................................................................................................................................................................................................ www.ti.com The output voltage options are: Table 1. Output Voltage Selection DEF_LDO 1 0 LDO1 3.3 V 3.3 V LDO2 1.8 V 1.2 V LDO3 1.8 V 1.3 V DEF_DCDC2 1 0 DCDC2 1.8 V 1.2 V RESET GENERATION AND OUTPUT MONITORING The TPS65058 contains a monitor circuitry that monitors the outputs of the DCDC converters and applies a reset pulse to the RESET pin. As soon as the supply voltage on the VCC pin is above the undervoltage lockout threshold, the RESET pin is pulled low. After the enabling of both DCDC converters, the output voltages are monitored. When both outputs are within 95% of the desired output voltage, the reset timer is started and after a delay of 100ms the Reset output is switched to high impedance. If one of the output voltages is outside of the regulation band (90% of the desired value) the RESET pin remains to be pulled to ground. After both outputs are back in regulation, the 100ms timer is started, and after 100ms the RESET output is again switched to high impedance. Undervoltage lockout Vcc Enable DCDC 1 Enable DCDC 2 90 % Vout DCDC 1 95 % 95 % Vout DCDC 2 100 ms 100 ms RESET Reset inactive after 100 msif DCDC 1 AND DCDC 2 in regulation Reset inactive if DCDC 1 XOR DCDC 2 disabled Reset active if DCDC1 AND DCDC 2 Enabled but DCDC 1 OR DCDC 2 out of regulation Reset active if DCDC1 AND DCDC 2 disabled Figure 19. RESET Pulse Circuit SHORT-CIRCUIT PROTECTION All outputs are short circuit protected with a maximum output current as defined in the Electrical Characteristics. THERMAL SHUTDOWN As soon as the junction temperature, TJ, exceeds typically 150°C for the DCDC converters, the device goes into thermal shutdown. In this mode, the P and N-Channel MOSFETs are turned-off. The device continues its operation when the junction temperature falls below the thermal shutdown hysteresis again. A thermal shutdown for one of the DCDC converters will disable both converters simultaneously. 16 Submit Documentation Feedback Copyright © 2008, Texas Instruments Incorporated Product Folder Link(s) :TPS65058 TPS65058 www.ti.com ........................................................................................................................................................................................................ SLVS851 – MAY 2008 The thermal shutdown temperature for the LDOs are set to typically 140°C. Therefore, a LDO which is used to power an external voltage will never heat up the chip to a temperature high enough to turn off the DCDC converters. If one LDO exceeds the thermal shutdown temperature, all LDOs will turn off simultaneously. Low Dropout Voltage Regulators The low dropout voltage regulators are designed to operate with low value ceramic input and output capacitors. They operate with input voltages down to 1.5V. The LDOs offer a maximum dropout voltage of 280mV at rated output current. Each LDO supports a current limit feature. The LDOs are enabled by the EN_LDO1, ENLDO2, and EN_LDO3 pin. The output voltage of LDO1, LDO2 and LDO3 can be selected by the DEF_LDO pin according to Table 1. For noise and stability reasons, X5R or X7R type ceramic capacitors are recommended to limit degeneration of °C over temperature and Vout. OUTPUT FILTER DESIGN (INDUCTOR AND OUTPUT CAPACITOR) Inductor Selection The two converters operate typically with 2.2µH output inductor. Larger or smaller inductor values can be used to optimize the performance of the device for specific operation conditions. For output voltages higher than 2.8V, an inductor value of 3.3µH minimum should be selected, otherwise the inductor current will ramp down too fast causing imprecise internal current measurement, and therefore, increased output voltage ripple under some operating conditions in PFM mode. The selected inductor has to be rated for its DC resistance and saturation current. The DC resistance of the inductance will directly influence the efficiency of the converter. Therefore, an inductor with lowest DC resistance should be selected for highest efficiency. Equation 4 calculates the maximum inductor current under static load conditions. The saturation current of the inductor should be rated higher than the maximum inductor current as calculated with Equation 4. This is recommended because during heavy load transient the inductor current will rise above the calculated value. 1 - Vout DI Vin DIL = Vout x ILmax = Iout max + L Lxf 2 (4) with: f = Switching Frequency (2.25 MHz typical) L = Inductor Value ΔIL = Peak to Peak inductor ripple current ILmax = Maximum Inductor current The highest inductor current will occur at maximum Vin. Open core inductors have a soft saturation characteristic, and usually handle higher inductor currents versus a comparable shielded inductor. A more conservative approach is to select the inductor current rating just for the maximum switch current of the corresponding converter. A consideration to be considered is that the core material from inductor to inductor differs, and has an impact on the efficiency, especially at high switching frequencies. See Table 2 and the typical applications for possible inductors. Table 2. Tested Inductors INDUCTOR TYPE INDUCTOR VALUE SUPPLIER LPS3010 2.2 µH Coilcraft LPS3015 3.3 µH Coilcraft LPS4012 2.2 µH Coilcraft VLF4012 2.2 µH TDK Submit Documentation Feedback Copyright © 2008, Texas Instruments Incorporated Product Folder Link(s) :TPS65058 17 TPS65058 SLVS851 – MAY 2008 ........................................................................................................................................................................................................ www.ti.com Output Capacitor Selection The advanced Fast Response voltage mode control scheme of the two converters allow the use of small ceramic capacitors with a typical value of 22µF, without having large output voltage under and overshoots during heavy load transients. Ceramic capacitors having low ESR values result in lowest output voltage ripple and are recommended. SeeTable 3 for recommended components. If ceramic output capacitors are used, the capacitor RMS ripple current rating will always meet the application requirements. Just for completeness the RMS ripple current is calculated as: 1 * Vout Vin 1 I RMSCout + Vout L ƒ 2 Ǹ3 (5) At nominal load, current the inductive converters operate in PWM mode. The overall output voltage ripple is the sum of the voltage spike, caused by the output capacitor ESR plus the voltage ripple, caused by charging and discharging the output capacitor: 1 * Vout Vin 1 DVout + Vout ) ESR 8 Cout ƒ L ƒ (6) ǒ Ǔ Where the highest output voltage ripple occurs at the highest input voltage Vin. At light load currents, the converters operate in Power Save Mode and the output voltage ripple is dependent on the output capacitor value. The output voltage ripple is set by the internal comparator delay and the external capacitor. The typical output voltage ripple is less than 1% of the nominal output voltage. Input Capacitor Selection Because of the nature of the buck converter having a pulsating input current, a low ESR input capacitor is required for best input voltage filtering, and minimizing the interference with other circuits caused by high input voltage spikes. The converters need a ceramic input capacitor of 10µF. The input capacitor can be increased without any limit for better input voltage filtering. Table 3. Possible Capacitors 18 22 µF 0805 TDK C2012X5R0J226MT Ceramic 22 µF 0805 Taiyo Yuden JMK212BJ226MG Ceramic 10 µF 0805 Taiyo Yuden JMK212BJ106M Ceramic 10uF 0805 TDK C2012X5R0J106M Ceramic Submit Documentation Feedback Copyright © 2008, Texas Instruments Incorporated Product Folder Link(s) :TPS65058 TPS65058 www.ti.com ........................................................................................................................................................................................................ SLVS851 – MAY 2008 APPLICATION INFORMATION TYPICAL APPLICATION CIRCUIT 10 W VIN VINDCDC1/2 VCC 22 mF 1 mF ENABLE VIN 2.2 mH EN_DCDC1 DCDC1 (I/O) STEP-DOWN CONVERTER 600 mA MODE L1 3.3 V FB_DCDC1 10 mF PGND1 PGOOD1 2.2 mF DCDC2 (core) ENABLE Voltage Switching (1/0) EN_DCDC2 DEF_DCDC2 1.8V / 1.2V L2 FB_DCDC2 STEP-DOWN CONVERTER 1A 10 mF PGND2 PGOOD2 VIN 2.2 mF ENABLE Voltage Switching (1/0) VIN 2.2 mF ENABLE ENABLE VLDO1 VIN_LDO1 3.3 V / 3.3 V VLDO1 4.7 mF EN_LDO1 400 mA LDO DEF_LDO VIN_LDO2/3 VLDO2 EN_LDO2 VLDO2 1.8 V / 1.2 V 2.2 mF 200 mA LDO EN_LDO3 VLDO3 VLDO3 1.8 V / 1.3 V 2.2 mF 200 mA LDO I/O Voltage RESET R19 RESET AGND Submit Documentation Feedback Copyright © 2008, Texas Instruments Incorporated Product Folder Link(s) :TPS65058 19 PACKAGE OPTION ADDENDUM www.ti.com 9-Jun-2008 PACKAGING INFORMATION Orderable Device Status (1) Package Type Package Drawing Pins Package Eco Plan (2) Qty TPS65058RGER ACTIVE VQFN RGE 24 3000 Green (RoHS & no Sb/Br) CU NIPDAU Level-2-260C-1 YEAR TPS65058RGET ACTIVE VQFN RGE 24 250 CU NIPDAU Level-2-260C-1 YEAR Green (RoHS & no Sb/Br) Lead/Ball Finish MSL Peak Temp (3) (1) The marketing status values are defined as follows: ACTIVE: Product device recommended for new designs. LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect. NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design. PREVIEW: Device has been announced but is not in production. Samples may or may not be available. OBSOLETE: TI has discontinued the production of the device. (2) Eco Plan - The planned eco-friendly classification: Pb-Free (RoHS), Pb-Free (RoHS Exempt), or Green (RoHS & no Sb/Br) - please check http://www.ti.com/productcontent for the latest availability information and additional product content details. TBD: The Pb-Free/Green conversion plan has not been defined. Pb-Free (RoHS): TI's terms "Lead-Free" or "Pb-Free" mean semiconductor products that are compatible with the current RoHS requirements for all 6 substances, including the requirement that lead not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, TI Pb-Free products are suitable for use in specified lead-free processes. Pb-Free (RoHS Exempt): This component has a RoHS exemption for either 1) lead-based flip-chip solder bumps used between the die and package, or 2) lead-based die adhesive used between the die and leadframe. The component is otherwise considered Pb-Free (RoHS compatible) as defined above. Green (RoHS & no Sb/Br): TI defines "Green" to mean Pb-Free (RoHS compatible), and free of Bromine (Br) and Antimony (Sb) based flame retardants (Br or Sb do not exceed 0.1% by weight in homogeneous material) (3) MSL, Peak Temp. -- The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder temperature. Important Information and Disclaimer:The information provided on this page represents TI's knowledge and belief as of the date that it is provided. TI bases its knowledge and belief on information provided by third parties, and makes no representation or warranty as to the accuracy of such information. Efforts are underway to better integrate information from third parties. TI has taken and continues to take reasonable steps to provide representative and accurate information but may not have conducted destructive testing or chemical analysis on incoming materials and chemicals. TI and TI suppliers consider certain information to be proprietary, and thus CAS numbers and other limited information may not be available for release. In no event shall TI's liability arising out of such information exceed the total purchase price of the TI part(s) at issue in this document sold by TI to Customer on an annual basis. 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