CIRRUS MP240_09

MP240
MP240
P r o dMP240
u c t IInnnnoovvaa t i o n FFr roomm
Power Operational Amplifier
FEATURES
GENERAL DESCRIPTION
The MP240 operational amplifier is a surface mount
constructed component that provides a cost effective
solution in many industrial applications. The MP240
offers outstanding performance that rivals much more
expensive hybrid components yet has a footprint of
only 4.7 sq in. The MP240 has many optional features such as four-wire current limit sensing, a shutdown control and external compensation. In addition,
the class A/B output stage biasing can be turned off
for lower quiescent current with class C operation in
applications where crossover distortion is less important such as when driving motors, for example. A boost
voltage feature biases the output stage for close linear
swings to the supply rail for extra efficient operation.
The MP240 is built on a thermally conductive but electrically insulating substrate that can be mounted to a
heat sink.
♦ LOW COST
♦ HIGH VOLTAGE - 200 VOLTS
♦ HIGH OUTPUT CURRENT - 20 AMPS
♦ 170 WATT DISSIPATION CAPABILITY
APPLICATIONS
♦ MOTOR DRIVE
♦ MAGNETIC DEFLECTION
♦ PROGRAMMABLE POWER SUPPLIES
♦ INDUSTRIAL AUDIO AMPLIFIER
EQUIVALENT CIRCUIT DIAGRAM
HSD
8
LSD
7
+Vb
1
+Vs
R1
C1
GND
R2
Q1A
2
R3
Q1B
C2
Q17
Cc2
R13
3.9k
Q6
R7
Q11A
Q11B
R8
R10
R9
R16
35 -ILIM
Q21
Q19
OUT
24-26
OUT
R11
D2
5
R12
30-32
Q13
Q13A
R12A
Q14
GND 40
C3
R13
Q15
R14
21-23
-Vs
27-29
-Vs
-Vb 38
http://www.cirrus.com
OUT
36 +ILIM
Q18
Q20
R15
Q10
15-17
OUT
9-11
D3
R6
MP240U
Q3A
R4
Q5
Iq
Q3
R5A
Cc1 6
+IN 41
R5
Q4
4
-IN 42
+Vs
18-20
Q16
Q2
D1
12-14
LEVEL
SHIFT
Copyright © Cirrus Logic, Inc. 2009
(All Rights Reserved)
SEP 2009
1
APEX − MP240UREVH
MP240
P r o d u c t I n n o v a t i o nF r o m
CHARACTERISTICS AND SPECIFICATIONS
ABSOLUTE MAXIMUM RATINGS
Parameter
Symbol
Min
Max
Units
SUPPLY VOLTAGE, +VS to -VS
200
V
OUTPUT CURRENT, +VB
(Note 6)
+VS + 15V
V
POWER DISSIPATION, -VB
(Note 6)
-VS - 15V
V
OUTPUT CURRENT, peak, within SOA
25
A
POWER DISSIPATION, internal, DC
170
W
INPUT VOLTAGE
+VB to -VB
V
225
°C
150
°C
TEMPERATURE, pin solder, 10s
TEMPERATURE, junction
(Note 2)
TEMPERATURE RANGE, storage
−40
105
°C
OPERATING TEMPERATURE, case
−40
85
°C
SPECIFICATIONS
Parameter
Test Conditions
Min
Typ
Max
Units
INPUT
OFFSET VOLTAGE
OFFSET VOLTAGE vs. temperature
Full temperature range
1
5
mV
20
50
µV/°C
20
µV/V
OFFSET VOLTAGE vs. supply
BIAS CURRENT, initial
100
pA
BIAS CURRENT vs. supply
(Note 3)
0.1
pA/V
OFFSET CURRENT, initial
50
pA
INPUT IMPEDANCE, DC
INPUT CAPACITANCE
100
GΩ
4
pF
COMMON MODE VOLTAGE RANGE
+VB - 15
V
COMMON MODE VOLTAGE RANGE
-VB + 15
V
COMMON MODE REJECTION, DC
92
dB
DIFFERENTIAL INPUT VOLTAGE
±25
5
V
NOISE
1MHz bandwidth, 1kΩ RS
µV RMS
SHUTDOWN, active
HSD - LSD
4.5
5
5.5
V
SHUTDOWN, inactive
HSD - LSD
-0.5
0
0.25
V
GAIN
OPEN LOOP @ 15Hz
RL= 1KΩ, CC = 100pF
GAIN BANDWIDTH PRODUCT @ 1MHz
CC = 100pF
PHASE MARGIN
Full temperature range
96
dB
1.8
60
MHz
°
OUTPUT
VOLTAGE SWING
IO = 20A
+VS - 10
+VS - 7
V
VOLTAGE SWING
IO = -20A
-VS + 10
-VS + 8
V
VOLTAGE SWING
IO = 20A, +VB = +VS +10V
+VS - 3.0
+VS - 2.0
V
VOLTAGE SWING
IO = -20A, -VB = -VS -10V
-VS + 6.0
-VS + 5.0
V
CURRENT, continuous, DC
SLEW RATE, A V = -10
2
20
CC = 100pF
12
A
14
V/µS
MP240U
MP240
P r o d u c t I n n o v a t i o nF r o m
Parameter
Test Conditions
Min
SETTLING TIME, to 0.1%
A V = -1, 10V Step, CC = 680pF
RESISTANCE, open loop
DC, 10A Load
Typ
Max
Units
5
µS
0.2
Ω
POWER SUPPLY
VOLTAGE
±15
CURRENT, quiescent, total
±75
±100
V
16.5
25
mA
CURRENT, shutdown or class C quiescent
8.5
mA
CURRENT, boost supply
8.5
mA
THERMAL
RESISTANCE, AC, junction to case (Note 5) Full temp range, f ≥ 60Hz
0.58
°C/W
RESISTANCE, DC, junction to case
Full temp range, f < 60Hz
0.73
°C/W
RESISTANCE, junction to air
Full temp range
14
°C/W
85
°C
TEMPERATURE RANGE, case
-40
NOTES:
1. Unless otherwise noted: TC = 25°C, compensation CC = 680pF, DC input specifications are ± value
given, power supply voltage is typical rating. Amplifier operated without boost feature.
2. Long term operation at the maximum junction temperature will result in reduced product life. Derate
internal power dissipation to achieve high MTBF.
3. Doubles for every 10°C of case temperature increase.
4. +VS and -VS denote the + and - output stage supply voltages. +VB and -VB denote the + and - input
stage supply voltages (boost voltages).
5. Rating applies if the output current alternates between both output transistors at a rate faster than
60Hz.
6. Power supply voltages +VB and -VB must not be less than +VS and -VS respectively.
EXTERNAL CONNECTIONS
C1
+
C2
Cc
1
2
3
+Vb GND NC
-IN
42
+IN GND NC
41
40
39
-Vb
38
4
5
Rs1
6
7
8
9
10
Rs2
12
13
14
15
16
17
18
19
20
Iq Cc1 LSD HSD OUT OUT OUT +Vs +Vs +Vs OUT OUT OUT +Vs +Vs +Vs
VIEW FROM COMPONENT SIDE
NC +ILIM -ILIM NC NC OUT OUT OUT -Vs -Vs -Vs OUT OUT OUT -Vs -Vs -Vs
34
32
30
27
25
23
33
29
26
22
21
35
31
28
24
37 36
Cc2
RLIM
LOAD &
FEEDBACK
Rs4
Rs3
C3
+
C4
NOTES:
CC IS NPO (COG) RATED FOR FULL SUPPLY VOLTAGE +VS TO -VS.
BOTH PINS 2 AND 40 REQUIRED CONNECTED TO SIGNAL GROUND.
C2 AND C3 ELECTROLYTIC ≤10µF PER AMP OUTPUT CURRENT.
C1 AND C4 HIGH QUALITY CERAMIC ≤0.1µF.
SEE TEXT FOR SELECTION OF VALUES FOR Rs1 - Rs4.
MP240U
11
PHASE COMPENSATION
CC
GAIN W/O BOOST GAIN W/BOOST TYP. SLEW RATE
≤1
≤3
3V/µS
680pF
≤3
≤6
6V/µS
330pF
100pF
≤10
≤13
42-Pin DIP
Package Style FC
14V/µS
3
MP240
P r o d u c t I n n o v a t i o nF r o m
POWER DERATING
150
100
CC = 100pF
150
120
CC = 330pF
150
RL = 2.5Ω
180
50K 100K
1M
FREQUENCY, F(Hz)
SMALL SIGNAL RESPONSE W/O BOOST
90
80
70
-50 -25
0
25
50
75 100
CASE TEMPERATURE. TC (°C)
1
0.1
PO = 1W
PO = 10W
0.01
0.001
30
PO = 150W
10K 30K
1K
100
FREQUENCY, F (Hz)
OUTPUT VOLTAGE, VO(VP-P)
OPEN LOOP GAIN, A (dB)
7
HARMONIC DISTORTION
AV = 16
CC = 100pF
+/-VS = 60V
RL = 8Ω
160
120
TC
80
=
TC =
C
0°
-4
TC
5°C
=8
25°C
40
0
40
80
120 160
200
TOTAL SUPPLY VOLTAGE, VS (V)
OUTPUT VOLTAGE SWING
6
5
OM
FR
OST
BO
W/O
TC = 25ºC
50mS PULSE
4
3
ST
2
TH
WI
1
0
OM +V S
OST FR
W/O BO
0
O
BO
M
RO
-V S
-V S
F
WITH
OM
T FR
+V S
S
BOO
5
10
15
OUTPUT CURRENT, IO (A)
20
NORMALIZED QUIESCENT CURRENT, IQ (%)
100
200
20
1K
1M 2M
OUTPUT CURRENT FROM +VS OR -VS (A)
110
1K 10K 100K
100
FREQUENCY, F(Hz)
QUIESCENT CURRENT VS SUPPLY
NORMALIZED QUIESCENT CURRENT, IQ (%)
CURRENT LIMIT
120
10
0
10
1M 2M
0pF
1K 10K 100K
FREQUENCY
3
= 10
100
2
20
0pF
130
3
1
40
= 33
2
20
60
100
0pF
1
80
= 68
40
1 - CC = 100pF
2 - CC = 330pF
3 - CC = 680pF
RL = 2.5Ω
100
2M
POWER RESPONSE
CC
60
200
120
VOLTAGE DROP FROM SUPPLY, (V)
80
2M
CC
1 - CC = 100pF
2 - CC = 330pF
3 - CC = 680pF
RL = 2.5Ω
100
RL = 2.5Ω
180
50K 100K
1M
FREQUENCY, F(Hz)
CC
OPEN LOOP GAIN, A (dB)
CC = 330pF
120
CC = 100pF
0
-40 -20 0
20 40 60 80 100
CASE TEMPERATURE. TC (°C)
0
10
NORMALIZED CURRENT LIMIT, (%)
CC = 680pF
50
120
DISTORTION, THD (%)
90
CC = 680pF
SMALL SIGNAL RESPONSE W/ BOOST
4
PHASE RESPONSE W/O BOOST
PHASE RESPONSE W/BOOST
90
PHASE Ф, (°)
200
PHASE Ф, (°)
INTERNAL POWER DISSIPATION, P (W)
TYPICAL PERFORMANCE GRAPHS
10K
100K
FREQUENCY, F(Hz)
500K
QUIESCENT CURRENT vs TEMPERATURE
130
120
110
100
90
-40 -20 0
20 40 60 80 100
CASE TEMPERATURE, (°C)
30
SAFE OPERATING AREA
10
5
10mS, TC = 25°C
100mS, TC = 25°C
DC, TC = 25°C
1
DC, TC = 85°C
0.5
1
10
100 200
SUPPLY TO OUTPUT DIFFERENTIAL, VS - VO (V)
MP240U
MP240
P r o d u c t I n n o v a t i o nF r o m
TYPICAL APPLICATION
+Vs
MOTOR POSITION CONTROL
12-14
18-20
The MOSFET output stage of the MP240 provides supeRs1
1
rior SOA performance compared to bipolar output stages
+Vs
Rs2
2
+Vb
42
Rs3
35
where secondary breakdown is a concern. The extended
GND
Rs4
-ILIM
*
SOA is ideal in motor drive applications where the back DAC OUTPUT
36
OUT
EMF of the motor may impose simultaneously both high POSITION
Cc1
+ILIM
RLIM
COMMAND
Cc2
voltage and high current across the output stage transis41
GND 4 6
MOTOR
*OUT
-Vb
DRIVE
tors. In the figure above a mechanical to electrical feed40
9-11
-Vs
38
15-17
back position converter allows the MP240 to drive the moCc
24-26
21-23
tor in either direction to a set point determined by the DAC
30-32
27-29
voltage.
-Vs
POSITION
The MP400 is ideally suited to driving both piezo actuaFEEDBACK
tion and deflection applications off of a single low voltage
supply. The circuit above boosts a system 24V buss to 350V to drive an ink jet print head. The MP400s high speed
deflection amplifier is biased for single supply operation by external resistors R2 – R6, so that a 0 to 5V DAC can
be used as the input to the amplifier to drive the print head from 0 to >300V.
GENERAL
Please read Application Note 1 “General Operating Considerations” which covers stability, power supplies, heat
sinking, mounting, current limit, SOA interpretation, and specification interpretation. Visit www.cirrus.com for design
tools that help automate tasks such as calculations for stability, internal power dissipation, current limit, heat sink
selection, Apex Precision Power’s complete Application Notes library, Technical Seminar Workbook and Evaluation
Kits.
GROUND PINS
The MP240 has two ground pins (pins 2, 40). These pins provide a return for the internal capacitive bypassing of
the small signal stages of the MP240. The two ground pins are not connected together on the substrate. Both of
these pins are required to be connected to the system signal ground.
BALANCING RESISTOR SELECTION (RS1-RS4)
The MP240 uses parallel sets of output transistors. To ensure that the load current is evenly shared among the
transistors external balancing resistors RS1-RS4 are required. To calculate the required value for each of the resistors
use: R = 4.5/I2 ,where I is the maximum expected output current. For example, with a maximum output current of
10A each balancing resistor should be 0.045 ohms. Each resistor dissipates 1.125W at the maximum current. Use
a non-inductive 2W rated resistor. A ready source for such resistors is the IRC resistor series LR available from
Mouser Electronics.
SAFE OPERATING AREA
The MOSFET output stage of the MP240 is not limited by second breakdown considerations as in bipolar output
stages. Only thermal considerations and current handling capabilities limit the SOA (see Safe Operating Area graph
on previous page). The output stage is protected against transient flyback by the parasitic diodes of the output stage
MOSFET structure. However, for protection against sustained high energy flyback external fast-recovery diodes
must be used.
COMPENSATION
The external compensation capacitor CC is connected to pins 4 and 6. Unity gain stability can be achieved with
CC = 680pF for a minimum phase margin of 60 degrees. At higher gains more phase shift can usually be tolerated
and CC can be reduced resulting in higher bandwidth and slew rate. Use the typical operating curves as a guide to
select CC. A 200V NPO (COG) type capacitor is required. Boost operation requires more compensation or higher
gains than with normal operation due to the increased capacitance of the output transistors when the output signal
swings close to the supply rails.
MP240U
5
MP240
P r o d u c t I n n o v a t i o nF r o m
OVERVOLTAGE PROTECTION
Although the MP240 can withstand differential input voltages up to ±25V, in
some applications additional external protection may be needed. 1N4148
signal diodes connected anti-parallel across the input pins is usually sufficient. In more demanding applications where bias current is important
diode connected JFETs such as 2N4416 will be required. See Q1 and Q2
in Figure 1. In either case the differential input voltage will be clamped to
±0.7V. This is sufficient overdrive to produce the maximum power bandwidth. Some applications will also need over-voltage protection devices
connected to the power supply rails. Unidirectional zener diode transient
suppressors are recommended. The zeners clamp transients to voltages
within the power supply rating and also clamp power supply reversals to
ground. Whether the zeners are used or not the system power supply
should be evaluated for transient performance including power-on overshoot and power-off polarity reversals as well as line regulation. See Z1
and Z2 in Figure 1.
+Vs
-IN
42
Q1
Q2
1
+Vs
+Vb
2
GND
OUT
GND
41
+IN
Z1
-Vb
-Vs
38
-Vs
40
Z2
FIGURE 1: OVERVOLTAGE PROTECTION
POWER SUPPLY BYPASSING
Bypass capacitors to power supply terminals +VS and -VS must be connected physically close to the pins to prevent local parasitic oscillation in the output stage of the MP240. Use electrolytic capacitors at least 10µF per output amp required. Bypass
the electrolytic capacitors with high quality ceramic capacitors 0.1µF or greater. In most applications power supply terminals
+VB and -VB will be connected to +VS and -VS respectively. Although +VB and -VB are bypassed internally it is recommended to
bypass +VB and -VB with 0.1µF externally. Additionally ground pins 2 and 40 must be connected to the system signal ground.
RF
CURRENT LIMIT
The two current limit sense lines are to be connected directly across the current limit sense resistor. For the current limit to work correctly pin 36 must
be connected to the amplifier output side and pin 35 connected to the load
side of the current limit resistor RLIM as shown in Figure 2. This connection
will bypass any parasitic resistances RP, formed by socket and solder joints
as well as internal amplifier losses. The current limiting resistor may not be
placed anywhere in the output circuit except where shown in Figure 2. The
value of the current limit resistor can be calculated as follows: RLIM = .65/ILIMIT
RIN
42
IN
35
-ILIM 36
+ILIM OUT
41
RP
RLIM
RL
FIGURE 2: 4 WIRE CURRENT LIMIT
BOOST OPERATION
With the boost feature the small signal stages of the amplifier are operated at a higher supply voltages than the amplifier’s
high current output stage. +VB (pin 1) and -VB (pin 38) are connected to the small signal stages. An additional 10V on the +VB
and -VB pin is sufficient to allow the small signal stages to drive the output stage into the triode region and improve the output
voltage swing for extra efficient operation when required. When the boost feature is not needed +VS and -VS are connected
to +VB and -VB respectively. +VB and -VB must not be operated at supply voltages less than +VS and -VS respectively.
SHUTDOWN
The output stage is turned off by applying a 5V level to HSD (pin 8) relative to LSD (pin 7). This is a non-latching circuit. As
long as HSD remains high relative to LSD the output stage will be turned off. LSD will normally be tied to signal ground but
LSD may float from -VB to +VB - 15V. Shutdown can be used to lower quiescent current for standby operation or as part of a
load protection circuit.
BIAS CLASS OPTION
Normally pin 5 (Iq) is left open. But when pin 5 is connected to pin 6 (Cc1) the quiescent current in the output stage is disabled.
This results in lower quiescent power, but also class C operation of the output stage and the resulting crossover distortion.
In many applications, such as driving motors, the distortion may be unimportant and lower standby power dissipation is an
advantage.
6
MP240U
P r o d u c t I n n o v a t i o nF r o m
MP240
CONTACTING CIRRUS LOGIC SUPPORT
For all Apex Precision Power product questions and inquiries, call toll free 800-546-2739 in North America.
For inquiries via email, please contact [email protected]
International customers can also request support by contacting their local Cirrus Logic Sales Representative.
To find the one nearest to you, go to www.cirrus.com
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to change without notice and is provided "AS IS" without warranty of any kind (express or implied). Customers are advised to obtain the latest version of relevant
information to verify, before placing orders, that information being relied on is current and complete. All products are sold subject to the terms and conditions of sale
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MP240U
7