PB58PB58 • PB58A • PB58A PPB58, r o d u c t IPB58A Innnnoovvaa t i o n FFr roomm Power Booster Amplifier FEATURES • WIDE SUPPLY RANGE — ±15V to ±150V • HIGH OUTPUT CURRENT — 1.5A Continuous (PB58) 2.0A Continuous (PB58A) • VOLTAGE AND CURRENT GAIN • HIGH SLEW — 50V/µs Minimum (PB58) 75V/µs Minimum (PB58A) • PROGRAMMABLE OUTPUT CURRENT LIMIT • HIGH POWER BANDWIDTH — 320 kHz Minimum • LOW QUIESCENT CURRENT — 12mA Typical • EVALUATION KIT — See EK50 8-pin TO-3 PACKAGE STYLE CE EQUIVALENT SCHEMATIC 3 +Vs APPLICATIONS • HIGH VOLTAGE INSTRUMENTATION • Electrostatic TRANSDUCERS & DEFLECTION • Programmable Power Supplies Up to 280V p-p Q1 Q3 DESCRIPTION The PB58 is a high voltage, high current amplifier designed to provide voltage and current gain for a small signal, general purpose op amp. Including the power booster within the feedback loop of the driver amplifier results in a composite amplifier with the accuracy of the driver and the extended output voltage range and current capability of the booster. The PB58 can also be used without a driver in some applications, requiring only an external current limit resistor to function properly. The output stage utilizes complementary MOSFETs, providing symmetrical output impedance and eliminating second breakdown limitations imposed by Bipolar Transistors. Internal feedback and gainset resistors are provided for a pin-strapable gain of 3. Additional gain can be achieved with a single external resistor. Compensation is not required for most driver/gain configurations, but can be accomplished with a single external capacitor. Enormous flexibility is provided through the choice of driver amplifier, current limit, supply voltage, voltage gain, and compensation. This hybrid circuit utilizes a beryllia (BeO) substrate, thick film resistors, ceramic capacitors and semiconductor chips to maximize reliability, minimize size and give top performance. Ultrasonically bonded aluminum wires provide reliable interconnections at all operating temperatures. The 8-pin TO-3 package is electrically isolated and hermetically sealed using one-shot resistance welding. The use of compressible isolation washers voids the warranty. TYPICAL APPLICATION VIN RI +15V OP AMP –15V PB58U http://www.cirrus.com Figure 1. Inverting composite amplifier. CF RF +Vs IN 4 Q4 PB58 –Vs Q5 Q6 GAIN 6.2K 7 OUT 1 50K 3.1K 2 CL Q7 COM 5 Q11 COMP 8 Q8 Q9 Q10 –Vs 6 EXTERNAL CONNECTIONS +VS CL 3 RCL 2 1 IN 4 OUT TOP VIEW COM RCL 5 –VS 6 IN COM Q2 8 7 GAIN COMP CC RG OUT CC RL RG Copyright © Cirrus Logic, Inc. 2009 (All Rights Reserved) MAY 20091 APEX − PB58UREVK PB58 • PB58A ABSOLUTE MAXIMUM RATINGS P r o d u c t I n n o v a t i o nF r o m SUPPLY VOLTAGE, +VS to –VS OUTPUT CURRENT, within SOA POWER DISSIPATION, internal at TC = 25°C1 INPUT VOLTAGE, referred to COM TEMPERATURE, pin solder—10 sec max TEMPERATURE, junction1 TEMPERATURE, storage OPERATING TEMPERATURE RANGE, case 300V 2.0A 83W ±15V 300°C 175°C –65 to +150°C –55 to +125°C SPECIFICATIONS PARAMETER TEST CONDITIONS2 INPUT OFFSET VOLTAGE, initial OFFSET VOLTAGE, vs. temperature INPUT IMPEDANCE, DC INPUT CAPACITANCE CLOSED LOOP GAIN RANGE GAIN ACCURACY, internal Rg, Rf GAIN ACCURACY, external Rf PHASE SHIFT OUTPUT VOLTAGE SWING VOLTAGE SWING VOLTAGE SWING CURRENT, continuous SLEW RATE CAPACITIVE LOAD SETTLING TIME to .1% POWER BANDWIDTH SMALL SIGNAL BANDWIDTH SMALL SIGNAL BANDWIDTH POWER SUPPLY VOLTAGE, ±VS4 CURRENT, quiescent THERMAL RESISTANCE, AC junction to case5 RESISTANCE, DC junction to case RESISTANCE, junction to air TEMPERATURE RANGE, case MIN Full temperature range3 25 3 AV = 3 AV = 10 f = 10kHz, AVCL = 10, CC = 22pF f = 200kHz, AVCL = 10, CC = 22pF Io = 1.5A (PB58), 2A (PB58A) Io = 1A Io = .1A Full temperature range Full temperature range RL = 100Ω, 2V step VC = 100 Vpp CC = 22pF, AV = 25, Vcc = ±100 CC = 22pF, AV = 3, Vcc = ±30 Full temperature range VS = ±15 VS = ±60 VS = ±150 Full temp. range, f > 60Hz Full temp. range, f < 60Hz Full temperature range Meets full range specifications VS–11 VS–10 VS–8 1.5 50 160 ±156 –25 PB58 TYP MAX MIN ±.75 –4.5 50 3 10 ±10 ±15 10 60 ±1.75 –7 * 25 * ±15 ±25 VS –8 VS –7 VS –5 100 2200 2 320 100 1 PB58A TYP MAX UNITS * ±1.0 * * * * * * * * * * * * VS–15 VS–11 * * * * 2.0 75 * * * 240 * * * V mV/°C kΩ pF V/V % % ° ° V V V A V/µs pF µs kHz kHz MHz ±60 11 12 14 ±150 * 18 * * * * * * V mA mA mA 1.2 1.6 30 25 1.3 1.8 85 * * * * * * * * °C/W °C/W °C/W °C NOTES: * The specification of PB58A is identical to the specification for PB58 in applicable column to the left. 1. Long term operation at the maximum junction temperature will result in reduced product life. Derate internal power dissipation to achieve high MTTF (Mean Time to Failure). 2. The power supply voltage specified under typical (TYP) applies, TC = 25°C unless otherwise noted. 3. Guaranteed by design but not tested. 4. +VS and –VS denote the positive and negative supply rail respectively. 5. Rating applies if the output current alternates between both output transistors at a rate faster than 60Hz. 6. +VS/–VS must be at least 15V above/below COM. CAUTION 2 The PB58 is constructed from MOSFET transistors. ESD handling procedures must be observed. The internal substrate contains beryllia (BeO). Do not break the seal. If accidentally broken, do not crush, machine, or subject to temperatures in excess of 850°C to avoid generating toxic fumes. PB58U PB58 • PB58A 0 CC = 22pF V Vs = 30 300 50 75 100 125 0 25 CASE TEMPERATURE, TC (°C) POWER RESPONSE OUTPUT VOLTAGE, VQ (V) 100 50 40 30 20 10 100K PB58U 1M 300K 3M FREQUENCY, F (Hz) 10M 400 -.5 -1 +S 100 .1 60 20 0 -20 -40 10M SLEW RATE VS. TEMP. LE 200 PULSE RESPONSE 40 10K 1M 100K FREQUENCY, F (Hz) 300 0 –25 0 25 50 75 100 125 CASE TEMPERATURE, TC (°C) 80 200 CC = 22pF –180 1K INPUT OFFSET VOLTAGE 0 -1.5 –25 –135 .03 W -SLEW 0 25 50 75 100 125 CASE TEMPERATURE, TC (°C) HARMONIC DISTORTION DRIVER = TL070 VS = 60V VO = 95VP-P Ω 0V Vs = 10 5 0 –25 OUTPUT VOLTAGE, VQ (VP-P) 0V Vs = 15 10M AVCL = 25 –90 .01 L 10 INPUT OFFSET VOLTAGE, VOS (V) QUIESCENT CURRENT, IQ (mA) 15 100K 1M 10K FREQUENCY, F (Hz) AVCL = 10 1K AVCL = 3 –45 AVCL = 3 = 10 –10 1K 2 5Ω AVCL = 10 .5 .05 1 1.5 OUTPUT CURRENT, IO (A) SMALL SIGNAL RESPONSE 20 QUIESCENT CURRENT 4 .01 0 AVCL = 25 20 VO + 6 SMALL SIGNAL RESPONSE DISTORTION, THD (%) 1K 10K 100K 1M FREQUENCY, F (Hz) –180 10M 30 0 50 75 100 125 25 CASE TEMPERATURE, TC (°C) VO - 8 R –135 20 0 100 0 –25 10 L –90 40 RCL = 1.5Ω .5 0 –45 60 Ω 12 R SMALL SIGNAL RESPONSE 7Ω RC = L .68 1 0 25 50 75 100 125 CASE TEMPERATURE, TC (°C) OPEN LOOP PHASE, Ф (°) 0 –25 = .4 CLOSED LOOP PHASE, Ф (°) 20 CL SLEW RATE, SR (V/µs) 40 R OUTPUT VOLTAGE SWING 14 =3 CURRENT LIMIT, ILIM (A) 60 1.5 VOLTAGE DROP FROM SUPPLY, VS - VO (V) CURRENT LIMIT 2 80 80 OPEN LOOP GAIN, A (dB) POWER DERATING 100 CLOSED LOOP GAIN, A (dB) INTERNAL POWER DISSIPATION, P(W) P r o d u c t I n n o v a t i o nF r o m .003 -60 -80 1 2 3 4 5 TIME, t (µs) 6 7 8 .001 300 10K 1K 3K FREQUENCY, F (Hz) 30K 3 PB58 • PB58A P r o d u c t I n n o v a t i o nF r o m GENERAL Please read Application Note 1 "General Operating Considerations" which covers stability, supplies, heat sinking, mounting, current limit, SOA interpretation, and specification interpretation. Visit www.Cirrus.com for design tools that help automate tasks such as calculations for stability, internal power dissipation, current limit; heat sink selection; Apex Precision Power’s complete Application Notes library; Technical Seminar Workbook; and Evaluation Kits. CURRENT LIMIT OUTPUT CURRENT FROM +VS or –VS (A) For proper operation, the current limit resistor (RCL) must be connected as shown in the external connection diagram. The minimum value is 0.33Ω with a maximum practical value of 47Ω. For optimum reliability the resistor value should be set as high as possible. The value is calculated as follows: +IL= .65/RCL + .010, -IL = .65/RCL. SOA 3 2 1 .5 .4 .3 ste ad ys ste ad ta te ad ys T C t= ste ta = te C 12 5° 0m s ys T C = 10 ta te T C 85 °C = 25 °C .2 .1 10 20 30 40 50 100 200 300 SUPPLY TO OUTPUT DIFFERENTIAL VOLTAGE, VS –VO (V) STABILITY Stability can be maximized by observing the following guidelines: 1. Operate the booster in the lowest practical gain. 2. Operate the driver amplifier in the highest practical effective gain. 3. Keep gain-bandwidth product of the driver lower than the closed loop bandwidth of the booster. 4. Minimize phase shift within the loop. A good compromise for (1) and (2) is to set booster gain from 3 to 10 with total (composite) gain at least a factor of 3 times booster gain. Guideline (3) implies compensating the driver as required in low composite gain configurations. Phase shift within the loop (4) is minimized through use of booster and loop compensation capacitors Cc and Cf when required. Typical values are 5pF to 33pF. Stability is the most difficult to achieve in a configuration where driver effective gain is unity (ie; total gain = booster gain). For this situation, Table 1 gives compensation values for optimum square wave response with the op amp drivers listed. CF CC DRIVER CCH OP07 22p 22p 741 18p 10p LF155 4.7p 10p LF156 4.7p 10p TL070 22p 15p 10p For: RF = 33K, RI = 3.3K, RG = 22K COMPOSITE AMPLIFIER CONSIDERATIONS Cascading two amplifiers within a feedback loop has many advantages, but also requires careful consideration of several amplifier and system parameters. The most important of these are gain, stability, slew rate, and output swing of the driver. Operating the booster amplifier in higher gains results in a higher slew rate and lower output swing requirement for the driver, but makes stability more difficult to achieve. GAIN SET RG = [ (Av-1) • 3.1K] – 6.2K RG + 6.2K Av = +1 3.1K The booster’s closed-loop gain is given by the equation above.The composite amplifier’s closed loop gain is determined by the feedback network, that is: –Rf/Ri (inverting) or 1+Rf/Ri (non-inverting). The driver amplifier’s “effective gain” is equal to the composite gain divided by the booster gain. Example: Inverting configuration (figure 1) with R i = 2K, R f = 60K, R g = 0 : Av (booster) = (6.2K/3.1K) + 1 = 3 Av (composite) = 60K/2K = – 30 Av (driver) = – 30/3 = –10 4 SR 1.5 7 >60 >60 >60 Table 1: Typical values for case where op amp effective gain = 1. CF SAFE OPERATING AREA NOTE: The output stage is protected against transient flyback. However, for protection against sustained, high energy flyback, external fast-recovery diodes should be used. FPBW 4kHz 20kHz 60kHz 80kHz 80kHz RF +15V CCH RI VIN OP AMP +Vs RCL IN COM PB58 –15V –Vs OUT COMP CC RL GAIN RG Figure 2. Non-inverting composite amplifier. SLEW RATE The slew rate of the composite amplifier is equal to the slew rate of the driver times the booster gain, with a maximum value equal to the booster slew rate. OUTPUT SWING The maximum output voltage swing required from the driver op amp is equal to the maximum output swing from the booster divided by the booster gain. The Vos of the booster must also be supplied by the driver, and should be subtracted from the available swing range of the driver. Note also that effects of Vos drift and booster gain accuracy should be considered when calculating maximum available driver swing. PB58U P r o d u c t I n n o v a t i o nF r o m PB58 • PB58A Contacting Cirrus Logic Support For all Apex Precision Power product questions and inquiries, call toll free 800-546-2739 in North America. For inquiries via email, please contact [email protected]. International customers can also request support by contacting their local Cirrus Logic Sales Representative. To find the one nearest to you, go to www.cirrus.com IMPORTANT NOTICE Cirrus Logic, Inc. and its subsidiaries ("Cirrus") believe that the information contained in this document is accurate and reliable. However, the information is subject to change without notice and is provided "AS IS" without warranty of any kind (express or implied). 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