TI SM73307

SM73307
SM73307 Dual Precision, 17 MHz, Low Noise, CMOS Input Amplifier
Literature Number: SNOSB88A
SM73307
Dual Precision, 17 MHz, Low Noise, CMOS Input Amplifier
General Description
Features
The SM73307 is a dual, low noise, low offset, CMOS input,
rail-to-rail output precision amplifier with a high gain bandwidth product. The SM73307 is ideal for a variety of instrumentation applications including solar photovoltaic.
Utilizing a CMOS input stage, the SM73307 achieves an input
bias current of 100 fA, an input referred voltage noise of 5.8
, and an input offset voltage of less than ±150 μV.
nV/
These features make the SM73307 a superior choice for precision applications.
Consuming only 1.30 mA of supply current per channel, the
SM73307 offers a high gain bandwidth product of 17 MHz,
enabling accurate amplification at high closed loop gains.
The SM73307 has a supply voltage range of 1.8V to 5.5V,
which makes it an ideal choice for portable low power applications with low supply voltage requirements.
The SM73307 is built with National’s advanced VIP50 process technology and is offered in an 8-pin MSOP package.
The SM73307 incorporates enhanced manufacturing and
support processes for the photovoltaic and automotive market, including defect detection methodologies. Reliability
qualification is compliant with the requirements and temperature grades defined in the Renewable Energy Grade and
AEC-Q100 standards.
Unless otherwise noted, typical values at VS = 5V.
■ Renewable Energy Grade
±150 μV (max)
■ Input offset voltage
100 fA
■ Input bias current
5.8 nV/√Hz
■ Input voltage noise
17 MHz
■ Gain bandwidth product
1.30 mA
■ Supply current
1.8V to 5.5V
■ Supply voltage range
0.001%
■ THD+N @ f = 1 kHz
−40°C to 125°C
■ Operating temperature range
■ Rail-to-rail output swing
■ 8-Pin MSOP package
Applications
■
■
■
■
■
Photovoltaic Electronics
Active filters and buffers
Sensor interface applications
Transimpedance amplifiers
Automotive
Typical Performance
Offset Voltage Distribution
Input Referred Voltage Noise
30155322
© 2011 National Semiconductor Corporation
301553
30155339
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SM73307 Dual Precision, 17 MHz, Low Noise, CMOS Input Amplifier
June 1, 2011
SM73307
Soldering Information
Infrared or Convection (20 sec)
Wave Soldering Lead Temp. (10 sec)
Absolute Maximum Ratings (Note 1)
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales Office/
Distributors for availability and specifications.
ESD Tolerance (Note 2)
Human Body Model
Machine Model
Charge-Device Model
VIN Differential
Supply Voltage (VS = V+ – V−)
Voltage on Input/Output Pins
Storage Temperature Range
Junction Temperature (Note 3)
Operating Ratings
235°C
260°C
(Note 1)
Temperature Range (Note 3)
Supply Voltage (VS = V+ – V−)
2000V
200V
1000V
±0.3V
6.0V
V+ +0.3V, V− −0.3V
−65°C to 150°C
+150°C
−40°C to 125°C
0°C ≤ TA ≤ 125°C
1.8V to 5.5V
−40°C ≤ TA ≤ 125°C
2.0V to 5.5V
Package Thermal Resistance (θJA(Note 3))
8-Pin MSOP
236°C/W
2.5V Electrical Characteristics
Unless otherwise specified, all limits are guaranteed for TA = 25°C, V+ = 2.5V, V− = 0V ,VO = VCM = V+/2. Boldface limits apply at
the temperature extremes.
Symbol
VOS
TC VOS
IB
Typ
(Note 4)
Max
(Note 5)
−20°C ≤ TA ≤ 85°C
±20
±180
±330
−40°C ≤ TA ≤ 125°C
±20
±180
±430
–1.75
±4
−40°C ≤ TA ≤ 85°C
0.05
1
25
−40°C ≤ TA ≤ 125°C
0.05
1
100
0.006
0.5
50
Parameter
Conditions
Min
(Note 5)
Input Offset Voltage
Input Offset Voltage Temperature Drift
(Note 6, Note 8)
Input Bias Current
VCM = 1.0V
(Note 7, Note 8)
IOS
Input Offset Current
VCM = 1V
(Note 8)
CMRR
Common Mode Rejection Ratio
0V ≤ VCM ≤ 1.4V
83
80
100
2.0V ≤ V+ ≤ 5.5V
V− = 0V, VCM = 0
85
80
100
1.8V ≤ V+ ≤ 5.5V
V− = 0V, VCM = 0
85
98
PSRR
CMVR
Power Supply Rejection Ratio
Common Mode Voltage Range
CMRR ≥ 80 dB
VO = 0.15 to 2.2V
AVOL
Open Loop Voltage Gain
RL = 2 kΩ to V+/2
VO = 0.15 to 2.2V
RL = 10 kΩ to V+/2
Output Voltage Swing
High
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84
80
92
90
86
95
pA
pA
V
dB
RL = 2 kΩ to V+/2
25
70
77
RL = 10 kΩ to V+/2
20
60
66
RL = 2 kΩ to V+/2
30
70
73
RL = 10 kΩ to V+/2
15
60
62
2
μV/°C
dB
1.5
1.5
VOUT
Output Voltage Swing
Low
μV
dB
−0.3
–0.3
CMRR ≥ 78 dB
Units
mV from
either rail
IOUT
Output Current
IS
Supply Current
SR
Slew Rate
GBW
Gain Bandwidth
en
Input Referred Voltage Noise Density
in
Input Referred Current Noise Density
THD+N
Min
(Note 5)
Typ
(Note 4)
Sourcing to V−
VIN = 200 mV (Note 9)
36
30
52
Sinking to V+
VIN = −200 mV (Note 9)
7.5
5.0
15
Parameter
Total Harmonic Distortion + Noise
Conditions
Per Channel
Max
(Note 5)
Units
mA
1.10
AV = +1, Rising (10% to 90%)
8.3
AV = +1, Falling (90% to 10%)
10.3
f = 400 Hz
6.8
f = 1 kHz
5.8
f = 1 kHz
0.01
f = 1 kHz, AV = 1, RL = 100 kΩ
VO = 0.9 VPP
0.003
f = 1 kHz, AV = 1, RL = 600Ω
VO = 0.9 VPP
0.004
1.50
1.85
mA
V/μs
14
MHz
nV/
pA/
%
5V Electrical Characteristics
Unless otherwise specified, all limits are guaranteed for TA = 25°C, V+ = 5V, V− = 0V, VCM = V+/2. Boldface limits apply at the
temperature extremes.
Symbol
VOS
TC VOS
IB
Typ
(Note 4)
Max
(Note 5)
−20°C ≤ TA ≤ 85°C
±10
±150
±300
−40°C ≤ TA ≤ 125°C
±10
±150
±400
–1.75
±4
0.1
1
25
0.1
1
100
0.01
0.5
50
Parameter
Conditions
Min
(Note 5)
Input Offset Voltage
Input Offset Voltage Temperature Drift
(Note 6, Note 8)
Input Bias Current
−40°C ≤ TA ≤ 85°C
VCM = 2.0V
(Note 7, Note 8)
−40°C ≤ TA ≤ 125°C
IOS
Input Offset Current
VCM = 2.0V
(Note 8)
CMRR
Common Mode Rejection Ratio
0V ≤ VCM ≤ 3.7V
85
82
100
2.0V ≤ V+ ≤ 5.5V
V− = 0V, VCM = 0
85
80
100
1.8V ≤ V+ ≤ 5.5V
V− = 0V, VCM = 0
85
PSRR
CMVR
AVOL
Power Supply Rejection Ratio
Common Mode Voltage Range
Open Loop Voltage Gain
VO = 0.3 to 4.7V
84
80
90
90
86
95
VO = 0.3 to 4.7V
RL = 10 kΩ to V+/2
3
μV/°C
pA
pA
dB
98
−0.3
–0.3
RL = 2 kΩ to V+/2
μV
dB
CMRR ≥ 80 dB
CMRR ≥ 78 dB
Units
4
4
V
dB
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SM73307
Symbol
SM73307
Symbol
Typ
(Note 4)
Max
(Note 5)
RL = 2 kΩ to V+/2
32
70
77
RL = 10 kΩ to V+/2
22
60
66
RL = 2 kΩ to V+/2
45
75
78
RL = 10 kΩ to V+/2
20
60
62
Parameter
Output Voltage Swing
High
Conditions
Min
(Note 5)
VOUT
Output Voltage Swing
Low
IOUT
Output Current
IS
Supply Current
SR
Slew Rate
GBW
Gain Bandwidth
en
Input Referred Voltage Noise Density
in
Input Referred Current Noise Density
THD+N
Total Harmonic Distortion + Noise
Sourcing to V−
VIN = 200 mV (Note 9)
46
38
66
Sinking to V+
VIN = −200 mV (Note 9)
10.5
6.5
23
(per channel)
Units
mV from
either rail
mA
1.30
AV = +1, Rising (10% to 90%)
6.0
9.5
AV = +1, Falling (90% to 10%)
7.5
11.5
1.70
2.05
17
f = 400 Hz
7.0
f = 1 kHz
5.8
f = 1 kHz
0.01
f = 1 kHz, AV = 1, RL = 100 kΩ
VO = 4 VPP
0.001
f = 1 kHz, AV = 1, RL = 600Ω
VO = 4 VPP
0.004
mA
V/μs
MHz
nV/
pA/
%
Note 1: Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for which the device is
intended to be functional, but specific performance is not guaranteed. For guaranteed specifications and the test conditions, see the Electrical Characteristics
Tables.
Note 2: Human Body Model, applicable std. MIL-STD-883, Method 3015.7. Machine Model, applicable std. JESD22-A115-A (ESD MM std. of JEDEC)
Field-Induced Charge-Device Model, applicable std. JESD22-C101-C (ESD FICDM std. of JEDEC).
Note 3: The maximum power dissipation is a function of TJ(MAX), θJA. The maximum allowable power dissipation at any ambient temperature is
PD = (TJ(MAX) - TA)/θJA. All numbers apply for packages soldered directly onto a PC Board.
Note 4: Typical values represent the most likely parametric norm as determined at the time of characterization. Actual typical values may vary over time and will
also depend on the application and configuration. The typical values are not tested and are not guaranteed on shipped production material.
Note 5: Limits are 100% production tested at 25°C. Limits over the operating temperature range are guaranteed through correlations using the Statistical Quality
Control (SQC) method.
Note 6: Offset voltage average drift is determined by dividing the change in VOS at the temperature extremes by the total temperature change.
Note 7: Positive current corresponds to current flowing into the device.
Note 8: This parameter is guaranteed by design and/or characterization and is not tested in production.
Note 9: The short circuit test is a momentary open loop test.
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SM73307
Connection Diagram
8-Pin MSOP
30155302
Top View
Ordering Information
Package
Part Number
Package Marking
SM73307MM
8–Pin MSOP
SM73307MME
SM73307MMX
Transport Media
NSC Drawing
Features
MUA08A
Renewable Energy Grade
1k Units Tape and Reel
S307
250 Units Tape and Reel
3.5k Units Tape and Reel
5
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SM73307
Typical Performance Characteristics
Unless otherwise noted: TA = 25°C, VS = 5V, VCM = VS/2.
Offset Voltage Distribution
Offset Voltage Distribution
30155381
30155322
TCVOS Distribution
Offset Voltage vs. VCM
30155380
30155310
Offset Voltage vs. VCM
Offset Voltage vs. VCM
30155312
30155311
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SM73307
Offset Voltage vs. Supply Voltage
CMRR vs. Frequency
30155321
30155356
Input Bias Current vs. VCM
Input Bias Current vs. VCM
30155323
30155324
Supply Current vs. Supply Voltage
Crosstalk Rejection Ratio
30155376
30155377
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SM73307
Sourcing Current vs. Supply Voltage
Sinking Current vs. Supply Voltage
30155320
30155319
Sourcing Current vs. Output Voltage
Sinking Current vs. Output Voltage
30155350
30155354
Output Swing High vs. Supply Voltage
Output Swing Low vs. Supply Voltage
30155317
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30155315
8
SM73307
Output Swing High vs. Supply Voltage
Output Swing Low vs. Supply Voltage
30155316
30155314
Output Swing High vs. Supply Voltage
Output Swing Low vs. Supply Voltage
30155318
30155313
Open Loop Frequency Response
Open Loop Frequency Response
30155373
30155341
9
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SM73307
Phase Margin vs. Capacitive Load
Phase Margin vs. Capacitive Load
30155345
30155346
Overshoot and Undershoot vs. Capacitive Load
Slew Rate vs. Supply Voltage
30155330
30155329
Small Signal Step Response
Large Signal Step Response
30155338
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30155337
10
SM73307
Small Signal Step Response
Large Signal Step Response
30155334
30155333
THD+N vs. Output Voltage
THD+N vs. Output Voltage
30155326
30155304
THD+N vs. Frequency
THD+N vs. Frequency
30155357
30155355
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SM73307
PSRR vs. Frequency
Input Referred Voltage Noise vs. Frequency
30155339
30155328
Time Domain Voltage Noise
Closed Loop Frequency Response
30155382
30155336
Closed Loop Output Impedance vs. Frequency
30155332
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The SM73307 is a dual, low noise, low offset, rail-to-rail output
precision amplifier with a wide gain bandwidth product of 17
MHz and low supply current. The wide bandwidth makes the
SM73307 an ideal choice for wide-band amplification in photovoltaic and portable applications.
The SM73307 is superior for sensor applications. The very
at 1 kHz
low input referred voltage noise of only 5.8 nV/
and very low input referred current noise of only 10 fA/
mean more signal fidelity and higher signal-to-noise ratio.
The SM73307 has a supply voltage range of 1.8V to 5.5V over
a wide temperature range of 0°C to 125°C. This is optimal for
low voltage commercial applications. For applications where
the ambient temperature might be less than 0°C, the
SM73307 is fully operational at supply voltages of 2.0V to
5.5V over the temperature range of −40°C to 125°C.
The outputs of the SM73307 swing within 25 mV of either rail
providing maximum dynamic range in applications requiring
low supply voltage. The input common mode range of the
SM73307 extends to 300 mV below ground. This feature enables users to utilize this device in single supply applications.
The use of a very innovative feedback topology has enhanced
the current drive capability of the SM73307, resulting in sourcing currents of as much as 47 mA with a supply voltage of only
1.8V.
The SM73307 is offered in an 8-pin MSOP package. This
small package is an ideal solution for applications requiring
minimum PC board footprint.
30155375
FIGURE 2. Input Common Mode Capacitance
CAPACITIVE LOAD
The unity gain follower is the most sensitive configuration to
capacitive loading. The combination of a capacitive load
placed directly on the output of an amplifier along with the
output impedance of the amplifier creates a phase lag which
in turn reduces the phase margin of the amplifier. If phase
margin is significantly reduced, the response will be either
under-damped or the amplifier will oscillate.
The SM73307 can directly drive capacitive loads of up to
120 pF without oscillating. To drive heavier capacitive loads,
an isolation resistor, RISO as shown in Figure 1, should be
used. This resistor and CL form a pole and hence delay the
phase lag or increase the phase margin of the overall system.
The larger the value of RISO, the more stable the output voltage will be. However, larger values of RISO result in reduced
output swing and reduced output current drive.
This input capacitance will interact with other impedances,
such as gain and feedback resistors which are seen on the
inputs of the amplifier, to form a pole. This pole will have little
or no effect on the output of the amplifier at low frequencies
and under DC conditions, but will play a bigger role as the
frequency increases. At higher frequencies, the presence of
this pole will decrease phase margin and also cause gain
peaking. In order to compensate for the input capacitance,
care must be taken in choosing feedback resistors. In addition
to being selective in picking values for the feedback resistor,
a capacitor can be added to the feedback path to increase
stability.
The DC gain of the circuit shown in Figure 3 is simply −R2/
R1.
30155361
FIGURE 1. Isolating Capacitive Load
30155364
FIGURE 3. Compensating for Input Capacitance
13
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SM73307
INPUT CAPACITANCE
CMOS input stages inherently have low input bias current and
higher input referred voltage noise. The SM73307 enhances
this performance by having the low input bias current of only
50 fA, as well as, a very low input referred voltage noise of
. In order to achieve this a larger input stage has
5.8 nV/
been used. This larger input stage increases the input capacitance of the SM73307. Figure 2 shows typical input common
mode capacitance of the SM73307.
Application Information
SM73307
For the time being, ignore CF. The AC gain of the circuit in
Figure 3 can be calculated as follows:
(1)
This equation is rearranged to find the location of the two
poles:
(2)
As shown in Equation 2, as the values of R1 and R2 are increased, the magnitude of the poles are reduced, which in
turn decreases the bandwidth of the amplifier. Figure 4 shows
the frequency response with different value resistors for R1
and R2. Whenever possible, it is best to choose smaller feedback resistors.
30155360
FIGURE 5. Closed Loop Frequency Response
TRANSIMPEDANCE AMPLIFIER
In many applications the signal of interest is a very small
amount of current that needs to be detected. Current that is
transmitted through a photodiode is a good example. Barcode
scanners, light meters, fiber optic receivers, and industrial
sensors are some typical applications utilizing photodiodes
for current detection. This current needs to be amplified before it can be further processed. This amplification is performed using a current-to-voltage converter configuration or
transimpedance amplifier. The signal of interest is fed to the
inverting input of an op amp with a feedback resistor in the
current path. The voltage at the output of this amplifier will be
equal to the negative of the input current times the value of
the feedback resistor. Figure 6 shows a transimpedance amplifier configuration. CD represents the photodiode parasitic
capacitance and CCM denotes the common-mode capacitance of the amplifier. The presence of all of these capacitances at higher frequencies might lead to less stable
topologies at higher frequencies. Care must be taken when
designing a transimpedance amplifier to prevent the circuit
from oscillating.
With a wide gain bandwidth product, low input bias current
and low input voltage and current noise, the SM73307 is ideal
for wideband transimpedance applications.
30155359
FIGURE 4. Closed Loop Frequency Response
As mentioned before, adding a capacitor to the feedback path
will decrease the peaking. This is because CF will form yet
another pole in the system and will prevent pairs of poles, or
complex conjugates from forming. It is the presence of pairs
of poles that cause the peaking of gain. Figure 5 shows the
frequency response of the schematic presented in Figure 3
with different values of CF. As can be seen, using a small value capacitor significantly reduces or eliminates the peaking.
30155369
FIGURE 6. Transimpedance Amplifier
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PRECISION RECTIFIER
Rectifiers are electrical circuits used for converting AC signals
to DC signals. Figure 9 shows a full-wave precision rectifier.
Each operational amplifier used in this circuit has a diode on
its output. This means for the diodes to conduct, the output of
the amplifier needs to be positive with respect to ground. If
VIN is in its positive half cycle then only the output of the bottom amplifier will be positive. As a result, the diode on the
output of the bottom amplifier will conduct and the signal will
show at the output of the circuit. If VIN is in its negative half
cycle then the output of the top amplifier will be positive, resulting in the diode on the output of the top amplifier conducting and delivering the signal from the amplifier's output to the
circuit's output.
For R2/ R1 ≥ 2, the resistor values can be found by using the
equation shown in Figure 9. If R2/ R1 = 1, then R3 should be
left open, no resistor needed, and R4 should simply be shorted.
(3)
Calculating CF from Equation 3 can sometimes result in capacitor values which are less than 2 pF. This is especially the
case for high speed applications. In these instances, it is often
more practical to use the circuit shown in Figure 7 in order to
allow more sensible choices for CF. The new feedback capacitor, CF′, is (1+ RB/RA) CF. This relationship holds as long
as RA << RF.
30155331
FIGURE 7. Modified Transimpedance Amplifier
SENSOR INTERFACE
The SM73307 has a low input bias current and low input referred noise, which makes it an ideal choice for sensor interfaces such as thermopiles, Infra Red (IR) thermometry,
thermocouple amplifiers, and pH electrode buffers.
Thermopiles generate voltage in response to receiving radiation. These voltages are often only a few microvolts. As a
result, the operational amplifier used for this application
needs to have low offset voltage, low input voltage noise, and
low input bias current. Figure 8 shows a thermopile application where the sensor detects radiation from a distance and
generates a voltage that is proportional to the intensity of the
radiation. The two resistors, RA and RB, are selected to provide high gain to amplify this signal, while CF removes the high
frequency noise.
30155374
FIGURE 9. Precision Rectifier
30155327
FIGURE 8. Thermopile Sensor Interface
15
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SM73307
A feedback capacitance CF is usually added in parallel with
RF to maintain circuit stability and to control the frequency response. To achieve a maximally flat, 2nd order response, RF
and CF should be chosen by using Equation 3
SM73307
Physical Dimensions inches (millimeters) unless otherwise noted
8-Pin MSOP
NS Package Number MUA08A
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16
SM73307
Notes
17
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SM73307 Dual Precision, 17 MHz, Low Noise, CMOS Input Amplifier
Notes
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