)*()70-5"(&108&301&3"5*0/"-".1-*'*&3 1" . * $ 3 0 5 & $ ) / 0 - 0 ( : 888"1&9.*$305&$)$0. "1&9 FEATURES • RoHS COMPLIANT • SURFACE MOUNT PACKAGE • MONOLITHIC MOS TECHNOLOGY • LOW COST • HIGH VOLTAGE OPERATION—350V • LOW QUIESCENT CURRENT TYP.—2.2mA • NO SECOND BREAKDOWN • HIGH OUTPUT CURRENT—120 mA PEAK APPLICATIONS • TELEPHONE RING GENERATOR • PIEZO ELECTRIC POSITIONING • ELECTROSTATIC TRANSDUCER & DEFLECTION • DEFORMABLE MIRROR FOCUSING 24-pin PSOP PACKAGE STYLE DF EQUIVALENT SCHEMATIC (one of two channels) +VS DESCRIPTION Q1 The PA243 is a dual high voltage monolithic MOSFET operational amplifier achieving performance features previously found only in hybrid designs while increasing reliability. This approach provides a cost-effective solution to applications where multiple amplifiers are required. Inputs are protected from excessive common mode and differential mode voltages. The safe operating area (SOA) has no secondary breakdown limitations and can be observed with all type loads by choosing an appropriate current limiting resistor. External compensation provides the user flexibility in choosing optimum gain and bandwidth for the application. The PA243DF is packaged in a 24 pin PSOP (JEDEC MO-166) package. The heatslug of the PA243DF package is isolated in excess of full supply voltage. Q2 Q3 C C1 Q4 C C2 +IN Q5 Q7 -IN ILIM Q6 Q8 Q9 D4 D1 D2 Q13 D3 Q11 OUT Q10 Q14 Q12 Q15 D5 -VS TYPICAL APPLICATION 20R +175 R CL R CL +Vsa NC 1 24 B PA243 COMPa RCL RN A - OUTa -INb +INb –175 * NC +INa -INa NC OUTb NC CN B COMPb RCL COMPb ILb CC NC * Low Cost 660v p-p Piezo Drive A single PA243 amplifier operates as a bridge driver for a piezo transducer providing a low cost 660 volt total drive capability. The RN CN network serves to raise the apparent gain of A2 at high frequencies. If RN is set equal to R the amplifiers can be compensated identically and will have matching bandwidths. See application note 20 for more details. + COMPa CC -Vsa NC La 10pF PIEZO 180 TRANSDUCER 180 W –175 * +175 10pF A PA243 EXTERNAL CONNECTIONS 20R - VIN 20R + R -Vsb +Vsb * For CC values, see graph on page 3. Note: CC must be rated for full supply voltage. * Supply bypassing required. See general Operating Considerations. APEX MICROTECHNOLOGY CORPORATION • TELEPHONE (520) 690-8600 • FAX (520) 888-3329 • ORDERS (520) 690-8601 • EMAIL email@example.com PA243 ABSOLUTE MAXIMUM RATINGS SPECIFICATIONS ABSOLUTE MAXIMUM RATINGS SPECIFICATIONS PARAMETERTEST CONDITIONS1 SUPPLY VOLTAGE, +VS to –VS OUTPUT CURRENT, continuous within SOA OUTPUT CURRENT, peak POWER DISSIPATION, continuous @ TC = 25°C INPUT VOLTAGE, differential INPUT VOLTAGE, common mode TEMPERATURE, pin solder – 10 sec TEMPERATURE, junction2 TEMPERATURE, storage TEMPERATURE RANGE, powered (case) MINTYP 350V 60 mA 120 mA 12W ±16 V ±VS 220°C 150°C –65 to +150°C –40 to +125°C MAX INPUT OFFSET VOLTAGE, initial 25 40 OFFSET VOLTAGE, vs. temperature3 Full temperature range 100 500 OFFSET VOLTAGE, vs supply 3 OFFSET VOLTAGE, vs time 70 130 BIAS CURRENT, initial 50 200 BIAS CURRENT, vs supply 2 OFFSET CURRENT, initial 50 200 INPUT IMPEDANCE, DC 1011 INPUT CAPACITANCE 6 COMMON MODE, voltage range +VS–14 COMMON MODE, voltage range -VS+12 COMMON MODE REJECTION, DC VCM = ±90V DC 84 94 NOISE, broad band 10kHz BW, RS = 1K 50 NOISE, low frequency 1-10 Hz 125 GAIN OPEN LOOP at 15Hz RL = 5K 90 BANDWIDTH, gain bandwidth product POWER BANDWIDTH 280V p-p UNITS mV µV/°C µV/V µV/kh pA pA/V pA pF V V dB µV RMS µV p-p 96 3 30 dB MHz kHz OUTPUT VOLTAGE SWING IO = 40mA ±VS–12 ±VS–10 CURRENT, peak3 120 CURRENT, continuous 60 SETTLING TIME to .1% 10V step, A V = –10 2 SLEW RATE CC = 3.3pF 30 RESISTANCE4, 1mA RCL = 0 150 RESISTANCE4, 40 mA RCL = 0 5 V mA mA µs V/µs Ω Ω POWER SUPPLY VOLTAGE ±50 CURRENT, quiescent V mA ±150 2.2 ±175 2.5 THERMAL RESISTANCE, junction to case AC, single amplifier F > 60Hz 6 7 DC, single amplifier F < 60Hz 9 11 AC, both amplifiers5 3.3 4.0 DC, both amplifiers5 5.0 6.0 RESISTANCE, junction to air6 Full temperature range 25 TEMPERATURE RANGE, case Meets full range specifications –25 +85 NOTES: 1. 2. 3. 4. 5. 6. CAUTION °C/W °C/W °C/W °C/W °C/W °C Unless otherwise noted TC = 25°C, CC = 6.8pF. DC input specifications are ± value given. Power supply voltage is typical rating. Long term operation at the maximum junction temperature will result in reduced product life. Derate internal power dissipation to achieve high MTTF. For guidance, refer to heatsink data sheet. Guaranteed but not tested. The selected value of RCL must be added to the values given for total output resistance. Rating applies when power dissipation is equal in the two amplifiers. Rating applies with solder connection of heatslug to a minimum 1in2 foil area of the printed circuit board. The PA243 is constructed from MOSFET transistors. ESD handling procedures must be observed. APEX MICROTECHNOLOGY CORPORATION • 5980 NORTH SHANNON ROAD • TUCSON, ARIZONA 85741 • USA • APPLICATIONS HOTLINE: 1 (800) 546-2739 PA243 108&3%&3"5*/( #PUI"NQMJGJFST 4JOHMF"NQMJGJFS 55$ 55" 55" 5&.1&3"563&5$ 5&.1&3"563&$ 4."--4*(/"-3&410/4& 1)"4&þ Q' Q' Q' Q' Q' Q' , , , . '3&26&/$:')[ , . , . '3&26&/$:')[ . 4-&83"5& )"3.0/*$%*45035*0/ "7 $$Q' 3-, , , '3&26&/$:')[ $0..0/.0%&3&+&$5*0/ , , '3&26&/$:')[ , $0.1&/4"5*0/$"1"$*5"/$&$$Q' , 5$$ 5$$ /&("5*7& 104*5*7& 108&33&410/4& Q' Q' Q' , , , '3&26&/$:')[ , , '3&26&/$:')[ . 26*&4$&/5$633&/5 $ * 2 $ * 2 *2$ 505"-4611-:70-5"(&7 06516570-5"(&48*/( 7%301!$ 7%301!$ 7%301!$ Q' 108&34611-:3&+&$5*0/ ("*/ Q' 7%301'30.747 711 $0..0/.0%&3&+&$5*0/$.3E# 711 4-&83"5&7T 711 108&34611-:3&+&$5*0/143E# %*45035*0/ 5$$ Q' 1)"4&3&410/4& Q' 5$$ 06516570-5"(&7065 QQ 7#& 01&/-001("*/"E# 7#& $0.1&/4"5*0/Q' 55$ ("*/"/%$0.1&/4"5*0/ *-*.*5745&.1&3"563& /03."-*;&%26*&4$&/5$633&/5 7#&7 */5&3/"-108&3%*44*1"5*0/18 TYPICAL PERFORMANCE GRAPHS 7%301!$ 065165$633&/5*0N" APEX MICROTECHNOLOGY CORPORATION • TELEPHONE (520) 690-8600 • FAX (520) 888-3329 • ORDERS (520) 690-8601 • EMAIL firstname.lastname@example.org OPERATING CONSIDERATIONS PA243 GENERAL CURRENT LIMIT Please read Application Note 1 "General Operating Considerations" which covers stability, power supplies, heat sinking, mounting, current limit, SOA interpretation, and specification interpretation. Visit www.apexmicrotech.com for design tools that help automate tasks such as calculations for stability, internal power dissipation, current limit, heat sink selection, Apex's complete Application Notes library, Technical Seminar Workbook and Evaluation Kits. For proper operation, the current limit resistor, Rcl, must be connected as shown in the external connection diagram. The minimum value is 3.9 ohms, however for optimum reliability, the resistor should be set as high as possible. The maximum practical value is 110 ohms. Current limit values can be predicted as follows: Ilimit = Vbe Rcl Where Vbe is shown in the CURRENT LIMIT typical graph. Open loop gain and phase shift both increase with increasing temperature. The PHASE COMPENSATION typical graph shows closed loop gain and phase compensation capacitor value relationships for four case temperatures. The curves are based on achieving a phase margin of 50°. Calculate the highest case temperature for the application (maximum ambient temperature and highest internal power dissipation) before choosing the compensation. Keep in mind that when working with small values of compensation, parasitics may play a large role in performance of the finished circuit. The compensation capacitor must be rated for at least the total voltage applied to the amplifier and should be a temperature stable type such as NPO or COG. OTHER STABILITY CONCERNS There are two important concepts about closed loop gain when choosing compensation. They stem from the fact that while "gain" is the most commonly used term, β (the feedback factor) is really what counts when designing for stability. 1. Gain must be calculated as a non-inverting circuit (equal input and feedback resistors can provide a signal gain of -1, but for calculating offset errors, noise, and stability, this is a gain of 2). 2. Including a feedback capacitor changes the feedback factor or gain of the circuit. Consider Rin=4.7k, Rf=47k for a gain of 11. Compensation of 4.7 to 6.8pF would be reasonable. Adding 33pF parallel to the 47k rolls off the circuit at 103kHz, and at 2MHz has reduced gain from 11 to roughly 1.5 and the circuit is likely to oscillate. As a general rule the DC summing junction impedance (parallel combination of the feedback resistor and all input resistors) should be limited to 5k ohms or less. The amplifier input capacitance of about 6pF, plus capacitance of connecting traces or wires and (if used) a socket will cause undesirable circuit performance and even oscillation if these resistances are too high. In circuits requiring high resistances, measure or estimate the total sum point capacitance, multiply by Rin/Rf, and parallel Rf with this value. Capacitors included for this purpose are usually in the single digit pF range. This technique results in equal feedback factor calculations for AC and DC cases. It does not produce a roll off, but merely keeps β constant over a wide frequency range. Paragraph 6 of Application Note 19 details suitable stability tests for the finished circuit. Note that +Vbe should be used to predict current through the +Vs pin, -Vbe for current through the -Vs pin, and that they vary with case temperature. Value of the current limit resistor at a case temperature of 25° can be estimated as follows: Rcl = 0.7 Ilimit When the amplifier is current limiting, there may be spurious oscillation present during the current limited portion of the negative half cycle. The frequency of the oscillation is not predictable and depends on the compensation, gain of the amplifier, value of the current limit resistor, and the load. The oscillation will cease as the amplifier comes out of current limit. SAFE OPERATING AREA The MOSFET output stage of the PA243 is not limited by second breakdown considerations as in bipolar output stages. However there are still three distinct limitations: 1. Voltage withstand capability of the transistors. 2. Current handling capability of the die metalization. 3. Temperature of the output MOSFETS. 065165$633&/5'30.74PS74N" PHASE COMPENSATION 1"40" N 4 N 4 %$ %$ 5 $ 5 %$ $ $ $ 16-4&$637&4! %65:$:$-&."9 4611-:50065165%*''&3&/5*"-74707 APEX MICROTECHNOLOGY CORPORATION • 5980 NORTH SHANNON ROAD • TUCSON, ARIZONA 85741 • USA • APPLICATIONS HOTLINE: 1 (800) 546-2739 PA243 OPERATING CONSIDERATIONS These limitations can be seen in the SOA (see Safe Operating Area graphs). Note that each pulse capability line shows a constant power level (unlike second breakdown limitations where power varies with voltage stress). These lines are shown for a case temperature of 25°C and correspond to thermal resistances of 5.2°C/W for the PA243DF. Pulse stress levels for other case temperatures can be calculated in the same manner as DC power levels at different temperatures. The output stage is protected against transient flyback by the parasitic diodes of the output stage MOSFET structure. However, for protection against sustained high energy flyback external fast-recovery diodes must be used. HEATSINKING The PA243DF package has a large exposed integrated copper heatslug to which the monolithic amplifier is directly attached. The solder connection of the heatslug to a minimum of 1 square inch foil area on the printed circuit board will result in thermal performance of 25°C/W junction to air rating of the PA243DF. Solder connection to an area of 1 to 2 square inches is recommended. This may be adequate heatsinking but the large number of variables involved suggest temperature measurements be made on the top of the package. Do not allow the temperature to exceed 85°C. In the case of inverting circuits where the +IN pin is grounded, the diodes mentioned above will also afford protection from excessive common mode voltage. In the case of non-inverting circuits, clamp diodes from each input to each supply will provide protection. Note that these diodes will have substantial reverse bias voltage under normal operation and diode leakage will produce errors. Some applications will also need over-voltage protection devices connected to the power supply rails. Unidirectional zener diode transient suppressors are recommended. The zeners clamp transients to voltages within the power supply rating and also clamp power supply reversals to ground. Whether the zeners are used or not the system power supply should be evaluated for transient performance including power-on overshoot and power-off polarity reversals as well as line regulation. See Z1 and Z2 in Figure 1. APPLICATION REFERENCES: For additional technical information please refer to the following Application Notes: AN1: General Operating Considerations AN3: Bridge Circuit Drives AN25: Driving Capacitive Loads AN38: Loop Stability with Reactive Loads FIGURE 1 +Vs +Vs -IN Q1 +IN Z1 OUT Q2 -Vs -Vs Z2 OVERVOLTAGE PROTECTION Although the PA241 can withstand differential input voltages up to 16V, in some applications additional external protection may be needed. Differential inputs exceeding 16V will be clipped by the protection circuitry. However, if more than a few milliamps of current is available from the overload source, the protection circuitry could be destroyed. For differential sources above 16V, adding series resistance limiting input current to 1mA will prevent damage. Alternatively, 1N4148 signal diodes connected anti-parallel across the input pins is usually sufficient. In more demanding applications where bias current is important, diode connected JFETs such as 2N4416 will be required. See Q1 and Q2 in Figure 1. In either case the differential input voltage will be clamped to 0.7V. This is sufficient overdrive to produce the maximum power bandwidth. This data sheet has been carefully CORPORATION checked and is believed to be reliable,(520) however, no responsibility assumed888-3329 for possible • inaccuracies omissions. All specifications are email@example.com subject to change without notice. APEX MICROTECHNOLOGY • TELEPHONE 690-8600 • FAXis (520) ORDERS or(520) 690-8601 • EMAIL PA243U REV D MARCH 2006 © 2006 Apex Microtechnology Corp.