EL5144, EL5146, EL5244, EL5246, EL5444 ® Data Sheet April 13, 2005 100MHz Single-Supply Rail-to-Rail Amplifiers Features • Rail-to-rail output swing The EL5144 series amplifiers are voltage-feedback, high speed, rail-to-rail amplifiers designed to operate on a single +5V supply. They offer unity gain stability with an unloaded 3dB bandwidth of 100MHz. The input common-mode voltage range extends from the negative rail to within 1.5V of the positive rail. Driving a 75Ω double terminated coaxial cable, the EL5144 series amplifiers drive to within 150mV of either rail. The 200V/µs slew rate and 0.1%/0.1° differential gain/differential phase makes these parts ideal for composite and component video applications. With their voltagefeedback architecture, these amplifiers can accept reactive feedback networks, allowing them to be used in analog filtering applications These amplifiers will source 90mA and sink 65mA. • -3dB bandwidth = 100MHz • Single-supply +5V operation • Power-down to 2.6µA • Large input common-mode range 0V < VCM < 3.5V • Diff gain/phase = 0.1%/0.1° • Low power 35mW per amplifier • Space-saving SOT23-5, MSOP8 & 10, & QSOP16 packages • Pb-Free available (RoHS compliant) Applications The EL5146 and EL5246 have a power-savings disable feature. Applying a standard TTL low logic level to the CE (Chip Enable) pin reduces the supply current to 2.6µA within 10ns. Turn-on time is 500ns, allowing true break-beforemake conditions for multiplexing applications. Allowing the CE pin to float or applying a high logic level will enable the amplifier. • Video amplifiers For applications where board space is critical, singles are offered in a 5-pin SOT-23 package, duals in 8- and 10-pin MSOP packages, and quads in a 16-pin QSOP package. Singles, duals, and quads are also available in industrystandard pinouts in SO and PDIP packages. All parts operate over the industrial temperature range of -40°C to +85°C. • High speed communications 1 FN7177.1 • 5V analog signal processing • Multiplexers • Line drivers • Portable computers • Sample & hold amplifiers • Comparators CAUTION: These devices are sensitive to electrostatic discharge; follow proper IC Handling Procedures. 1-888-INTERSIL or 1-888-352-6832 | Intersil (and design) is a registered trademark of Intersil Americas Inc. Copyright Intersil Americas Inc. 2003, 2005. All Rights Reserved All other trademarks mentioned are the property of their respective owners. EL5144, EL5146, EL5244, EL5246, EL5444 Ordering Information (Continued) Ordering Information PART NUMBER PACKAGE TAPE & REEL PKG. DWG. # PART NUMBER PACKAGE TAPE & REEL PKG. DWG. # EL5246CYZ (See Note) 10-Pin MSOP (Pb-free) - MDP0043 EL5246CYZ-T7 (See Note) 10-Pin MSOP (Pb-free) 7” MDP0043 MDP0038 10-Pin MSOP (Pb-free) MDP0043 MDP0038 EL5246CYZ-T13 (See Note) 13” 7” (250 pcs) EL5444CN 14-Pin PDIP - MDP0031 8-Pin PDIP - MDP0031 EL5444CS 14-Pin SOIC - MDP0027 EL5146CS 8-Pin SOIC - MDP0027 EL5444CS-T7 14-Pin SOIC 7” MDP0027 EL5146CS-T7 8-Pin SOIC 7” MDP0027 EL5444CS-T13 14-Pin SOIC 13” MDP0027 EL5146CS-T13 8-Pin SOIC 13” MDP0027 - MDP0027 14-Pin SOIC (Pb-free) MDP0027 8-Pin SOIC (Pb-free) EL5444CSZ (See Note) - EL5146CSZ (See Note) 7” MDP0027 14-Pin SOIC (Pb-free) MDP0027 8-Pin SOIC (Pb-free) EL5444CSZ-T7 (See Note) 7” EL5146CSZ-T7 (See Note) 13” MDP0027 14-Pin SOIC (Pb-free) MDP0027 8-Pin SOIC (Pb-free) EL5444CSZ-T13 (See Note) 13” EL5146CSZ-T13 (See Note) EL5444CU 16-Pin QSOP - MDP0040 EL5244CN 8-Pin PDIP - MDP0031 EL5444CU-T13 16-Pin QSOP 13” MDP0040 EL5244CS 8-Pin SOIC - MDP0027 7” MDP0027 16-Pin QSOP (Pb-free) MDP0040 8-Pin SOIC EL5444CUZ (See Note) - EL5244CS-T7 EL5244CS-T13 8-Pin SOIC 13” MDP0027 MDP0040 8-Pin SOIC (Pb-free) - MDP0027 16-Pin QSOP (Pb-free) 7” EL5244CSZ (See Note) EL5444CUZ-T7 (See Note) MDP0040 8-Pin SOIC (Pb-free) 7” 16-Pin QSOP (Pb-free) 13” EL5244CSZ-T7 (See Note) EL5444CUZ-T13 (See Note) EL5244CSZ-T13 (See Note) 8-Pin SOIC (Pb-free) 13” MDP0027 EL5244CY 8-Pin MSOP - MDP0043 EL5244CY-T13 8-Pin MSOP 13” MDP0043 EL5244CYZ (See Note) 8-Pin MSOP (Pb-free) - MDP0043 EL5244CYZ-T7 (See Note) 8-Pin MSOP (Pb-free) 7” MDP0043 EL5244CYZ-T13 (See Note) 8-Pin MSOP (Pb-free) 13” MDP0043 EL5246CN 14-Pin PDIP - MDP0031 EL5246CS 14-Pin SOIC - MDP0027 EL5246CS-T7 14-Pin SOIC 7” MDP0027 EL5246CS-T13 14-Pin SOIC 13” MDP0027 EL5246CSZ (See Note) 14-Pin SOIC (Pb-free) - MDP0027 EL5246CSZ-T7 (See Note) 14-Pin SOIC (Pb-free) 7” MDP0027 EL5246CSZ-T13 (See Note) 14-Pin SOIC (Pb-free) 13” MDP0027 EL5246CY 10-Pin MSOP - MDP0043 EL5246CY-T13 10-Pin MSOP 13” MDP0043 EL5144CW-T7 5-Pin SOT-23* 7” (3K pcs) MDP0038 EL5144CW-T7A 5-Pin SOT-23* 7” (250 pcs) MDP0038 EL5144CWZ-T7 (See Note) 5-Pin SOT-23* (Pb-free) 7” (3K pcs) EL5144CWZ-T7A (See Note) 5-Pin SOT-23* (Pb-free) EL5146CN 2 MDP0027 *EL5144CW symbol is .Jxxx where xxx represents date NOTE: Intersil Pb-free products employ special Pb-free material sets; molding compounds/die attach materials and 100% matte tin plate termination finish, which are RoHS compliant and compatible with both SnPb and Pb-free soldering operations. Intersil Pb-free products are MSL classified at Pb-free peak reflow temperatures that meet or exceed the Pb-free requirements of IPC/JEDEC J STD-020. EL5144, EL5146, EL5244, EL5246, EL5444 s Pinouts EL5146 & EL5146 (8-PIN SO, PDIP) TOP VIEW EL5144 (5-PIN SOT-23) TOP VIEW OUT 1 GND 2 5 + 4 IN- 1 INA- 2 - 8 VS INA+ 1 7 OUTB CEA 2 6 INB- GND 3 5 INB+ CEB 4 INB+ 5 + INA+ 3 - GND + 4 1 IN- 2 IN+ 3 GND 4 - 10 INA+ + - + 8 CE 7 VS 6 OUT 5 NC EL5246 (14-PIN SOIC, PDIP) TOP VIEW EL5246 (10-PIN MSOP) TOP VIEW EL5244 (8-PIN SOIC, PDIP, MSOP) TOP VIEW OUTA NC - 3 IN+ VS INA+ 1 NC 2 14 INA- 9 OUTA 8 VS CEA 3 12 NC 7 OUTB GND 4 11 VS 6 INB- CEB 5 10 NC NC 6 INB+ 7 13 OUTA + + - 9 OUTB 8 INB- EL5444 (16-PIN QSOP) TOP VIEW EL5444 (14-PIN SOIC, PDIP) TOP VIEW INA- 2 15 IND- 12 IND+ INA+ 3 14 IND+ 4 11 GND VS 4 13 GND INB+ 5 10 INC+ VS 5 12 GND INB- 6 9 INC- INB+ 6 11 INC+ OUTB 7 8 OUTC INB- 7 OUTB 8 - + - + - + 3 - VS + 3 - INA+ + 13 - 2 + INA- - IND- OUTD + 16 OUTD 14 - 1 1 + OUTA OUTA 10 INC- 9 OUTC EL5144, EL5146, EL5244, EL5246, EL5444 Absolute Maximum Ratings (TA = 25°C) Pin Voltages. . . . . . . . . . . . . . . . . . . . . . . . . GND -0.5V to VS +0.5V Storage Temperature . . . . . . . . . . . . . . . . . . . . . . . .-65°C to +150°C Operating Temperature . . . . . . . . . . . . . . . . . . . . . . .-40°C to +85°C Supply Voltage between VS and GND . . . . . . . . . . . . . . . . . . . . .+6V Maximum Continuous Output Current . . . . . . . . . . . . . . . . . . . 50mA Power Dissipation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . See Curves CAUTION: Stresses above those listed in “Absolute Maximum Ratings” may cause permanent damage to the device. This is a stress only rating and operation of the device at these or any other conditions above those indicated in the operational sections of this specification is not implied. IMPORTANT NOTE: All parameters having Min/Max specifications are guaranteed. Typical values are for information purposes only. Unless otherwise noted, all tests are at the specified temperature and are pulsed tests, therefore: TJ = TC = TA Electrical Specifications PARAMETER VS = +5V, GND = 0V, TA = 25°C, CE = +2V, unless otherwise specified. DESCRIPTION CONDITIONS MIN TYP MAX UNIT AC PERFORMANCE dG Differential Gain Error (Note 1) G = 2, RL = 150Ω to 2.5V, RF = 1kΩ dP Differential Phase Error (Note 1) G = 2, RL = 150Ω to 2.5V, RF = 1kΩ 0.1 ° BW Bandwidth -3dB, G = 1, RL = 10kΩ, RF = 0 100 MHz -3dB, G = 1, RL = 150Ω, RF = 0 60 MHz ±0.1dB, G = 1, RL = 150Ω to GND, RF = 0 8 MHz 60 MHz 200 V/µs 35 ns BW1 Bandwidth GBWP Gain Bandwidth Product SR Slew Rate G = 1, RL = 150Ω to GND, RF = 0, VO = 0.5V to 3.5V tS Settling Time to 0.1%, VOUT = 0V to 3V 0.1 150 % DC PERFORMANCE AVOL VOS Open Loop Voltage Gain Offset Voltage TCVOS Input Offset Voltage Temperature Coefficient IB Input Bias Current RL = no load, VOUT = 0.5V to 3V 54 65 dB RL = 150Ω to GND, VOUT = 0.5V to 3V 40 50 dB VCM = 1V, SOT23-5 and MSOP packages 25 mV VCM = 1V, All other packages 15 mV 10 VCM = 0V & 3.5V 2 mV/°C 100 nA 3.5 V INPUT CHARACTERISTICS CMIR Common Mode Input Range CMRR ≥ 47dB 0 CMRR Common Mode Rejection Ratio DC, VCM = 0 to 3.0V 50 60 dB DC, VCM = 0 to 3.5V 47 60 dB RIN Input Resistance 1.5 GΩ CIN Input Capacitance 1.5 pF OUTPUT CHARACTERISTICS VOP VON Positive Output Voltage Swing Negative Output Voltage Swing RL = 150Ω to 2.5V (Note 2) 4.70 4.85 V RL = 150Ω to GND (Note 2) 4.20 4.65 V RL = 1kΩ to 2.5V (Note 2) 4.95 4.97 V RL = 150Ω to 2.5V (Note 2) 0.15 RL = 150Ω to GND (Note 2) 0 RL = 1kΩ to 2.5V (Note 2) 0.30 V V 0.03 0.05 V +IOUT Positive Output Current RL = 10Ω to 2.5V 60 90 120 mA -IOUT Negative Output Current RL = 10Ω to 2.5V -50 -65 -80 mA ENABLE (EL5146 & EL5246 ONLY) 4 EL5144, EL5146, EL5244, EL5246, EL5444 Electrical Specifications PARAMETER VS = +5V, GND = 0V, TA = 25°C, CE = +2V, unless otherwise specified. (Continued) DESCRIPTION CONDITIONS MIN TYP MAX UNIT tEN Enable Time EL5146, EL5246 500 ns tDIS Disable Time EL5146, EL5246 10 ns IIHCE CE pin Input High Current CE = 5V, EL5146, EL5246 0.003 1 mA IILCE CE pin Input Low Current CE = 0V, EL5146, EL5246 -1.2 -3 mA VIHCE CE pin Input High Voltage for Power EL5146, EL5246 Up VILCE CE pin Input Low Voltage for Power EL5146, EL5246 Down 2.0 V 0.8 V SUPPLY IsON Supply Current - Enabled (per amplifier) No load, VIN = 0V, CE = 5V 7 8.8 mA IsOFF Supply Current - Disabled (per amplifier) No load, VIN = 0V, CE = 0V 2.6 5 mA PSOR Power Supply Operating Range 4.75 5.0 5.25 V PSRR Power Supply Rejection Ratio 50 60 DC, VS = 4.75V to 5.25V NOTES: 1. Standard NTSC test, AC signal amplitude = 286mVP-P, f = 3.8MHz, VOUT is swept from 0.8V to 3.4V, RL is DC-coupled. 2. RL is total load resistance due to feedback resistor and load resistor. 5 dB EL5144, EL5146, EL5244, EL5246, EL5444 Typical Performance Curves Non-Inverting Frequency Response (Gain) Non-Inverting Frequency Response (Phase) 2 0 AV=1, RF=0Ω 0 -45 AV=2, RF=1kΩ -2 Phase (°) Normalized Magnitude (dB) AV=1, RF=0Ω AV=5.6, RF=1kΩ -4 AV=5.6, RF=1kΩ -90 AV=2, RF=1kΩ -135 -6 VCM=1.5V RL=150Ω VCM=1.5V RL=150Ω -180 -8 1M 10M 100M 1M 10M Frequency (Hz) 100M Frequency (Hz) Inverting Frequency Response (Gain) Inverting Frequency Response (Phase) 2 AV=-1 135 AV=-2 -2 Phase (°) Normalized Magnitude (dB) 180 AV=-1 0 AV=-5.6 -4 AV=-2 90 AV=-5.6 45 -6 VCM=1.5V RF=1kΩ RL=150Ω VCM=1.5V RF=1kΩ RL=150Ω 0 -8 1M 10M 100M 1M 10M Frequency (Hz) 3dB Bandwidth vs Die Temperature for Various Gains 3dB Bandwidth vs Die Temperature for Various Gains 100 150 RL=150Ω RL=10kΩ 120 3dB Bandwidth (MHz) 3dB Bandwidth (MHz) 80 AV=1, RF=0Ω 60 40 AV=2, RF=1kΩ 20 0 -55 100M Frequency (Hz) 25 60 AV=2, RF=1kΩ AV=5.6, RF=1kΩ 65 Die Temperature (°C) 6 90 30 AV=5.6, RF=1kΩ -15 AV=1, RF=0Ω 105 145 0 -55 -15 25 65 Die Temperature (°C) 105 145 EL5144, EL5146, EL5244, EL5246, EL5444 Typical Performance Curves (Continued) Frequency Response for Various RL VCM=1.5V RF=0Ω AV=1 VCM=1.5V RL=150Ω AV=1 8 Normalized Magnitude (dB) 4 Normalized Magnitude (dB) Frequency Response for Various CL RL=10kΩ 2 0 RL=520Ω -2 RL=150Ω -4 CL=100pF CL=47pF 4 0 CL=22pF -4 CL=0pF -8 1M 10M 100M 1M 10M Frequency (Hz) 100M Frequency (Hz) Frequency Response for Various RF and RG Group Delay vs Frequency 10 RF=RG=2kΩ RF=RG=1kΩ 0 -2 RF=RG=560Ω -4 6 4 AV=1 RF=1Ω 2 VCM=1.5V RL=150Ω AV=2 -6 AV=2 RF=1kΩ 8 Group Delay (ns) Normalized Magnitude (dB) 2 1M 10M 0 1M 100M 10M 100M Frequency (Hz) Frequency (Hz) Open Loop Gain and Phase vs Frequency Open Loop Voltage Gain vs Die Temperature 0 80 45 70 RL=1kΩ Phase 90 40 RL=150Ω 135 Gain 20 180 Phase (°) Gain (dB) 60 Open Loop Gain (dB) 80 No Load 60 50 RL=150Ω 40 0 1k 10k 100k 1M Frequency (Hz) 7 10M 225 100M 30 -55 -15 25 65 Die Temperature (°C) 105 145 EL5144, EL5146, EL5244, EL5246, EL5444 Typical Performance Curves (Continued) Voltage Noise vs Frequency - Video Amp Closed Loop Output Impedance vs Frequency 10k 200 Closed Loop (ZO) Voltage Noise (nV/√Hz) RF=0Ω AV=2 1k 100 20 2 0.2 10 10 100 10k 1k 100k 1M 10M 100M 10k 100k Frequency (Hz) 1M 10M 100M Frequency (Hz) Offset Voltage vs Die Temperature (6 Typical Samples) PSRR and CMRR vs Frequency 20 12 PSRR, CMRR (dB) Offset Voltage (mV) 0 6 0 -6 CMRR -20 PSRR-40 PSRR+ -60 -12 -55 -15 25 65 105 -80 1k 145 10k Die Temperature (°C) Output Voltage Swing vs Frequency for THD < 1% 1M 10M 100M Output Voltage Swing vs Frequency for THD < 0.1% 5 RF=1kΩ AV=2 4 RL=500Ω to 2.5V 3 RL=150Ω to 2.5V 2 1 0 1M 10M Frequency (Hz) 8 100M Output Voltage Swing (VPP) 5 Output Voltage Swing (VPP) 100k Frequency (Hz) RF=1kΩ AV=2 4 3 RL=500Ω to 2.5V 2 1 RL=150Ω to 2.5V 0 1M 10M Frequency (Hz) 100M EL5144, EL5146, EL5244, EL5246, EL5444 Typical Performance Curves (Continued) Large Signal Pulse Response (Single Supply) Small Signal Pulse Response (Single Supply) 1.9 VS=5V RL=150Ω to 0V RF=1kΩ AV=2 3 Output Voltage (V) Output Voltage (V) 4 2 1 0 VS=5V RL=150Ω to 0V RF=1kΩ AV=2 1.7 1.5 1.3 1.1 Time (20ns/div) Time (20ns/div) Large Signal Pulse Response (Split Supplies) Small Signal Pulse Response (Split Supply) 0.4 VS=±2.5V RL=150Ω to 0V RF=1kΩ AV=2 2 Output Voltage (V) Output Voltage (V) 4 0 -2 -4 VS=±2.5V RL=150Ω to 0V RF=1kΩ AV=2 0.2 0 -0.2 -0.4 Time (20ns/div) Time (20ns/div) Settling Time vs Settling Accuracy Slew Rate vs Die Temperature 250 100 Settling Time (ns) 80 Slew Rate (V/µs) RL=1kΩ RF=500Ω AV=-1 VSTEP=3V 60 40 200 20 0 0.01 0.1 Settling Accuracy (%) 9 1 150 -55 -15 25 65 Die Temperature (°C) 105 145 EL5144, EL5146, EL5244, EL5246, EL5444 Typical Performance Curves (Continued) Differential Phase for RL Tied to 0V Differential Gain for RL Tied to 0V RF=0Ω AV=1 RF=0Ω AV=1 0.2 Differential Phase (°) Differential Gain (%) 0.08 0.04 RL=10kΩ 0 RL=150Ω -0.04 -0.08 0.1 RL=10kΩ 0 RL=150Ω -0.1 -0.2 0.25 1.75 3.25 0.25 VOUT (V) Differential Gain for RL Tied to 2.5V Differential Phase (°) Differential Gain (%) RF=0Ω AV=1 0.2 0.1 0 RL=10kΩ -0.1 RL=150Ω -0.2 0.1 RL=10kΩ 0 -0.1 RL=150Ω -0.2 0.5 2 3.5 0.5 2 VOUT (V) 0.2 Differential Phase for RL Tied to 0V RF=1kΩ AV=2 0.1 0 0.2 Differential Phase (°) RL=150Ω 3.5 VOUT (V) Differential Gain for RL Tied to 0V Differential Gain (%) 3.25 Differential Phase for RL Tied to 2.5V RF=0Ω AV=1 0.2 1.75 VOUT (V) RL=10kΩ -0.1 -0.2 RF=1kΩ AV=2 RL=150Ω 0.1 0 RL=10kΩ -0.1 -0.2 0.5 2 VOUT (V) 10 3.5 0.5 2 VOUT (V) 3.5 EL5144, EL5146, EL5244, EL5246, EL5444 Typical Performance Curves (Continued) Differential Gain for RL Tied to 2.5V RF=1kΩ AV=2 RF=1kΩ AV=2 0.2 0.1 Differential Phase (°) 0.2 Differential Gain (%) Differential Phase for RL Tied to 2.5V RL=150Ω 0 -0.1 RL=10kΩ -0.2 RL=10kΩ 0.1 0 RL=150Ω -0.1 -0.2 0.5 3.5 2 0.5 VOUT (V) 2nd and 3rd Harmonic Distortion vs Frequency 2nd and 3rd Harmonic Distortion vs Frequency -25 -25 -45 HD3 -35 HD3 Distortion (dBc) Distortion (dBc) -35 HD2 -55 -65 -45 HD2 -55 -65 -75 1M VOUT=0.25V to 2.25V RL=100Ω to 0V 10M 100M 10M 100M Frequency (Hz) 2nd and 3rd Harmonic Distortion vs. Frequency Channel to Channel Crosstalk - Duals and Quads (Worst Channel) -25 0 HD3 -20 Crosstalk (dB) -35 -45 -55 VOUT=0.5V to 2.5V RL=100Ω to 0V -75 1M Frequency (Hz) Distortion (dBc) 3.5 2 VOUT (V) HD2 -65 -40 -60 -80 VOUT VOUT =1V =1V to to 3V =100Ω to 0V RL3V -75 1M 10M Frequency (Hz) 11 100M -100 100k 1M 10M Frequency (Hz) 100M EL5144, EL5146, EL5244, EL5246, EL5444 Typical Performance Curves (Continued) Supply Current (per Amp) vs Supply Voltage Output Current vs Die Temperature 120 RL=10Ω to 2.5V 8 Output Current (mA) Supply Current (mA) 100 6 4 2 Source 80 60 Sink 40 0 0 1 2 3 4 20 -55 5 -15 Supply Current - ON (per Amp) vs Die Temperature 65 105 145 105 145 105 145 Supply Current - OFF (per Amp) vs Die Temperature 9 5 8 4 Supply Current (µA) Supply Current (mA) 25 Die Temperature (°C) Supply Voltage (V) 7 6 5 3 2 1 4 -55 25 -15 65 105 0 -55 145 -15 Die Temperature (°C) 25 65 Die Temperature (°C) Positive Output Voltage Swing vs Die Temperature Negative Output Voltage Swing vs Die Temperature 5 0.5 RL=150Ω 0.4 Output Voltage (V) Output Voltage (V) 4.9 RL=150Ω to 2.5V 4.8 4.7 RL=150Ω to 0V 4.6 0.3 0.2 RL=150Ω to 2.5V 0.1 RL=150Ω to 0V 4.5 -55 -15 25 65 Die Temperature (°C) 12 105 145 0 -55 -15 25 65 Die Temperature (°C) EL5144, EL5146, EL5244, EL5246, EL5444 Typical Performance Curves (Continued) Output Voltage from Either Rail vs Die Temperature for Various Effective RLOAD OFF Isolation - EL5146 & EL5246 300 -20 Output Voltage (V) Effective RLOAD=1kΩ 10 Ω Effective RLOAD=5k 1 -55 25 65 105 -60 EL5246CS -80 EL5246CN -100 Effective RLOAD = RL//RF to VS/2 -15 EL5146CS & EL5146CN -40 Magnitude (dBc) Effective RLO 100 50Ω AD=1 -120 10k 145 100k Die Temperature (°C) Maximum Power Dissipation vs. Ambient Temperature Singles (TJMAX = 150°C) PDIP, ΘJA = 110°C/W 1.6 Power Dissipation (W) Power Dissipation (W) 100M 2.5 SOIC, ΘJA = 161°C/W 1.2 0.8 0.4 0 -50 -20 10 40 70 100 Ambient Temperature (°C) 2.5 PDIP-14, ΘJA = 83°C/W 1.5 1.0 SOIC-14, ΘJA = 118°C/W QSOP-16, ΘJA = 158°C/W 0 -50 -20 10 40 Ambient Temperature (°C) 13 PDIP-8, ΘJA = 107°C/W SOIC-14, ΘJA = 120°C/W 1.5 1.0 0.5 0 -50 SOIC-8, ΘJA = 159°C/W MSOP-8,10, ΘJA = 206°C/W -20 10 40 Ambient Temperature (°C) Maximum Power Dissipation vs. Ambient Temperature Quads (TJMAX = 150°C) 2.0 PDIP-14, ΘJA = 87°C/W 2.0 SOT23-5, ΘJA = 256°C/W Power Dissipation (W) 10M Maximum Power Dissipation vs. Ambient Temperature Duals (TJMAX = 150°C) 2.0 0.5 1M Frequency (Hz) 70 100 70 100 EL5144, EL5146, EL5244, EL5246, EL5444 Pin Descriptions 5-PIN SOT23 8-PIN SO/PDIP/ 8-PIN MSOP SO/PDIP 16-PIN MSOP 14-PIN 14-PIN SO/PDIP SO/PDIP 16-PIN QSOP NAME FUNCTION 5 7 8 8 11 4 4,5 VS Positive Power Supply 2 4 4 3 4 11 12,13 GND Ground or Negative Power Supply 3 3 IN+ EQUIVALENT CIRCUIT Noninverting Input VS GND Circuit 1 4 2 IN- 1 6 OUT Inverting Input (Reference Circuit 1) Amplifier Output VS GND Circuit 2 3 1 1 3 3 INA+ Amplifier A Noninverting Input (Reference Circuit 1) 2 10 14 2 2 INA- Amplifier A Inverting Input (Reference Circuit 1) 1 9 13 1 1 OUTA Amplifier A Output (Reference Circuit 2) 5 5 7 5 6 INB+ Amplifier B Noninverting Input (Reference Circuit 1) 6 6 8 6 7 INB- Amplifier B Inverting Input (Reference Circuit 1) 7 7 9 7 8 OUTB Amplifier B Output (Reference Circuit 2) 10 11 INC+ Amplifier C Noninverting Input (Reference Circuit 1) 9 10 INC- Amplifier C Inverting Input (Reference Circuit 1) 8 9 OUTC Amplifier C Output (Reference Circuit 2) 12 14 IND+ Amplifier D Noninverting Input (Reference Circuit 1) 13 15 IND- Amplifier D Inverting Input (Reference Circuit 1) 14 EL5144, EL5146, EL5244, EL5246, EL5444 Pin Descriptions 5-PIN SOT23 (Continued) 8-PIN SO/PDIP/ 8-PIN MSOP SO/PDIP 16-PIN MSOP 14-PIN 14-PIN SO/PDIP SO/PDIP 14 8 16-PIN QSOP NAME 16 OUTD CE FUNCTION Amplifier D Output EQUIVALENT CIRCUIT (Reference Circuit 2) Enable (Enabled when high) VS + – 1.4V GND Circuit 3 1,5 2 3 CEA Enable Amplifier (Reference Circuit 3) A (Enabled when high) 4 5 CEB Enable Amplifier (Reference Circuit 3) B (Enabled when high) 2,6, 10,12 NC Description of Operation and Applications Information Product Description The EL5144 series is a family of wide bandwidth, single supply, low power, rail-to-rail output, voltage feedback operational amplifiers. The family includes single, dual, and quad configurations. The singles and duals are available with a power down pin to reduce power to 2.6µA typically. All the amplifiers are internally compensated for closed loop feedback gains of +1 or greater. Larger gains are acceptable but bandwidth will be reduced according to the familiar GainBandwidth Product. Connected in voltage follower mode and driving a high impedance load, the EL5144 series has a -3dB bandwidth of 100MHz. Driving a 150Ω load, they have a -3dB bandwidth of 60MHz while maintaining a 200V/µs slew rate. The input common mode voltage range includes ground while the output can swing rail to rail. Power Supply Bypassing and Printed Circuit Board Layout As with any high-frequency device, good printed circuit board layout is necessary for optimum performance. Ground plane construction is highly recommended. Lead lengths should be as short as possible. The power supply pin must be well bypassed to reduce the risk of oscillation For normal single supply operation, where the GND pin is connected to the ground plane, a single 4.7µF tantalum capacitor in parallel with a 0.1µF ceramic capacitor from VS to GND will 15 No Connect. Not internally connected. suffice. This same capacitor combination should be placed at each supply pin to ground if split supplies are to be used. In this case, the GND pin becomes the negative supply rail. For good AC performance, parasitic capacitance should be kept to a minimum. Use of wire wound resistors should be avoided because of their additional series inductance. Use of sockets, particularly for the SO package, should be avoided if possible. Sockets add parasitic inductance and capacitance that can result in compromised performance. Input, Output, and Supply Voltage Range The EL5144 series has been designed to operate with a single supply voltage of 5V. Split supplies can be used so long as their total range is 5V. The amplifiers have an input common mode voltage range that includes the negative supply (GND pin) and extends to within 1.5V of the positive supply (VS pin). They are specified over this range. The output of the EL5144 series amplifiers can swing rail to rail. As the load resistance becomes lower in value, the ability to drive close to each rail is reduced. However, even with an effective 150Ω load resistor connected to a voltage halfway between the supply rails, the output will swing to within 150mV of either rail. EL5144, EL5146, EL5244, EL5246, EL5444 Figure 1 shows the output of the EL5144 series amplifier swinging rail to rail with RF = 1kΩ, AV = +2 and RL = 1MΩ. Figure 2 is with RL = 150Ω. 5V 0V FIGURE 1. 5V Video Performance For good video signal integrity, an amplifier is required to maintain the same output impedance and the same frequency response as DC levels are changed at the output. This can be difficult when driving a standard video load of 150Ω, because of the change in output current with DC level. A look at the Differential Gain and Differential Phase curves for various supply and loading conditions will help you obtain optimal performance. Curves are provided for AV = +1 and +2, and RL = 150Ω and 10kΩ tied both to ground as well as 2.5V. As with all video amplifiers, there is a common mode sweet spot for optimum differential gain/differential phase. For example, with AV = +2 and RL = 150Ω tied to 2.5V, and the output common mode voltage kept between 0.8V and 3.2V, dG/dP is a very low 0.1%/0.1°. This condition corresponds to driving an AC-coupled, double terminated 75Ω coaxial cable. With AV = +1, RL = 150Ω tied to ground, and the video level kept between 0.85V and 2.95V, these amplifiers provide dG/dP performance of 0.05%/0.20°. This condition is representative of using the EL5144 series amplifier as a buffer driving a DC coupled, double terminated, 75Ω coaxial cable. Driving high impedance loads, such as signals on computer video cards, gives similar or better dG/dP performance as driving cables. Driving Cables and Capacitive Loads 0V FIGURE 2. Choice of Feedback Resistor, RF These amplifiers are optimized for applications that require a gain of +1. Hence, no feedback resistor is required. However, for gains greater than +1, the feedback resistor forms a pole with the input capacitance. As this pole becomes larger, phase margin is reduced. This causes ringing in the time domain and peaking in the frequency domain. Therefore, RF has some maximum value that should not be exceeded for optimum performance. If a large value of RF must be used, a small capacitor in the few picofarad range in parallel with RF can help to reduce this ringing and peaking at the expense of reducing the bandwidth. As far as the output stage of the amplifier is concerned, RF + RG appear in parallel with RL for gains other than +1. As this combination gets smaller, the bandwidth falls off. Consequently, RF also has a minimum value that should not be exceeded for optimum performance. For AV = +1, RF = 0Ω is optimum. For AV = -1 or +2 (noise gain of 2), optimum response is obtained with RF between 300Ω and 1kΩ. For AV = -4 or +5 (noise gain of 5), keep RF between 300Ω and 15kΩ. 16 The EL5144 series amplifiers can drive 50pF loads in parallel with 150Ω with 4dB of peaking and 100pF with 7dB of peaking. If less peaking is desired in these applications, a small series resistor (usually between 5Ω and 50Ω) can be placed in series with the output to eliminate most peaking. However, this will obviously reduce the gain slightly. If your gain is greater than 1, the gain resistor (RG) can then be chosen to make up for any gain loss which may be created by this additional resistor at the output. Another method of reducing peaking is to add a “snubber” circuit at the output. A snubber is a resistor in a series with a capacitor, 150Ω and 100pF being typical values. The advantage of a snubber is that it does not draw DC load current. When used as a cable driver, double termination is always recommended for reflection-free performance. For those applications, the back-termination series resistor will decouple the EL5144 series amplifier from the cable and allow extensive capacitive drive. However, other applications may have high capacitive loads without a back-termination resistor. Again, a small series resistor at the output can reduce peaking. Disable/Power-Down The EL5146 and EL5246 amplifiers can be disabled, placing its output in a high-impedance state. Turn off time is only 10ns and turn on time is around 500ns. When disabled, the amplifier’s supply current is reduced to 2.6µA typically, thereby effectively eliminating power consumption. The amplifier’s power down can be controlled by standard TTL or CMOS signal levels at the CE pin. The applied logic signal is EL5144, EL5146, EL5244, EL5246, EL5444 relative to the GND pin. Letting the CE pin float will enable the amplifier. Hence, the 8-pin PDIP and SOIC single amps are pin compatible with standard amplifiers that don’t have a power down feature. Short Circuit Current Limit The EL5144 series amplifiers do not have internal short circuit protection circuitry. Short circuit current of 90mA sourcing and 65mA sinking typically will flow if the output is trying to drive high or low but is shorted to half way between the rails. If an output is shorted indefinitely, the power dissipation could easily increase such that the part will be destroyed. Maximum reliability is maintained if the output current never exceeds ±50mA. This limit is set by internal metal interconnect limitations. Obviously, short circuit conditions must not remain or the internal metal connections will be destroyed. Power Dissipation With the high output drive capability of the EL5144 series amplifiers, it is possible to exceed the 150°C Absolute Maximum junction temperature under certain load current conditions. Therefore, it is important to calculate the maximum junction temperature for the application to determine if load conditions or package type need to be modified for the amplifier to remain in the safe operating area. The maximum power dissipation allowed in a package is determined according to: If we set the two PDMAX equations equal to each other, we can solve for RL: V OUT × ( V S - V OUT ) R L = -------------------------------------------------------------------------------------------- T JMAX - T AMAX --------------------------------------------- - ( V S × I SMAX ) N × θ JA Assuming worst case conditions of TA = +85°C, VOUT = VS/2V, VS = 5.5V, and ISMAX = 8.8mA per amplifier, below is a table of all packages and the minimum RL allowed. PART PACKAGE MINIMUM RL EL5144CW SOT23-5 37 EL5146CS SOIC-8 21 EL5146CN PDIP-8 14 EL5244CS SOIC-8 48 EL5244CN PDIP-8 30 EL5244CY MSOP-8 69 EL5246CY MSOP-10 69 EL5246CS SOIC-14 34 EL5246CN PDIP-14 23 EL5444CU QSOP-16 139 EL5444CS SOIC-14 85 EL5444CN PDIP-14 51 EL5144 Series Comparator Application T JMAX - T AMAX PD MAX = -------------------------------------------θ JA The EL5144 series amplifier can be used as a very fast, single supply comparator. Most op amps used as a comparator allow only slow speed operation because of output saturation issues. The EL5144 series amplifier doesn’t suffer from output saturation issues. Figure 3 shows the amplifier implemented as a comparator. Figure 4 is a where: TJMAX = Maximum junction temperature TAMAX = Maximum ambient temperature θJA = Thermal resistance of the package PDMAX = Maximum power dissipation in the package The maximum power dissipation actually produced by an IC is the total quiescent supply current times the total power supply voltage, plus the power in the IC due to the load, or: V OUT PD MAX = N × V S × I SMAX + ( V S - V OUT ) × ---------------R L where: N = Number of amplifiers in the package VS = Total supply voltage ISMAX = Maximum supply current per amplifier VOUT = Maximum output voltage of the application RL = Load resistance tied to ground 17 EL5144, EL5146, EL5244, EL5246, EL5444 graph of propagation delay vs. overdrive as a square wave is presented at the input of the comparator. directly together. Isolation resistors at each output are not necessary. +5V 1 VIN + – 2 3 VIN 1 3VPP 10MHz 8 EL5146 0.1µF 7 + 6 +2.5V 2 VOUT 14 + 3 RL 4 1 VOUT 13 12 EL5246 5 +5V 4 11 5 10 Select FIGURE 3. 6 VIN 2 2.4VPP 5MHz Propagation Delay vs. Overdrive for Amplifier Used as a Comparator + - 7 4.7µF 0.1µF 9 150Ω 8 1000 Propagation Delay (ns) FIGURE 5. 5V Negative Going Signal 100 VOUT Positive Going Signal 0V 10 0.01 0.1 1.0 Overdrive (V) 5V Select 0V FIGURE 4. FIGURE 6. Multiplexing with the EL5144 Series Amplifier Besides normal power down usage, the CE pin on the EL5146 and EL5246 series amplifiers also allow for multiplexing applications. Figure 5 shows an EL5246 with its outputs tied together, driving a back terminated 75Ω video load. A 3VP-P 10MHz sine wave is applied at Amp A input, and a 2.4VP-P 5MHz square wave to Amp B. Figure 6 shows the SELECT signal that is applied, and the resulting output waveform at VOUT. Observe the break-before-make operation of the multiplexing. Amp A is on and VIN1 is being passed through to the output of the amplifier. Then Amp A turns off in about 10ns. The output decays to ground with an RLCL time constants. 500ns later, Amp B turns on and VIN2 is passed through to the output. This break-before-make operation ensures that more than one amplifier isn’t trying to drive the bus at the same time. Notice the outputs are tied 18 Free Running Oscillator Application Figure 7 is an EL5144 configured as a free running oscillator. To first order, ROSC and COSC determine the frequency of oscillation according to: 0.72 F OSC = --------------------------------------R OSC × C OSC For rail to rail output swings, maximum frequency of oscillation is around 15MHz. If reduced output swings are acceptable, 25MHz can be achieved. Figure 8 shows the EL5144, EL5146, EL5244, EL5246, EL5444 oscillator for ROSC = 510Ω, COSC = 240pF and FOSC = 6MHz. 470K +5V 1 5 470K 0.1µF + 2 3 ROSC 4 470K COSC FIGURE 7. 5V VOUT 0V FIGURE 8. 5V 0V FIGURE 9. All Intersil U.S. products are manufactured, assembled and tested utilizing ISO9000 quality systems. Intersil Corporation’s quality certifications can be viewed at www.intersil.com/design/quality Intersil products are sold by description only. Intersil Corporation reserves the right to make changes in circuit design, software and/or specifications at any time without notice. Accordingly, the reader is cautioned to verify that data sheets are current before placing orders. Information furnished by Intersil is believed to be accurate and reliable. However, no responsibility is assumed by Intersil or its subsidiaries for its use; nor for any infringements of patents or other rights of third parties which may result from its use. No license is granted by implication or otherwise under any patent or patent rights of Intersil or its subsidiaries. For information regarding Intersil Corporation and its products, see www.intersil.com 19