AOSMD AOZ1282DI

AOZ1282DI
EZBuck™ 1.2A Simple Buck Regulator
General Description
Features
The AOZ1282DI is a high efficiency, simple to use, 1.2A
buck regulator flexible enough to be optimized for a
variety of applications. The AOZ1282DI works from a
4.5V to 36V input voltage range, and provides up to 1.2A
of continuous output current. The output voltage is
adjustable down to 0.8V. The fixed switching frequency
of 450kHz PWM operation reduces inductor size.
 4.5V to 36V operating input voltage range
 240mΩ internal NMOS
 Up to 95% efficiency
 Internal compensation
 1.2A continuous output current
 Fixed 450kHz PWM operation
 Internal soft start
 Output voltage adjustable down to 0.8V
 Cycle-by-cycle current limit
 Short-circuit protection
 Thermal shutdown
 Small size DFN2x2-8L
Applications
 Point of load DC/DC conversion
 Set top boxes and cable modems
 DVD drives and HDDs
 LCD Monitors & TVs
 Telecom/Networking/Datacom equipment
Typical Application
VIN
C3
C1
4.7µF
VIN
BS
EN
L1
AOZ1282DI
LX
VOUT
22µH
R1
GND
C2
10µF
FB
R2
Figure 1. 1.2A Buck Regulator
Rev. 0.6 September 2012
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Page 1 of 13
AOZ1282DI
Ordering Information
Part Number
Ambient Temperature Range
Package
Environmental
AOZ1282DI
-40 °C to +85 °C
DFN2x2-8L
Green Product
AOS Green Products use reduced levels of Halogens, and are also RoHS compliant.
Please visit www.aosmd.com/media/AOSGreenPolicy.pdf for additional information.
Pin Configuration
LX
1
VIN
2
8
BST
7
GND
EPAD
VIN
3
6
GND
EN
4
5
FB
DFN 2x2-8L
(Top View)
Pin Description
Pin Number
Pin Name
Pin Function
1
LX
PWM Output. Connect to inductor.
2, 3
VIN
Supply Voltage Input. Range from 4.5V to 36V. When VIN rises above the UVLO
threshold the device starts up.
4
EN
Enable Pin. The enable pin is active high. Connect EN pin to VIN through current limiting
resistor. Do not leave the EN pin floating.
5
FB
Feedback Input. It is regulated to 0.8V. The FB pin is used to determine the PWM output
voltage via a resistor divider between the output and GND.
6, 7
GND
Ground.
8
BST
Bootstrap Voltage Input. High side driver supply. Connected to 100nF capacitor between
BST and LX.
Exposed Pad
EPAD
Thermal Exposed Pad. Pad can be connected to GND if necessary for improved thermal
performance.
Rev. 0.6 September 2012
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Page 2 of 13
AOZ1282DI
Absolute Maximum Ratings
Recommended Operating Conditions
Exceeding the Absolute Maximum Ratings may damage the
device.
The device is not guaranteed to operate beyond the
Recommended Operating Conditions.
Parameter
Rating
Supply Voltage (VIN)
Parameter
40V
LX to GND
-0.7V to VVIN+ 0.3V
EN to GND
-0.3V to 40V
FB to GND
-0.3V to 6V
VLX + 6V
BST to GND
Junction Temperature (TJ)
+150°C
Storage Temperature (TS)
-65°C to +150°C
ESD Rating
(1)
2kV
Rating
Supply Voltage (VIN)
4.5V to 36V
Output Voltage (VOUT)
0.8V to VVIN
Ambient Temperature (TA)
-40°C to +85°C
(2)
Package Thermal Resistance (JA)
DFN 2x2-8L
55°C/W
Note:
2. The value of JA is measured with the device mounted on a 1-in2
FR-4 board with 2 oz. Copper, in a still air environment with
TA = 25 °C. The value in any given application depends on the
user’s specific board design.
Note:
1. Devices are inherently ESD sensitive, handling precautions are
required. Human body model rating: 1.5kΩ in series with 100pF.
Electrical Characteristics
TA = 25 °C, VIN = VEN = 12V, unless otherwise specified. Specifications in BOLD indicate a temperature range of -40°C to +85°C.
These specifications are guaranteed by design.
Symbol
VIN
VUVLO
Parameter
Conditions
Supply Voltage
Input Under-Voltage Lockout Threshold
Min.
4.5
VIN rising
VIN falling
Max.
36
V
V
V
260
Supply Current (Quiescent)
IOUT = 0, VFB = 1V, VEN > 1.2V
IOFF
Shutdown Supply Current
VEN = 0V
VFB
Feedback Voltage
TA = 25ºC
1
784
800
Units
2.9
2.3
UVLO Hysteresis
IIN
Typ.
mV
1.5
mA
8
A
816
mV
VFB_LOAD Load Regulation
120mA < Load < 1.08A
0.5
%
VFB_LINE
Line Regulation
Load = 600mA
0.03
%/V
Feedback Voltage Input Current
VFB = 800mV
500
nA
VEN_OFF
VEN_ON
EN Input Threshold
Off threshold
On threshold
VEN_HYS
EN Input Hysteresis
IEN
Enable Input Current
IFB
ENABLE
0.4
1.2
200
V
V
mV
3
A
540
kHz
MODULATOR
fO
DMAX
TON_MIN
ILIM
Frequency
450
Maximum Duty Cycle
87
%
Minimum On Time
150
ns
1.9
A
150
110
°C
°C
1.5
ms
Current Limit
Over-Temperature Shutdown Limit
TSS
360
1.5
TJ rising
TJ falling
Soft Start Interval
POWER STATE OUTPUT
ILEAKAGE
NMOS Leakage
VEN = 0V, VLX = 0V
RDS(ON)
NMOS On-Resistance
VIN = 12V
Rev. 0.6 September 2012
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10
420
A
mΩ
Page 3 of 13
AOZ1282DI
Block Diagram
VIN
Regulator
EN
Enable
Detect
Current
Sense
SoftStart
Ramp
Generator
OSC
BST
LDO
OC
CLK
FB
Driver
PWM
Logic
0.8V
Error
Amplifier
BST
LX
PWM
Comparator
GND
Rev. 0.6 September 2012
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Page 4 of 13
AOZ1282DI
Typical Performance Characteristics
Circuit of Figure 1. TA = 25°C, VIN = VEN = 12V, VOUT = 3.3 V, unless otherwise specified.
Full Load Operation
Light Load Operation
IN
Voltage
(500mV/div)
IN
Voltage
(1V/div)
OUT
Voltage
(100mV/div)
OUT
Voltage
(100mV/div)
LX
Voltage
(10V/div)
LX
Voltage
(10V/div)
LOAD
Current
(1A/div)
LOAD
Current
(1A/div)
2µs/div
2µs/div
Start Up to Full Load
Load Transient
IN
Voltage
(5V/div)
OUT
Voltage
(100mV/div)
OUT
Current
(1A/div)
OUT
Voltage
(2V/div)
OUT
Current
(1A/div)
5ms/div
200µs/div
Short Circuit Protection
Short Circuit Recovery
LX
Voltage
(10V/div)
LX
Voltage
(10V/div)
OUT
Voltage
(2V/div)
OUT
Voltage
(2V/div)
LOAD
Current
(1A/div)
2ms/div
2ms/div
Rev. 0.6 September 2012
LOAD
Current
(1A/div)
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Page 5 of 13
AOZ1282DI
Typical Performance Characteristics (continued)
Efficiency (Vo=5V)
vs. Load Current
Efficiency (Vo=3.3V)
vs. Load Current
100
100
95
5V–3.3V
90
85
Efficiency (%)
Efficiency (%)
90
24V–5V
80
75
70
65
85
80
70
55
55
0.2
0.4
0.6
0.8
Load Current (A)
1.0
1.2
18V–3.3V
65
60
0
24V–3.3V
75
60
50
12V–3.3V
95
12V–5V
18V–5V
50
0
0.2
0.4
0.6
0.8
Load Current (A)
1.0
1.2
Current Limit vs. Input Voltage
(Vo=3.3V)
2.0
Current Limit (A)
1.8
1.6
1.4
1.2
1.0
0.8
0.6
5
9
13
Rev. 0.6 September 2012
17
21
25
29
Input Voltage (V)
33
37
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Page 6 of 13
AOZ1282DI
Detailed Description
The AOZ1282DI is a current-mode step down regulator
with integrated high side NMOS switch. It operates from
a 4.5V to 36V input voltage range and supplies up to
1.2A of load current. Features include enable control,
under voltage lock-out, internal soft-start, output overvoltage protection, over-current protection and thermal
shut down.
The AOZ1282DI is available in DFN2x2-8L package.
Enable and Soft Start
The AOZ1282DI has internal soft start feature to limit inrush current and ensure the output voltage ramps up
smoothly to regulation voltage. A soft start process
begins when the input voltage rises to the voltage higher
than UVLO and voltage on EN pin is HIGH. In soft start
process, the output voltage is ramped to regulation
voltage in typically 400µs. The 400µs soft start time is set
internally.
The EN pin of the AOZ1282DI is active high. Connect the
EN pin to VIN if enable function is not used. Pull it to
ground will disable the AOZ1282DI. Do not leave it open.
The voltage on EN pin must be above 1.2 V to enable the
AOZ1282DI. When voltage on EN pin falls below 0.4V,
the AOZ1282DI is disabled.
Switching Frequency
The AOZ1282DI switching frequency is fixed and set by
an internal oscillator. The switching frequency is set
internally 450kHz.
Output Voltage Programming
Output voltage can be set by feeding back the output to
the FB pin with a resistor divider network. In the
application circuit shown in Figure 1. The resistor divider
network includes R1 and R2. Usually, a design is started
by picking a fixed R2 value and calculating the required
R1 with equation below.
R 1

V O = 0.8   1 + -------
R 2

Some standard values of R1 and R2 for the most
commonly used output voltage values are listed in
Table 1.
Vo (V)
R1 (kΩ)
R2 (kΩ)
1.8
80.6
64.2
2.5
49.9
23.4
3.3
49.9
15.8
5.0
49.9
9.53
Steady-State Operation
Under steady-state conditions, the converter operates in
fixed frequency and Continuous-Conduction Mode
(CCM).
The AOZ1282DI integrates an internal NMOS as the
high-side switch. Inductor current is sensed by amplifying
the voltage drop across the drain to source of the high
side power MOSFET. Output voltage is divided down by
the external voltage divider at the FB pin. The difference
of the FB pin voltage and reference is amplified by the
internal transconductance error amplifier. The error
voltage is compared against the current signal, which is
sum of inductor current signal and ramp compensation
signal, at PWM comparator input. If the current signal is
less than the error voltage, the internal high-side switch
is on. The inductor current flows from the input through
the inductor to the output. When the current signal
exceeds the error voltage, the high-side switch is off. The
inductor current is freewheeling through the external
Schottky diode to output.
Rev. 0.6 September 2012
Table 1.
The combination of R1 and R2 should be large enough to
avoid drawing excessive current from the output, which
will cause power loss.
Protection Features
The AOZ1282DI has multiple protection features to
prevent system circuit damage under abnormal
conditions.
Over Current Protection (OCP)
The sensed inductor current signal is also used for over
current protection.
The cycle by cycle current limit threshold is set normal
value of 1.9A. When the load current reaches the current
limit threshold, the cycle by cycle current limit circuit turns
off the high side switch immediately to terminate the
current duty cycle. The inductor current stop rising. The
cycle by cycle current limit protection directly limits
inductor peak current. The average inductor current is
also limited due to the limitation on peak inductor current.
When cycle by cycle current limit circuit is triggered, the
output voltage drops as the duty cycle decreasing.
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Page 7 of 13
AOZ1282DI
The AOZ1282DI has internal short circuit protection to
protect itself from catastrophic failure under output short
circuit conditions. The FB pin voltage is proportional to
the output voltage. Whenever FB pin voltage is below
0.2V, the short circuit protection circuit is triggered. As a
result, the converter is shut down and hiccups. The
converter will start up via a soft start once the short circuit
condition disappears. In short circuit protection mode, the
inductor average current is greatly reduced.
Under Voltage Lock Out (UVLO)
An UVLO circuit monitors the input voltage. When the
input voltage exceeds 2.9V, the converter starts
operation. When input voltage falls below 2.3V, the
converter will stop switching.
The relationship between the input capacitor RMS
current and voltage conversion ratio is calculated and
shown in Figure 2. It can be seen that when VO is half of
VIN, CIN is under the worst current stress. The worst
current stress on CIN is 0.5 x IO.
0.5
0.4
ICIN_RMS(m) 0.3
IO
0.2
0.1
Thermal Protection
0
An internal temperature sensor monitors the junction
temperature. It shuts down the internal control circuit and
high side NMOS if the junction temperature exceeds
150ºC. The regulator will restart automatically under the
control of soft-start circuit when the junction temperature
decreases to 110°C.
Application Information
The basic AOZ1282DI application circuit is shown in
Figure 1. Component selection is explained below.
Input Capacitor
The input capacitor must be connected to the VIN pin
and PGND pin of the AOZ1282DI to maintain steady
input voltage and filter out the pulsing input current. The
voltage rating of input capacitor must be greater than
maximum input voltage plus ripple voltage.
Since the input current is discontinuous in a buck
converter, the current stress on the input capacitor is
another concern when selecting the capacitor. For a buck
circuit, the RMS value of input capacitor current can be
calculated by:
VO
-------- = m
V IN
Rev. 0.6 September 2012
1
Figure 2. ICIN vs. Voltage Conversion Ratio
For reliable operation and best performance, the input
capacitors must have current rating higher than ICIN-RMS
at worst operating conditions. Ceramic capacitors are
preferred for input capacitors because of their low ESR
and high ripple current rating. Depending on the
application circuits, other low ESR tantalum capacitor or
aluminum electrolytic capacitor may also be used. When
selecting ceramic capacitors, X5R or X7R type dielectric
ceramic capacitors are preferred for their better
temperature and voltage characteristics. Note that the
ripple current rating from capacitor manufactures is
based on certain amount of life time. Further de-rating
may be necessary for practical design requirement.
The inductor is used to supply constant current to output
when it is driven by a switching voltage. For given input
and output voltage, inductance and switching frequency
together decide the inductor ripple current, which is:
VO  VO
IO

V IN = -----------------   1 – ---------  --------f  C IN 
V IN V IN
if we let m equal the conversion ratio:
0.5
m
Inductor
The input ripple voltage can be approximated by
equation below:
VO 
VO 
-  1 – --------
I CIN_RMS = I O  -------V IN 
V IN
0
VO 
VO 
-
I L = -----------   1 – -------fL 
V IN
The peak inductor current is:
I L
I Lpeak = I O + -------2
High inductance gives low inductor ripple current but
requires larger size inductor to avoid saturation. Low
ripple current reduces inductor core losses. It also
reduces RMS current through inductor and switches,
which results in less conduction loss.
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Page 8 of 13
AOZ1282DI
When selecting the inductor, make sure it is able to
handle the peak current without saturation even at the
highest operating temperature.
The inductor takes the highest current in a buck circuit.
The conduction loss on inductor needs to be checked for
thermal and efficiency requirements.
Surface mount inductors in different shape and styles are
available from Coilcraft, Elytone and Murata. Shielded
inductors are small and radiate less EMI noise. But they
cost more than unshielded inductors. The choice
depends on EMI requirement, price and size.
Output Capacitor
The output capacitor is selected based on the DC output
voltage rating, output ripple voltage specification and
ripple current rating.
The selected output capacitor must have a higher rated
voltage specification than the maximum desired output
voltage including ripple. De-rating needs to be
considered for long term reliability.
Output ripple voltage specification is another important
factor for selecting the output capacitor. In a buck
converter circuit, output ripple voltage is determined by
inductor value, switching frequency, output capacitor
value and ESR. It can be calculated by the equation
below:
1
V O = I L   ESR CO + -------------------------

8fC 
In a buck converter, output capacitor current is
continuous. The RMS current of output capacitor is
decided by the peak to peak inductor ripple current.
It can be calculated by:
I L
I CO_RMS = ---------12
Usually, the ripple current rating of the output capacitor is
a smaller issue because of the low current stress. When
the buck inductor is selected to be very small and
inductor ripple current is high, output capacitor could be
overstressed.
Schottky Diode Selection
The external freewheeling diode supplies the current to
the inductor when the high side NMOS switch is off. To
reduce the losses due to the forward voltage drop and
recovery of diode, Schottky diode is recommended to
use. The maximum reverse voltage rating of the chosen
Schottky diode should be greater than the maximum
input voltage, and the current rating should be greater
than the maximum load current.
Thermal Management and Layout
Consideration
O
where,
CO is output capacitor value, and
ESRCO is the equivalent series resistance of the output
capacitor.
When low ESR ceramic capacitor is used as output
capacitor, the impedance of the capacitor at the switching
frequency dominates. Output ripple is mainly caused by
capacitor value and inductor ripple current. The output
ripple voltage calculation can be simplified to:
1
V O = I L   -------------------------
8  f  C 
O
If the impedance of ESR at switching frequency
dominates, the output ripple voltage is mainly decided by
capacitor ESR and inductor ripple current. The output
ripple voltage calculation can be further simplified to:
V O = I L  ESR CO
For lower output ripple voltage across the entire
operating temperature range, X5R or X7R dielectric type
of ceramic, or other low ESR tantalum capacitor or
aluminum electrolytic capacitor may also be used as
output capacitors.
In the AOZ1282DI buck regulator circuit, high pulsing
current flows through two circuit loops. The first loop
starts from the input capacitors, to the VIN pin, to the LX
pins, to the filter inductor, to the output capacitor and
load, and then return to the input capacitor through
ground. Current flows in the first loop when the high side
switch is on. The second loop starts from inductor, to the
output capacitors and load, to the anode of Schottky
diode, to the cathode of Schottky diode. Current flows in
the second loop when the low side diode is on.
In PCB layout, minimizing the two loops area reduces the
noise of this circuit and improves efficiency. A ground
plane is strongly recommended to connect input
capacitor, output capacitor, and PGND pin of the
AOZ1282DI.
In the AOZ1282DI buck regulator circuit, the major power
dissipating components are the AOZ1282DI, the
Schottky diode and output inductor. The total power
dissipation of converter circuit can be measured by input
power minus output power.
P total_loss =  V IN  I IN  –  V O  V IN 
Rev. 0.6 September 2012
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Page 9 of 13
AOZ1282DI
The power dissipation in Schottky can be approximated
as:
Several layout tips are listed below for the best electric
and thermal performance.
P diode_loss = I O   1 – D   V FW_Schottky
1. The input capacitor should be connected as close as
possible to the VIN pin and the GND pin.
where,
2. The inductor should be placed as close as possible
to the LX pin and the output capacitor.
VFW_Schottky is the Schottky diode forward voltage drop.
The power dissipation of inductor can be approximately
calculated by output current and DCR of inductor.
P inductor_loss = IO2  R inductor  1.1
4. Place the feedback resistors and compensation
components as close to the chip as possible.
The actual junction temperature can be calculated with
power dissipation in the AOZ1282DI and thermal
impedance from junction to ambient.
T
3. Keep the connection of the schottky diode between
the LX pin and the GND pin as short and wide
as possible.
P
–P
–P

total_loss diode_loss inductor_loss
= -------------------------------------------------------------------------------------------------------------------------junction

+T
JA
ambient
5. Keep sensitive signal traces away from the LX pin.
6. Pour a maximized copper area to the VIN pin, the
LX pin and especially the GND pin to help thermal
dissipation.
7. Pour a copper plane on all unused board area and
connect the plane to stable DC nodes, like VIN,
GND or VOUT.
The maximum junction temperature of AOZ1282DI is
150ºC, which limits the maximum load current capability.
The thermal performance of the AOZ1282DI is strongly
affected by the PCB layout. Extra care should be taken
by users during design process to ensure that the IC will
operate under the recommended environmental
conditions.
Rev. 0.6 September 2012
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Page 10 of 13
AOZ1282DI
Package Dimensions, DFN2x2-8L
B
D
C A B
bbb
A
8
b
e
8
R
aaa C
2x
E
Pin#1 Identification
Option 1
E1
L
1
D1
1
a a a C 2x
BOTTOM VIEW
TOP VIEW
8
ccc C
A C
C
A1
ddd C
Pin#1 Identification
Option 2
seating
plan
SIDE VIEW
Chamfer 0.2x45°
1
BOTTOM VIEW
RECOMMENDED LAND PATTERN
0.50
Dimensions in millimeters
0.25
0.25
0.85
0.90
1.70
0.30
1.50
UNIT: mm
Symbols
A
A1
b
c
D
D1
E
E1
e
Min.
0.70
0.00
0.18
L
R
aaa
bbb
ccc
ddd
0.20
1.90
1.35
1.90
0.75
Nom.
0.75
0.02
0.25
0.20 REF
2.00
1.50
2.00
0.90
0.50 BSC
Max.
0.80
0.05
0.30
0.30
0.20
0.15
0.10
0.10
0.08
0.40
2.10
1.60
2.10
1.00
Dimensions in inches
Symbols
A
A1
b
c
D
D1
E
E1
e
Min.
0.028
0.000
0.007
Nom. Max.
0.030 0.031
0.001 0.002
0.010 0.012
0.008 REF
0.075 0.079 0.083
0.053 0.059 0.063
0.075 0.079 0.083
0.030 0.035 0.039
0.020 BSC
L
R
aaa
bbb
ccc
ddd
0.008
0.012
0.008
0.006
0.004
0.004
0.003
0.016
Notes:
1. Dimensioning and tolerancing conform to ASME Y14.5M-1994.
2. Controlling dimension is in millimeter, converted inch dimensions are not necessarily exact.
3. Dimension b applies to matellized terminal and is measured between 0.10mm and 0.30mm from the terminal tip.
If the terminal has the optional radius on the other end of the terminal, the dimension b should not be measured
in that radius area.
4. Coplanarity ddd applies to the terminals and all other bottom surface metallization.
Rev. 0.6 September 2012
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Page 11 of 13
AOZ1282DI
Tape and Reel Dimensions, DFN2x2-8L
P1
Carrier Tape
T
P2
D1
E1
E2
E
B0
K0
P0
D0
A0
Feeding Direction
UNIT: mm
Package
A0
B0
K0
D0
DFN 2x2
(8mm)
2.30
0.20
2.30
0.20
1.00
±0.20
1.00
MIN.
D1
E
E1
1.50
8.00
1.75
+0.10/-0 +0.30/-0.10 ±0.10
Reel
E2
P0
P1
P2
T
3.50
±0.05
4.00
±0.20
4.00
±0.20
2.00
±0.05
0.30
±0.05
W1
S
G
N
M
K
V
R
H
W
UNIT: mm
Tape Size Reel Size
8mm
ø178
M
ø178.0
±1.0
N
70.5
±1.0
W
9.0
±0.5
W1
11.8
±1.1
H
ø13.0
+0.5/-0.2
K
10.25
±0.1
S
2.4
±0.1
G
ø9.8
R
N/A
V
N/A
Leader / Trailer
& Orientation
Trailer Tape
300mm Min. OR
75 Empty Pockets
Rev. 0.6 September 2012
Components Tape
Orientation in Pocket
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Leader Tape
500mm Min. OR
125 Empty Pockets
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AOZ1282DI
Part Marking
AOZ1282DI
(2x2 DFN)
Part Number Code
AF1A
9B12
Assembly Location Code
Option Code
Assembly Lot Code
Year Code
Week Code
This data sheet contains preliminary data; supplementary data may be published at a later date.
Alpha & Omega Semiconductor reserves the right to make changes at any time without notice.
LIFE SUPPORT POLICY
ALPHA & OMEGA SEMICONDUCTOR PRODUCTS ARE NOT AUTHORIZED FOR USE AS CRITICAL
COMPONENTS IN LIFE SUPPORT DEVICES OR SYSTEMS.
As used herein:
1. Life support devices or systems are devices or
systems which, (a) are intended for surgical implant into
the body or (b) support or sustain life, and (c) whose
failure to perform when properly used in accordance
with instructions for use provided in the labeling, can be
reasonably expected to result in a significant injury of
the user.
Rev. 0.6 September 2012
2. A critical component in any component of a life
support, device, or system whose failure to perform can
be reasonably expected to cause the failure of the life
support device or system, or to affect its safety or
effectiveness.
www.aosmd.com
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