ACS710
120 kHz Bandwidth, High Voltage Isolation
Current Sensor with Integrated Overcurrent Detection
Features and Benefits
Description
▪ Industry-leading noise performance with greatly improved
bandwidth through proprietary amplifier and filter design
techniques
▪ Small footprint package suitable for space-constrained
applications
▪ 1 mΩ primary conductor resistance for low power loss
▪ High isolation voltage, suitable for line-powered
applications
▪ User-adjustable Overcurrent Fault level
▪ Overcurrent Fault signal typically responds to an
overcurrent condition in < 2 μs
▪ Integrated shield virtually eliminates capacitive coupling
from current conductor to die due to high dV/dt voltage
transients
▪ Filter pin capacitor improves resolution in low bandwidth
applications
▪ 3 to 5.5 V, single supply operation
▪ Factory trimmed sensitivity and quiescent output voltage
▪ Chopper stabilization results in extremely stable quiescent
output voltage
▪ Ratiometric output from supply voltage
The Allegro® ACS710 current sensor provides economical and
precise means for current sensing applications in industrial,
commercial, and communications systems. The device is offered
in a small footprint surface mount package that allows easy
implementation in customer applications.
Package: 16-pin SOIC Hall Effect IC
Package (suffix LA)
The ACS710 consists of a precision linear Hall sensor integrated
circuit with a copper conduction path located near the surface
of the silicon die. Applied current flows through the copper
conduction path, and the analog output voltage from the Hall
sensor linearly tracks the magnetic field generated by the
applied current. The accuracy of the ACS710 is maximized
with this patented packaging configuration because the Hall
element is situated in extremely close proximity to the current
to be measured.
High level immunity to current conductor dV/dt and stray
electric fields, offered by Allegro proprietary integrated shield
technology, results in low ripple on the output and low offset
drift in high-side, high voltage applications.
The voltage on the Overcurrent Input (VOC pin) allows
customers to define an overcurrent fault threshold for the device.
When the current flowing through the copper conduction path
(between the IP+ and IP– pins) exceeds this threshold, the open
drain Overcurrent Fault pin will transition to a logic low state.
Factory programming of the linear Hall sensor inside of the
ACS710 results in exceptional accuracy in both analog and
digital output signals.
The internal resistance of the copper path used for current
sensing is typically 1 mΩ, for low power loss. Also, the current
conduction path is electrically isolated from the low voltage
Approximate Scale 1:1
Continued on the next page…
Typical Application Circuit
1
2
3
4
IP
5
6
7
8
IP+
IP+
IP+
FAULT_EN
ACS710
VOC
VCC
IP+
FAULT
IP–
VIOUT
IP–
FILTER
IP–
VZCR
IP–
GND
ACS710-DS, Rev. 8
16 Fault_EN
RH
VCC
RH, RL
15
14
12
11
RPU
COC
COC
0.1 μF
B
CF
1 nF
A
Noise and bandwidth limiting filter capacitor
Fault delay setting capacitor, 22 nF maximum
A
Use of capacitor required
B
Use of resistor optional, 330 kΩ recommended.
If used, resistor must be connected between
¯F
¯¯A¯U¯¯L¯¯T
¯ pin and VCC.
VIOUT
10
9
CF
RL
13
Sets resistor divider reference for VOC
120 kHz Bandwidth, High Voltage Isolation
Current Sensor with Integrated Overcurrent Detection
ACS710
Description (continued)
sensor inputs and outputs. This allows the ACS710 family of sensors
to be used in applications requiring electrical isolation, without the
use of opto-isolators or other costly isolation techniques.
Pb-based solder balls, currently exempt from RoHS. The device is
fully calibrated prior to shipment from the factory.
The ACS710 is provided in a small, surface mount SOIC16 package.
The leadframe is plated with 100% matte tin, which is compatible
with standard lead (Pb) free printed circuit board assembly processes.
Internally, the device is Pb-free, except for flip-chip high-temperature
Applications include:
• Motor control and protection
• Load management and overcurrent detection
• Power conversion and battery monitoring / UPS systems
Selection Guide
Part Number
IP
(A)
Sens (typ)
at VCC = 5 V
(mV/A)
ACS710KLATR-6BB-T2,3
±6
151
ACS710KLATR-12CB-T2
±12.5
56
ACS710KLATR-25CB-T2
±25
28
ACS710KLATR-6BB-NL-T2,3
±6
151
ACS710KLATR-12CB-NL-T2
±12.5
56
ACS710KLATR-25CB-NL-T2
±25
28
Latched
Fault
TA
(°C)
Yes
–40 to 125
Tape and Reel, 1000 pieces per reel
No
–40 to 125
Tape and Reel, 1000 pieces per reel
Packing1
1 Contact Allegro
for packing options.
2Variant not intended for automotive applications.
3The formerly offered V
CC = 3.3 V version of the IP = ±6 A variant (formerly the ACS710KLATR-6BB-T) is now offered as the ACS716KLATR6BB-T. For additional information, please refer to the ACS716 datasheet.
Allegro MicroSystems, LLC
115 Northeast Cutoff
Worcester, Massachusetts 01615-0036 U.S.A.
1.508.853.5000; www.allegromicro.com
2
ACS710
120 kHz Bandwidth, High Voltage Isolation
Current Sensor with Integrated Overcurrent Detection
Absolute Maximum Ratings
Characteristic
Symbol
Supply Voltage
Notes
Rating
Unit
VCC
8
V
Filter Pin
VFILTER
8
V
Analog Output Pin
VIOUT
32
V
VOC
8
V
Overcurrent Input Pin
¯¯A¯U¯¯L¯¯T
¯ Pin
Overcurrent ¯F
V ¯F¯¯A¯U¯¯L¯¯T¯
8
V
Fault Enable (FAULT_EN) Pin
VFAULTEN
8
V
Voltage Reference Output Pin
VZCR
8
V
DC Reverse Voltage: VCC, FILTER, VIOUT, VOC,
¯F
¯¯A¯U¯¯L¯¯T
¯, FAULT_EN, and VZCR Pins
VRdcx
–0.5
V
Excess to Supply Voltage: FILTER, VIOUT, VOC,
¯F
¯¯A¯U¯¯L¯¯T
¯, FAULT_EN, and VZCR Pins
VEX
0.3
V
IIOUT(Source)
3
mA
IIOUT(Sink)
1
mA
–40 to 125
°C
Output Current Source
Output Current Sink
Operating Ambient Temperature
TA
Voltage by which pin voltage can exceed the VCC pin
voltage
Range K
Junction Temperature
TJ(max)
165
°C
Storage Temperature
Tstg
–65 to 170
°C
Isolation Characteristics
Characteristic
Symbol
Notes
Dielectric Strength Test Voltage*
VISO
Agency type-tested for 60 seconds per
UL standard 1577
Working Voltage for Basic Isolation
VWFSI
For basic (single) isolation per UL standard 1577;
for higher continuous voltage ratings, please contact
Allegro
Rating
Unit
3000
VAC
277
VAC
* Allegro does not conduct 60-second testing. It is done only during the UL certification process.
Thermal Characteristics
Characteristic
Package Thermal Resistance
Symbol
RθJA
Test Conditions
Value
Unit
When mounted on Allegro demo board with 1332 mm2 (654 mm2 on component side and 678 mm2 on opposite side) of 2 oz. copper connected to
the primary leadframe and with thermal vias connecting the copper layers.
Performance is based on current flowing through the primary leadframe and
includes the power consumed by the PCB.
17
ºC/W
Allegro MicroSystems, LLC
115 Northeast Cutoff
Worcester, Massachusetts 01615-0036 U.S.A.
1.508.853.5000; www.allegromicro.com
3
120 kHz Bandwidth, High Voltage Isolation
Current Sensor with Integrated Overcurrent Detection
ACS710
Functional Block Diagram
Latching Version
VCC
Hall
Bias
FAULT_EN
D
Q
CLK
R
POR
POR
Fault Latch
FAULT Reset
Drain
–
VOC
+
2VREF
OC Fault
Control
Logic
FAULT
3 mA
Fault
Comparator
–
Sensitivity
Trim
VZCR
+
IP+
VIOUT
Signal
Recovery
RF(INT)
Hall
Amplifier
IP–
VOUT(Q)
Trim
GND
FILTER
Terminal List Table, Latching Version
Number
Pin-out Diagram
IP+ 1
16 FAULT_EN
IP+ 2
15 VOC
IP+ 3
14 VCC
IP+ 4
13 FAULT
IP– 5
12 VIOUT
IP– 6
11 FILTER
IP– 7
10 VZCR
IP– 8
9 GND
Name
Description
1 through 4
IP+
Sensed current copper conduction path pins. Terminals for current being sensed;
fused internally, loop to IP– pins; unidirectional or bidirectional current flow.
5 through 8
IP–
Sensed current copper conduction path pins. Terminals for current being sensed;
fused internally, loop to IP+ pins; unidirectional or bidirectional current flow.
9
GND
Device ground connection.
10
VZCR
Voltage Reference Output pin. Zero current (0 A) reference; output voltage on this
pin scales with VCC . (Not a highly accurate reference.)
11
FILTER
Filter pin. Terminal for an external capacitor connected from this pin to GND to set
the device bandwidth.
12
VIOUT
Analog Output pin. Output voltage on this pin is proportional to current flowing
through the loop between the IP+ pins and IP– pins.
13
¯F
¯¯A¯U¯¯L¯¯T
¯
Overcurrent Fault pin. When current flowing between IP+ pins and IP– pins
exceeds the overcurrent fault threshold, this pin transitions to a logic low state.
14
VCC
Supply voltage.
15
VOC
Overcurrent Input pin. Analog input voltage on this pin sets the overcurrent fault
threshold.
16
¯¯A¯U¯¯L¯¯T
¯ when low.
FAULT_EN Enables overcurrent faulting when high. Resets ¯F
Allegro MicroSystems, LLC
115 Northeast Cutoff
Worcester, Massachusetts 01615-0036 U.S.A.
1.508.853.5000; www.allegromicro.com
4
120 kHz Bandwidth, High Voltage Isolation
Current Sensor with Integrated Overcurrent Detection
ACS710
Functional Block Diagram
Non-Latching Version
VCC
Hall
Bias
POR
Drain
–
VOC
+
FAULT_EN
FAULT
2VREF
FAULT Reset
3 mA
OC Fault
VZCR
Fault
Comparator
Sensitivity
Trim
IP+
VIOUT
Signal
Recovery
RF(INT)
Hall
Amplifier
IP–
VOUT(Q)
Trim
GND
FILTER
Terminal List Table, Non-Latching Version
Number
Pin-out Diagram
IP+ 1
16 FAULT_EN
IP+ 2
15 VOC
IP+ 3
14 VCC
IP+ 4
13 FAULT
IP– 5
12 VIOUT
IP– 6
11 FILTER
IP– 7
10 VZCR
IP– 8
9 GND
Name
Description
1 through 4
IP+
Sensed current copper conduction path pins. Terminals for current being sensed;
fused internally, loop to IP– pins; unidirectional or bidirectional current flow.
5 through 8
IP–
Sensed current copper conduction path pins. Terminals for current being sensed;
fused internally, loop to IP+ pins; unidirectional or bidirectional current flow.
9
GND
Device ground connection.
10
VZCR
Voltage Reference Output pin. Zero current (0 A) reference; output voltage on this
pin scales with VCC . (Not a highly accurate reference.)
11
FILTER
Filter pin. Terminal for an external capacitor connected from this pin to GND to set
the device bandwidth.
12
VIOUT
Analog Output pin. Output voltage on this pin is proportional to current flowing
through the loop between the IP+ pins and IP– pins.
13
¯F
¯¯A¯U¯¯L¯¯T
¯
Overcurrent Fault pin. When current flowing between IP+ pins and IP– pins
exceeds the overcurrent fault threshold, this pin transitions to a logic low state.
14
VCC
Supply voltage.
15
VOC
Overcurrent Input pin. Analog input voltage on this pin sets the overcurrent fault
threshold.
16
FAULT_EN Enables overcurrent faulting when high.
Allegro MicroSystems, LLC
115 Northeast Cutoff
Worcester, Massachusetts 01615-0036 U.S.A.
1.508.853.5000; www.allegromicro.com
5
ACS710
120 kHz Bandwidth, High Voltage Isolation
Current Sensor with Integrated Overcurrent Detection
COMMON OPERATING CHARACTERISTICS Valid at TA = –40°C to 125°C, VCC = 5 V, unless otherwise specified
Characteristic
ELECTRICAL CHARACTERISTICS
Supply Voltage1
Nominal Supply Voltage
Supply Current
Output Capacitance Load
Output Resistive Load
Magnetic Coupling from Device Conductor
to Hall Element
Internal Filter Resistance2
Symbol
Test Conditions
Min.
Typ.
Max.
Units
3
–
–
5
5.5
–
V
V
¯¯A¯U¯¯L¯¯T
¯ pin high
VIOUT open, ¯F
VIOUT pin to GND
VIOUT pin to GND
–
–
10
11
–
–
14.5
10
–
mA
nF
kΩ
Current flowing from IP+ to IP– pins
–
9.5
–
G/A
VCC
VCCN
ICC
CLOAD
RLOAD
MCHALL
–
1.7
–
kΩ
Primary Conductor Resistance
RPRIMARY
ANALOG OUTPUT SIGNAL CHARACTERISTICS
Full Range Linearity3
ELIN
Symmetry4
ESYM
TA = 25°C
–
1
–
mΩ
IP = ±IP0A
IP = ±IP0A
–0.75
99.1
±0.25
100
0.75
100.9
%
%
Bidirectional Quiescent Output
VOUT(QBI)
TIMING PERFORMANCE CHARACTERISTICS
IP = 0 A, TA = 25°C
–
VCC×0.5
–
V
–
3
–
μs
–
1
–
μs
–
4
–
μs
–
120
–
kHz
–
35
–
μs
VOC
VCC×0.25
–
VCC×0.4
V
INCOMP
–
±1
–
A
Switchpoint in VOC safe operating area;
assumes INCOMP = 0 A
–
±5
–
%
¯¯A¯U¯¯L¯¯T
¯ pin
1 mA sink current at ¯F
–
–
0.4
V
VIOUT Signal Rise Time
VIOUT Signal Propagation Time
RF(INT)
tr
tPROP
VIOUT Signal Response Time
tRESPONSE
VIOUT Large Signal Bandwidth
f3dB
Power-On Time
tPO
OVERCURRENT CHARACTERISTICS
Setting Voltage for Overcurrent Switchpoint5
Signal Noise at Overcurrent
Comparator Input
Overcurrent Fault Switchpoint Error6,7
EOC
¯¯A¯U¯¯L¯¯T
¯ Pin Output Voltage
Overcurrent ¯F
V ¯F¯¯A¯U¯¯L¯¯T¯
TA = 25°C, Swing IP from 0 A to IP0A,
no capacitor on FILTER pin, 100 pF from
VIOUT to GND
TA = 25°C, no capacitor on FILTER pin,
100 pF from VIOUT to GND
TA = 25°C, Swing IP from 0 A to IP0A,
no capacitor on FILTER pin, 100 pF from
VIOUT to GND
–3 dB, Apply IP such that VIOUT = 1 Vpk-pk,
no capacitor on FILTER pin, 100 pF from
VIOUT to GND
Output reaches 90% of steady-state level,
no capacitor on FILTER pin, TA = 25°C
Fault Enable (FAULT_EN Pin) Input Low
Voltage Threshold
VIL
–
–
0.1 × VCC
V
Fault Enable (FAULT_EN Pin) Input High
Voltage Threshold
VIH
0.8 × VCC
–
–
V
Fault Enable (FAULT_EN Pin) Input
Resistance
RFEI
–
1
–
MΩ
Continued on the next page…
Allegro MicroSystems, LLC
115 Northeast Cutoff
Worcester, Massachusetts 01615-0036 U.S.A.
1.508.853.5000; www.allegromicro.com
6
ACS710
120 kHz Bandwidth, High Voltage Isolation
Current Sensor with Integrated Overcurrent Detection
COMMON OPERATING CHARACTERISTICS (continued) Valid at TA = –40°C to 125°C, VCC = 5 V, unless otherwise specified
Characteristic
Symbol
OVERCURRENT CHARACTERISTICS (continued)
Fault Enable (FAULT_EN Pin) Delay8
tFED
Fault Enable (FAULT_EN Pin) Delay
(Non-Latching versions)9
tFED(NL)
Overcurrent Fault Response Time
tOC
Undercurrent Fault Response Time
(Non-Latching versions)
tUC
Overcurrent Fault Reset Delay
tOCR
Overcurrent Fault Reset Hold Time
tOCH
Overcurrent Input Pin Resistance
VOLTAGE REFERENCE CHARACTERISTICS
ROC
Voltage Reference Output
VZCR
Voltage Reference Output Load Current
IZCR
Voltage Reference Output Drift
∆VZCR
Test Conditions
Set FAULT_EN to low, VOC = 0.25 × VCC ,
COC = 0 F; then run a DC IP exceeding the
corresponding overcurrent threshold; then
reset FAULT_EN from low to high and
measure the delay from the rising edge of
¯¯A¯U¯¯L¯¯T
¯
FAULT_EN to the falling edge of ¯F
Set FAULT_EN to low, VOC = 0.25 × VCC ,
COC = 0 F; then run a DC IP exceeding the
corresponding overcurrent threshold; then
reset FAULT_EN from low to high and
measure the delay from the rising edge of
¯¯A¯U¯¯L¯¯T
¯
FAULT_EN to the falling edge of ¯F
FAULT_EN set to high for a minimum
of 20 μs before the overcurrent event;
switchpoint set at VOC = 0.25 × VCC ;
delay from IP exceeding overcurrent
fault threshold to V ¯F¯¯A¯U¯¯L¯¯T¯ < 0.4 V, without
external COC capacitor
FAULT_EN set to high for a minimum
of 20 μs before the undercurrent event;
switchpoint set at VOC = 0.25 × VCC ; delay
from IP falling below the overcurrent fault
threshold to V ¯F¯¯A¯U¯¯L¯¯T¯ > 0.8 × VCC , without
external COC capacitor, RPU = 330 kΩ
Time from VFAULTEN < VIL to
V ¯F¯¯A¯U¯¯L¯¯T¯ > 0.8 × VCC , RPU = 330 kΩ
Time from VFAULTEN <VIL to rising edge of
V ¯F¯¯A¯U¯¯L¯¯T¯
TA = 25°C, VOC pin to GND
TA = 25 °C
(Not a highly accurate reference)
Source current
Sink current
Min.
Typ.
Max.
Units
–
15
–
μs
–
150
–
ns
–
1.9
–
μs
–
3
–
μs
–
500
–
ns
–
250
–
ns
2
–
–
MΩ
0.48 x VCC
0.5 × VCC
0.51 x VCC
V
3
50
–
–
–
±10
–
–
–
mA
μA
mV
1Devices
are programmed for maximum accuracy at VCC = 5 V. The device contains ratiometry circuits that accurately alter the 0 A Output Voltage and
Sensitivity level of the device in proportion to the applied VCC level. However, as a result of minor nonlinearities in the ratiometry circuit, additional output
error will result when VCC varies from the VCC level at which the device was programmed. Customers that plan to operate the device at a VCC level other
than the VCC level at which the device was programmed should contact their local Allegro sales representative regarding expected device accuracy levels
under these bias conditions.
2R
F(INT) forms an RC circuit via the FILTER pin.
3This parameter can drift by as much as 0.8% over the lifetime of this product.
4This parameter can drift by as much as 1% over the lifetime of this product.
5See page 8 on how to set overcurrent fault switchpoint.
6Switchpoint can be lower at the expense of switchpoint accuracy.
7This error specification does not include the effect of noise. See the I
NCOMP specification in order to factor in the additional influence of noise on the
fault switchpoint.
8Fault Enable Delay is designed to avoid false tripping of an Overcurrent (OC) fault at power-up. A 15 μs (typical) delay will always be needed, every
time FAULT_EN is raised from low to high, before the device is ready for responding to any overcurrent event.
9During power-up, this delay is 15 μs in order to avoid false tripping of an Overcurrent (OC) fault.
Allegro MicroSystems, LLC
115 Northeast Cutoff
Worcester, Massachusetts 01615-0036 U.S.A.
1.508.853.5000; www.allegromicro.com
7
120 kHz Bandwidth, High Voltage Isolation
Current Sensor with Integrated Overcurrent Detection
ACS710
PERFORMANCE CHARACTERISTICS, TA Range K, valid at TA = – 40°C to 125°C, VCC = 5 V, unless otherwise specified
Characteristic
Symbol
Test Conditions
Min.
Typ.
Max.
Units
X6BB CHARACTERISTICS
Optimized Accuracy Range1
Linear Sensing Range
Noise2
IPOA
–7.5
–
7.5
A
IR
–14
–
14
A
VNOISE(rms) TA = 25°C, Sens = 100 mV/A, Cf = 0, CLOAD = 4.7 nF, RLOAD open
Sensitivity3
–
4.05
–
mV
IP = 6.5 A, TA = 25°C
–
151
–
mV/A
IP = 6.5 A, TA = 25°C to 125°C
–
151
–
mV/A
IP = 6.5 A, TA = – 40°C to 25°C
–
152
–
mV/A
IP = 0 A, TA = 25°C
–
±10
–
mV
IP = 0 A, TA = 25°C to 125°C
–
±11
–
mV
IP = 0 A, TA = – 40°C to 25°C
–
±40
–
mV
Over full scale of IPOA, IP applied for 5 ms, TA = 25°C to 125°C
–
±1.6
–
%
Over full scale of IPOA, IP applied for 5 ms, TA = – 40°C to 25°C
–
±5.6
–
%
IPOA
–12.5
–
12.5
A
IR
–37.5
–
37.5
A
–
1.50
–
mV
Sens
Electrical Offset Voltage
Variation Relative to
VOUT(QBI)4
VOE
Total Output Error5
ETOT
X12CB CHARACTERISTICS
Optimized Accuracy Range1
Linear Sensing Range
Noise2
Sensitivity3
VNOISE(rms) TA = 25°C, Sens = 56 mV/A, Cf = 0, CLOAD = 4.7 nF, RLOAD open
Sens
Electrical Offset Voltage
Variation Relative to
VOUT(QBI)4
VOE
Total Output Error5
ETOT
IP = 12.5 A, TA = 25°C
–
56
–
mV/A
IP = 12.5 A, TA = 25°C to 125°C
–
56
–
mV/A
IP = 12.5 A, TA = – 40°C to 25°C
–
57
–
mV/A
IP = 0 A, TA = 25°C
–
±4
–
mV
IP = 0 A, TA = 25°C to 125°C
–
±14
–
mV
IP = 0 A, TA = – 40°C to 25°C
–
±23
–
mV
Over full scale of IPOA, IP applied for 5 ms, TA = 25°C to 125°C
–
±2.2
–
%
Over full scale of IPOA, IP applied for 5 ms, TA = – 40°C to 25°C
–
±3.9
–
%
Continued on the next page…
Allegro MicroSystems, LLC
115 Northeast Cutoff
Worcester, Massachusetts 01615-0036 U.S.A.
1.508.853.5000; www.allegromicro.com
8
120 kHz Bandwidth, High Voltage Isolation
Current Sensor with Integrated Overcurrent Detection
ACS710
PERFORMANCE CHARACTERISTICS (continued), TA Range K, valid at TA = – 40°C to 125°C, VCC = 5 V, unless otherwise specified
X25CB CHARACTERISTICS
Optimized Accuracy Range1
Linear Sensing Range
Noise2
Sensitivity3
IPOA
–25
IR
VNOISE(rms) TA = 25°C, Sens = 28 mV/A, Cf = 0, CLOAD = 4.7 nF, RLOAD open
Sens
Electrical Offset Voltage
Variation Relative to
VOUT(QBI)4
VOE
Total Output Error5
ETOT
–
25
A
–75
–
75
A
–
1
–
mV
IP = 25 A, TA = 25°C
–
28
–
mV/A
IP = 25 A, TA = 25°C to 125°C
–
27.9
–
mV/A
IP = 25 A, TA = – 40°C to 25°C
–
28.5
–
mV/A
IP = 0 A, TA = 25°C
–
±3
–
mV
IP = 0 A, TA = 25°C to 125°C
–
±12
–
mV
IP = 0 A, TA = – 40°C to 25°C
–
±18
–
mV
Over full scale of IPOA, IP applied for 5 ms, TA = 25°C to 125°C
–
±2.9
–
%
Over full scale of IPOA, IP applied for 5 ms, TA = – 40°C to 25°C
–
±5.2
–
%
1Although
the device is accurate over the entire linear range, the device is programmed for maximum accuracy over the range defined by IPOA .
The reason for this is that in many applications, such as motor control, the start-up current of the motor is approximately three times higher than the
running current.
2V
pk-pk noise (6 sigma noise) is equal to 6 × VNOISE(rms). Lower noise levels than this can be achieved by using Cf for applications requiring narrower
bandwidth. See Characteristic Performance page for graphs of noise versus Cf and bandwidth versus Cf.
3This parameter can drift by as much as 2.4% over the lifetime of this product.
4This parameter can drift by as much as 13 mV over the lifetime of this product.
5This parameter can drift by as much as 2.5% over the lifetime of this product.
Allegro MicroSystems, LLC
115 Northeast Cutoff
Worcester, Massachusetts 01615-0036 U.S.A.
1.508.853.5000; www.allegromicro.com
9
120 kHz Bandwidth, High Voltage Isolation
Current Sensor with Integrated Overcurrent Detection
ACS710
Characteristic Performance
ACS710 Bandwidth versus External Capacitor Value, CF
Capacitor connected between FILTER pin and GND
1000
Bandwidth (kHz)
100
10
1
0.1
0.01
0.1
1
10
100
1000
Capacitance (nF)
ACS710 Noise versus External Capacitor Value, CF
Capacitor connected between FILTER pin and GND
ACS710x-25C
V CC = 3.3 V
1000
900
900
800
RMS Noise (μV)
RMS Noise (μV)
ACS710x-25C
V CC = 5 V
800
700
600
700
600
500
400
500
300
400
0
10
20
30
40
0
50
10
Capacitance (nF)
ACS710x-12C
V CC = 5 V
30
40
50
40
50
ACS710x-12C
V CC = 3.3 V
1600
1400
1400
1200
1200
RMS Noise (μV)
RMS Noise (μV)
1600
20
Capacitance (nF)
1000
800
600
400
200
1000
800
600
400
200
0
0
0
10
20
30
Capacitance (nF)
40
50
0
10
20
30
Capacitance (nF)
Allegro MicroSystems, LLC
115 Northeast Cutoff
Worcester, Massachusetts 01615-0036 U.S.A.
1.508.853.5000; www.allegromicro.com
10
120 kHz Bandwidth, High Voltage Isolation
Current Sensor with Integrated Overcurrent Detection
ACS710
Characteristic Performance Data
Data taken using the ACS710-6BB
Accuracy Data
Electrical Offset Voltage versus Ambient Temperature
Sensitivity versus Ambient Temperature
50
160.0
40
157.5
30
155.0
Sens (mV/A)
VOE (mV)
20
10
0
-10
-20
150.0
147.5
145.0
-30
142.5
-40
-50
–50
152.5
140.0
-25
0
25
50
75
100
125
150
–50
-25
0
25
TA (°C)
100.75
0.2
100.50
ESYM (%)
0.3
0.1
0
-0.1
99.75
99.50
99.25
50
150
100.00
-0.3
25
125
100.25
-0.2
0
100
Symmetry versus Ambient Temperature
101.00
75
100
125
99.00
–50
150
-25
0
25
TA (°C)
50
75
100
125
150
TA (°C)
Total Output Error versus Ambient Temperature
6.0
4.5
3.0
1.5
ETOT (%)
ELIN (%)
Nonlinearity versus Ambient Temperature
-25
75
TA (°C)
0.4
-0.4
–50
50
0
-1.5
-3.0
-4.5
-6.0
–50
-25
0
25
50
75
100
125
150
TA (°C)
Typical Maximum Limit
Mean
Typical Minimum Limit
Allegro MicroSystems, LLC
115 Northeast Cutoff
Worcester, Massachusetts 01615-0036 U.S.A.
1.508.853.5000; www.allegromicro.com
11
120 kHz Bandwidth, High Voltage Isolation
Current Sensor with Integrated Overcurrent Detection
ACS710
Characteristic Performance Data
Data taken using the ACS710-12CB
Accuracy Data
Electrical Offset Voltage versus Ambient Temperature
Sensitivity versus Ambient Temperature
58.5
25
20
58.0
Sens (mV/A)
15
VOE (mV)
10
5
0
-5
-10
57.0
56.5
56.0
-15
55.5
-20
-25
–50
57.5
-25
0
25
50
75
100
125
55.0
–50
150
-25
0
25
TA (°C)
100
125
150
Symmetry versus Ambient Temperature
100.1
ESYM (%)
100.0
99.9
99.8
99.7
99.6
-25
0
25
50
75
100
125
99.5
–50
150
-25
0
25
TA (°C)
50
75
100
125
150
TA (°C)
Total Output Error versus Ambient Temperature
6
5
4
3
ETOT (%)
ELIN (%)
75
TA (°C)
Nonlinearity versus Ambient Temperature
0.10
0.05
0
-0.05
-0.10
-0.15
-0.20
-0.25
-0.30
-0.35
-0.40
-0.45
–50
50
2
1
0
-1
-2
-3
–50
-25
0
25
50
75
100
125
150
TA (°C)
Typical Maximum Limit
Mean
Typical Minimum Limit
Allegro MicroSystems, LLC
115 Northeast Cutoff
Worcester, Massachusetts 01615-0036 U.S.A.
1.508.853.5000; www.allegromicro.com
12
120 kHz Bandwidth, High Voltage Isolation
Current Sensor with Integrated Overcurrent Detection
ACS710
Characteristic Performance Data
Data taken using the ACS710-25CB
Accuracy Data
Electrical Offset Voltage versus Ambient Temperature
Sensitivity versus Ambient Temperature
29.6
20
29.4
15
29.2
Sens (mV/A)
25
VOE (mV)
10
5
0
-5
29.0
28.8
28.6
28.4
-10
28.2
-15
28.0
-20
27.8
-25
–50
-25
0
25
50
75
100
125
27.6
–50
150
-25
0
25
TA (°C)
50
75
100
125
150
TA (°C)
Nonlinearity versus Ambient Temperature
Symmetry versus Ambient Temperature
0.10
100.1
0.05
100.0
ESYM (%)
-0.10
-0.15
-0.25
99.8
99.6
-0.30
-0.35
–50
99.9
99.7
-0.20
-25
0
25
50
75
100
125
99.5
–50
150
-25
0
25
TA (°C)
50
75
100
125
150
TA (°C)
Total Output Error versus Ambient Temperature
6
5
4
3
ETOT (%)
ELIN (%)
0
-0.05
2
1
0
-1
-2
-3
–50
-25
0
25
50
75
100
125
150
TA (°C)
Typical Maximum Limit
Mean
Typical Minimum Limit
Allegro MicroSystems, LLC
115 Northeast Cutoff
Worcester, Massachusetts 01615-0036 U.S.A.
1.508.853.5000; www.allegromicro.com
13
120 kHz Bandwidth, High Voltage Isolation
Current Sensor with Integrated Overcurrent Detection
ACS710
Setting Overcurrent Fault Switchpoint
Setting 12CB and 25CB Versions
The VOC needed for setting the overcurrent fault
switchpoint can be calculated as follows:
VOC = Sens × | IOC | ,
where VOC is in mV, Sens in mV/A, and IOC (overcurrent fault switchpoint) in A.
| Ioc | is the overcurrent fault switchpoint for a bidirectional (AC) current, which means a bi-directional
sensor will have two symmetrical overcurrent fault
switchpoints, +IOC and –IOC .
See the following graph for IOC and VOC ranges.
IOC versus VOC
(12CB and 25CB Versions)
IOC
0.4 VCC / Sens
Not Valid Range
Valid Range
0.25 VCC / Sens
0
0. 25 VCC
0. 4 VCC
VOC
– 0.25 VCC / Sens
– 0.4 VCC / Sens
Example: For ACS710KLATR-25CB-T, if required overcurrent fault switchpoint is 50 A, and VCC = 5 V, then the
required VOC can be calculated as follows:
VOC = Sens × IOC = 28 × 50 = 1400 (mV)
Allegro MicroSystems, LLC
115 Northeast Cutoff
Worcester, Massachusetts 01615-0036 U.S.A.
1.508.853.5000; www.allegromicro.com
14
ACS710
120 kHz Bandwidth, High Voltage Isolation
Current Sensor with Integrated Overcurrent Detection
| Ioc | is the overcurrent fault switchpoint for a bi-
Setting 6BB Versions
The VOC needed for setting the overcurrent fault
switchpoint can be calculated as follows:
directional (AC) current, which means a bi-directional
sensor will have two symmetrical overcurrent fault
VOC = 1.17 × Sens × | IOC | ,
where VOC is in mV, Sens in mV/A, and IOC (overcurrent fault switchpoint) in A.
switchpoints, +IOC and –IOC .
See the following graph for IOC and VOC ranges.
IOC versus VOC
(6BB Versions)
IOC
0.4 VCC / (1.17 × Sens)
Not Valid Range
Valid Range
0.25 VCC / (1.17 × Sens)
0
0.25 VCC
0.4 VCC
VOC
– 0.25 VCC / (1.17 × Sens)
– 0.4 VCC / (1.17 × Sens)
Example: For ACS710KLATR-6BB-T, if required overcurrent fault switchpoint is 10 A, and VCC = 5 V, then the
required VOC can be calculated as follows:
VOC = 1.17 × Sens × IOC = 1.17 × 151 × 10 = 1767 (mV)
Allegro MicroSystems, LLC
115 Northeast Cutoff
Worcester, Massachusetts 01615-0036 U.S.A.
1.508.853.5000; www.allegromicro.com
15
120 kHz Bandwidth, High Voltage Isolation
Current Sensor with Integrated Overcurrent Detection
ACS710
Functional Description (Latching Versions)
Overcurrent Fault Operation
The primary concern with high-speed fault detection is that noise
may cause false tripping. Various applications have or need to
be able to ignore certain faults that are due to switching noise or
other parasitic phenomena, which are application dependant. The
problem with simply trying to filter out this noise in the main
signal path is that in high-speed applications, with asymmetric
noise, the act of filtering introduces an error into the measurement. To get around this issue, and allow the user to prevent the
fault signal from being latched by noise, a circuit was designed to
¯¯T
¯ pin voltage based on the value of the capacitor
slew the ¯F¯A¯¯U¯¯L
from that pin to ground. Once the voltage on the pin falls below
2 V, as established by an internal reference, the fault output is
latched and pulled to ground quickly with an internal N-channel
MOSFET.
Fault Walk-through
The following walk-through references various sections and
attributes in the figure below. This figure shows different
fault set/reset scenarios and how they relate to the voltages on
¯¯T
¯ pin, FAULT_EN pin, and the internal Overcurrent
the ¯F¯A¯¯U¯¯L
(OC) Fault node, which is invisible to the customer.
1. Because the device is enabled (FAULT_EN is high for a
minimum period of time, the Fault Enable Delay, tFED , 15 μs
¯¯T
¯
typical) and there is an OC fault condition, the device ¯F¯A¯¯U¯¯L
pin starts discharging.
¯A
¯¯U
¯¯L
¯¯T
¯¯ pin voltage reaches approximately 2 V, the
2. When the F
¯¯T
¯
fault is latched, and an internal NMOS device pulls the ¯F¯A¯¯U¯¯L
¯¯T
¯
pin voltage to approximately 0 V. The rate at which the ¯F¯A¯¯U¯¯L
pin slews downward (see [4] in the figure) is dependent on the
¯¯T
¯ pin.
external capacitor, COC, on the ¯F¯A¯¯U¯¯L
¯A
¯¯U
¯¯L
¯¯T
¯¯
3. When the FAULT_EN pin is brought low, the F
pin starts resetting if no OC fault condition exists, and if
FAULT_EN is low for a time period greater than tOCH . The
VCC
1
4. The slope, and thus the delay to latch the fault is controlled by
¯¯T
¯ pin to ground. Durthe capacitor, COC, placed on the ¯F¯A¯¯U¯¯L
¯
¯
¯
¯¯T
¯ pin is between
ing this portion of the fault (when the FA¯U¯¯L
VCC and 2 V), there is a 3 mA constant current sink, which
discharges COC. The length of the fault delay, t, is equal to:
COC ( VCC – 2 V )
(1)
3 mA
where VCC is the device power supply voltage in volts, t is in
seconds and COC is in Farads. This formula is valid for RPU
equal to or greater than 330 kΩ. For lower-value resistors,
the current flowing through the RPU resistor during a fault
event, IPU , will be larger. Therefore, the current discharging
the capacitor would be 3 mA – IPU and equation 1 may not be
valid.
¯A
¯¯U
¯¯L
¯¯T
¯¯ pin did not reach the 2 V latch point before the
5. The F
OC fault condition cleared. Because of this, the fixed 3 mA
current sink turns off, and the internal PMOS pull-up turns on
¯¯T
¯ pin.
to recharge COC through the ¯F¯A¯¯U¯¯L
t=
6. This curve shows VCC charging external capacitor COC
through the internal PMOS pull-up. The slope is determined
by COC.
7. When the FAULT_EN pin is brought low, if the fault condition
¯¯T
¯ pin will be pulled low by the
still exists, the latched ¯F¯A¯¯U¯¯L
internal 3mA current source. When fault condition is removed
then the Fault pin charges as shown in step 6.
8. At this point there is a fault condition, and the part is enabled
¯¯T
¯ pin can charge to VCC. This shortens the
before the ¯F¯A¯¯U¯¯L
user-set delay, so the fault is latched earlier. The new delay
time can be calculated by equation 1, after substituting the
¯¯T
¯ pin for VCC.
voltage seen on the ¯F¯A¯¯U¯¯L
1
tFED
4
FAULT
(Output)
2V
internal NMOS pull-down turns off and an internal PMOS pullup turns on (see [7] if the OC fault condition still exists).
6
1
6
4
8
4
5
2
4
2
6
2
7
3
0V
Time
FAULT_EN
(Input)
OC Fault
Condition
(Active High)
Allegro MicroSystems, LLC
115 Northeast Cutoff
Worcester, Massachusetts 01615-0036 U.S.A.
1.508.853.5000; www.allegromicro.com
16
120 kHz Bandwidth, High Voltage Isolation
Current Sensor with Integrated Overcurrent Detection
ACS710
Functional Description (Non-Latching Versions)
Overcurrent Fault Operation
The primary concern with high-speed fault detection is that noise
may cause false tripping. Various applications have or need to
be able to ignore certain faults that are due to switching noise or
other parasitic phenomena, which are application dependant. The
problem with simply trying to filter out this noise in the main signal path is that in high-speed applications, with asymmetric noise,
the act of filtering introduces an error into the measurement.
To get around this issue, and allow the user to prevent the fault
signal from going low due to noise, a circuit was designed to slew
¯¯T
¯ pin voltage based on the value of the capacitor from
the ¯F¯A¯¯U¯¯L
that pin to ground. Once the voltage on the pin falls below 2 V, as
established by an internal reference, the fault output is pulled to
ground quickly with an internal N-channel MOSFET.
Fault Walk-through
The following walk-through references various sections and
attributes in the figure below. This figure shows different
fault set/reset scenarios and how they relate to the voltages on
¯¯T
¯ pin, FAULT_EN pin, and the internal Overcurrent
the ¯F¯A¯¯U¯¯L
(OC) Fault node, which is invisible to the customer.
1. Because the device is enabled (FAULT_EN is high for a minimum period of time, the Fault Enable Delay, tFED , and there is
¯¯T
¯ pin starts discharging.
an OC fault condition, the device ¯F¯A¯¯U¯¯L
¯A
¯¯U
¯¯L
¯¯T
¯¯ pin voltage reaches approximately 2 V, an
2. When the F
¯¯T
¯ pin voltage to approxinternal NMOS device pulls the ¯F¯A¯¯U¯¯L
¯¯T
¯ pin slews downward
imately 0 V. The rate at which the ¯F¯A¯¯U¯¯L
(see [4] in the figure) is dependent on the external capacitor,
¯¯T
¯ pin.
COC, on the ¯F¯A¯¯U¯¯L
¯A
¯¯U
¯¯L
¯¯T
¯¯ pin
3. When the FAULT_EN pin is brought low, the F
starts resetting if FAULT_EN is low for a time period greater
VCC
1
4. The slope, and thus the delay to pull the fault low is controlled
¯¯T
¯ pin to ground.
by the capacitor, COC, placed on the ¯F¯A¯¯U¯¯L
¯¯T
¯ pin is
During this portion of the fault (when the ¯F¯A¯¯U¯¯
L
between VCC and 2 V), there is a 3 mA constant current sink,
which discharges COC. The length of the fault delay, t, is equal
to:
COC ( VCC – 2 V )
(2)
3 mA
where VCC is the device power supply voltage in volts, t is in
seconds and COC is in Farads. This formula is valid for RPU
equal to or greater than 330 kΩ. For lower-value resistors,
the current flowing through the RPU resistor during a fault
event, IPU , will be larger. Therefore, the current discharging
the capacitor would be 3 mA – IPU and equation 1 may not be
valid.
¯¯T
¯ pin did not reach the 2 V latch point before the
5. The ¯F¯A¯¯U¯¯L
OC fault condition cleared. Because of this, the fixed 3 mA
current sink turns off, and the internal PMOS pull-up turns on
¯¯T
¯ pin.
to recharge COC through the ¯F¯A¯¯U¯¯L
t=
6. This curve shows VCC charging external capacitor COC
through the internal PMOS pull-up. The slope is determined
by COC.
7. At this point there is a fault condition, and the part is enabled
¯¯T
¯ pin can charge to VCC. This shortens the
before the ¯F¯A¯¯U¯¯L
user-set delay, so the fault gets pulled low earlier. The new
delay time can be calculated by equation 1, after substituting
¯¯T
¯ pin for VCC.
the voltage seen on the ¯F¯A¯¯U¯¯L
1
tFED
4
FAULT
(Output)
2V
than tOCH . The internal NMOS pull-down turns off and an
internal PMOS pull-up turns on.
6
1
6
4
7
4
5
2
4
2
6
2
3
0V
Time
FAULT_EN
(Input)
OC Fault
Condition
(Active High)
Allegro MicroSystems, LLC
115 Northeast Cutoff
Worcester, Massachusetts 01615-0036 U.S.A.
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17
ACS710
120 kHz Bandwidth, High Voltage Isolation
Current Sensor with Integrated Overcurrent Detection
Chopper Stabilization Technique
Chopper Stabilization is an innovative circuit technique that is
used to minimize the offset voltage of a Hall element and an associated on-chip amplifier. Allegro patented a Chopper Stabilization technique that nearly eliminates Hall IC output drift induced
by temperature or package stress effects. This offset reduction
technique is based on a signal modulation-demodulation process.
Modulation is used to separate the undesired dc offset signal from
the magnetically induced signal in the frequency domain. Then,
using a low-pass filter, the modulated DC offset is suppressed
while the magnetically induced signal passes through the filter.
As a result of this chopper stabilization approach, the output
voltage from the Hall IC is desensitized to the effects of temperature and mechanical stress. This technique produces devices that
have an extremely stable Electrical Offset Voltage, are immune to
thermal stress, and have precise recoverability after temperature
cycling.
This technique is made possible through the use of a BiCMOS
process that allows the use of low-offset and low-noise amplifiers
in combination with high-density logic integration and sample
and hold circuits.
Regulator
Clock/Logic
Amp
Sample and
Hold
Hall Element
Low-Pass
Filter
Concept of Chopper Stabilization Technique
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18
ACS710
120 kHz Bandwidth, High Voltage Isolation
Current Sensor with Integrated Overcurrent Detection
Definitions of Accuracy Characteristics
Sensitivity (Sens). The change in sensor output in response to a
1 A change through the primary conductor. The sensitivity is the
product of the magnetic circuit sensitivity (G / A) and the linear
IC amplifier gain (mV/G). The linear IC amplifier gain is programmed at the factory to optimize the sensitivity (mV/A) for the
full-scale current of the device.
Noise (VNOISE). The product of the linear IC amplifier gain
(mV/G) and the noise floor for the Allegro Hall effect linear
IC. The noise floor is derived from the thermal and shot noise
observed in Hall elements. Dividing the noise (mV) by the sensitivity (mV/A) provides the smallest current that the device is able
to resolve.
Linearity (ELIN). The degree to which the voltage output from
the sensor varies in direct proportion to the primary current
through its full-scale amplitude. Nonlinearity in the output can be
attributed to the saturation of the flux concentrator approaching
the full-scale current. The following equation is used to derive the
linearity:
{ [
100 1–
VIOUT_full-scale amperes – VIOUT(Q)
2 (VIOUT_1/2 full-scale amperes – VIOUT(Q) )
[{
Accuracy is divided into four areas:
0 A at 25°C. Accuracy of sensing zero current flow at 25°C,
without the effects of temperature.
0 A over Δ temperature. Accuracy of sensing zero current
flow including temperature effects.
Full-scale current at 25°C. Accuracy of sensing the full-scale
current at 25°C, without the effects of temperature.
Full-scale current over Δ temperature. Accuracy of sensing fullscale current flow including temperature effects.
Ratiometry. The ratiometric feature means that its 0 A output,
VIOUT(Q), (nominally equal to VCC/2) and sensitivity, Sens, are
proportional to its supply voltage, VCC . The following formula is
used to derive the ratiometric change in 0 A output voltage,
VIOUT(Q)RAT (%).
100
VCC / 5 V
The ratiometric change in sensitivity, SensRAT (%), is defined as:
where VIOUT_full-scale amperes = the output voltage (V) when the
sensed current approximates full-scale ±IP .
100
Symmetry (ESYM). The degree to which the absolute voltage
output from the sensor varies in proportion to either a positive
or negative full-scale primary current. The following formula is
used to derive symmetry:
100
VIOUT(Q)VCC / VIOUT(Q)5V
SensVCC / Sens5V
VCC / 5 V
Output Voltage versus Sensed Current
Accuracy at 0 A and at Full-Scale Current
Increasing VIOUT(V)
Accuracy
Over $Temp erature
VIOUT_+ full-scale amperes – VIOUT(Q)
VIOUT(Q) – VIOUT_–full-scale amperes
Accuracy
25°C Only
Quiescent output voltage (VIOUT(Q)). The output of the sensor
when the primary current is zero. For a unipolar supply voltage,
it nominally remains at 0.5×VCC. For example, in the case of a
bidirectional output device, VCC = 5 V translates into VIOUT(Q) =
2.5 V. Variation in VIOUT(Q) can be attributed to the resolution of
the Allegro linear IC quiescent voltage trim and thermal drift.
Electrical offset voltage (VOE). The deviation of the device output from its ideal quiescent voltage due to nonmagnetic causes.
To convert this voltage to amperes, divide by the device sensitivity, Sens.
Accuracy (ETOT). The accuracy represents the maximum deviation of the actual output from its ideal value. This is also known
as the total ouput error. The accuracy is illustrated graphically in
the output voltage versus current chart at right. Note that error is
directly measured during final test at Allegro.
Average
VIOUT
Accuracy
Over $Temp erature
Accuracy
25°C Only
IP(min)
–IP (A)
+IP (A)
Full Scale
IP(max)
0A
Accuracy
25°C Only
Accuracy
Over $Temp erature
Decreasing VIOUT(V)
Allegro MicroSystems, LLC
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19
ACS710
120 kHz Bandwidth, High Voltage Isolation
Current Sensor with Integrated Overcurrent Detection
Definitions of Dynamic Response Characteristics
I (%)
Propagation delay (tPROP). The time required for the sensor
output to reflect a change in the primary current signal. Propagation delay is attributed to inductive loading within the linear IC
package, as well as in the inductive loop formed by the primary
conductor geometry. Propagation delay can be considered as a
fixed time offset and may be compensated.
Primary Current
90
Transducer Output
0
Propagation Time, tPROP
I (%)
Response time (tRESPONSE). The time interval between
a) when the primary current signal reaches 90% of its final
value, and b) when the sensor reaches 90% of its output
corresponding to the applied current.
Primary Current
90
Transducer Output
0
Response Time, tRESPONSE
I (%)
Rise time (tr). The time interval between a) when the sensor
reaches 10% of its full scale value, and b) when it reaches 90%
of its full scale value. The rise time to a step response is used to
derive the bandwidth of the current sensor, in which ƒ(–3 dB) =
0.35 / tr. Both tr and tRESPONSE are detrimentally affected by eddy
current losses observed in the conductive IC ground plane.
t
t
Primary Current
90
Transducer Output
10
0
Rise Time, tr
t
Allegro MicroSystems, LLC
115 Northeast Cutoff
Worcester, Massachusetts 01615-0036 U.S.A.
1.508.853.5000; www.allegromicro.com
20
120 kHz Bandwidth, High Voltage Isolation
Current Sensor with Integrated Overcurrent Detection
ACS710
Package LA, 16-pin SOICW
10.30 ±0.20
8°
0°
16
0.33
0.20
7.50 ±0.10
0.65
16
1.27
2.25
10.30 ±0.33
9.50
A
1.40 REF
1
2
1.27
0.40
Branded Face
16X
SEATING
PLANE
0.10 C
0.51
0.31
1.27 BSC
2
0.25 BSC
C
SEATING PLANE
GAUGE PLANE
C
PCB Layout Reference View
2.65 MAX
0.30
0.10
For Reference Only; not for tooling use (reference MS-013AA)
Dimensions in millimeters
Dimensions exclusive of mold flash, gate burrs, and dambar protrusions
Exact case and lead configuration at supplier discretion within limits shown
A Terminal #1 mark area
B Branding scale and appearance at supplier discretion
C
1
Reference land pattern layout (reference IPC7351
SOIC127P600X175-8M); all pads a minimum of 0.20 mm from all
adjacent pads; adjust as necessary to meet application process
requirements and PCB layout tolerances
NNNNNNNNNNN
TTT-TTT
LLLLLLLLL
1
B Standard Branding Reference View
N = Device part number
T = Temperature range, package - amperage
L = Lot number
Allegro MicroSystems, LLC
115 Northeast Cutoff
Worcester, Massachusetts 01615-0036 U.S.A.
1.508.853.5000; www.allegromicro.com
21
ACS710
120 kHz Bandwidth, High Voltage Isolation
Current Sensor with Integrated Overcurrent Detection
Revision History
Revision
Revision Date
Rev. 8
January 15, 2013
Description of Revision
Add non-latching variants, update isolation
specifications
Copyright ©2007-2013, Allegro MicroSystems, LLC
The products described herein are protected by U.S. patents: 7,166,807; 7,425,821; 7,573,393; and 7,598,601.
Allegro MicroSystems, LLC reserves the right to make, from time to time, such departures from the detail specifications as may be required to
permit improvements in the performance, reliability, or manufacturability of its products. Before placing an order, the user is cautioned to verify that
the information being relied upon is current.
Allegro’s products are not to be used in life support devices or systems, if a failure of an Allegro product can reasonably be expected to cause the
failure of that life support device or system, or to affect the safety or effectiveness of that device or system.
The information included herein is believed to be accurate and reliable. However, Allegro MicroSystems, LLC assumes no responsibility for its
use; nor for any infringement of patents or other rights of third parties which may result from its use.
For the latest version of this document, visit our website:
www.allegromicro.com
Allegro MicroSystems, LLC
115 Northeast Cutoff
Worcester, Massachusetts 01615-0036 U.S.A.
1.508.853.5000; www.allegromicro.com
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