NSC LMV2011MAX

LMV2011
High Precision, Rail-to-Rail Output Operational Amplifier
General Description
Features
The LMV2011 is a new precision amplifier that offers unprecedented accuracy and stability at an affordable price and
is offered in miniature (SOT23-5) package and in 8 lead SOIC
package. This device utilizes patented techniques to measure
and continually correct the input offset error voltage. The result is an amplifier which is ultra stable over time and temperature. It has excellent CMRR and PSRR ratings, and does
not exhibit the familiar 1/f voltage and current noise increase
that plagues traditional amplifiers. The combination of the
LMV2011 characteristics makes it a good choice for transducer amplifiers, high gain configurations, ADC buffer amplifiers, DAC I-V conversion, and any other 2.7V-5V application
requiring precision and long term stability.
Other useful benefits of the LMV2011 are rail-to-rail output, a
low supply current of 930µA, and wide gain-bandwidth product of 3MHz. These extremely versatile features found in the
LMV2011 provide high performance and ease of use.
(For Vs = 5V, Typical unless otherwise noted)
■ Low Guaranteed Vos over temperature
■ Low Noise with no 1/f
■ High CMRR
■ High PSRR
■ High AVOL
■ Wide gain-bandwidth product
■ High slew rate
■ Low supply current
■ Rail-to-rail output
■ No external capacitors required
35µV
35nV/√Hz
130dB
120dB
130dB
3MHz
4V/µs
930µA
30mV
Applications
■ Precision Instrumentation Amplifiers
■ Thermocouple Amplifiers
■ Strain Gauge Bridge Amplifier
Connection Diagrams
5-Pin SOT23
8-Pin SOIC
20051502
20051538
Top View
Top View
Ordering Information
Package
5-Pin SOT23
8-Pin SOIC
Part Number
Package Marking
LMV2011MF
A84A
LMV2011MFX
LMV2011MA
LMV2011MA
LMV2011MAX
© 2008 National Semiconductor Corporation
200515
Transport Media
1k Units Tape and Reel
3k Units Tape and Reel
95 Units/Rail
2.5k Units Tape and Reel
NSC Drawing
MF05A
M08A
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LMV2011 High Precision, Rail-to-Rail Output Operational Amplifier
July 1, 2008
LMV2011
Current At Output Pin
Current At Power Supply Pin
Junction Temperature (TJ)
Lead Temperature (soldering
10 sec.)
Absolute Maximum Ratings (Note 1)
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales Office/
Distributors for availability and specifications.
ESD Tolerance
Human Body Model
Machine Model
Supply Voltage
Common-Mode Input Voltage
Differential Input Voltage
Current At Input Pin
2000V
200V
5.5V
Operating Ratings
30mA
50mA
150°C
+300°C
(Note 1)
Supply Voltage
Storage Temperature Range
Operating Temperature Range
−0.3≤ VCM ≤ VCC +0.3V
± Supply Voltage
30mA
2.7V to 5.25V
−65°C to 150°C
0°C to 70°C
2.7V DC Electrical Characteristics
Unless otherwise specified, all limits guaranteed for T J = 25°C, V+ =
2.7V, V- = 0V, V CM = 1.35V, VO = 1.35V and RL > 1MΩ. Boldface limits apply at the temperature extremes.
Symbol
VOS
TCVOS
Typ
Max
Units
Input Offset Voltage
Parameter
Conditions
Min
0.8
25
35
μV
Offset Calibration Time
0.5
10
12
ms
Input Offset Voltage
0.015
μV/°C
Long-Term Offset Drift
0.006
μV/month
2.5
Input Current
-3
IOS
Input Offset Current
6
pA
RIND
Input Differential Resistance
9
MΩ
CMRR
Common Mode Rejection
Ratio
PSRR
AVOL
VO
−0.3 ≤ VCM ≤ 0.9V
pA
130
95
90
dB
Power Supply Rejection Ratio 2.7V ≤ V+ ≤ 5V
120
95
90
dB
Open Loop Voltage Gain
RL = 10kΩ
130
95
90
RL = 2kΩ
124
90
85
Output Swing
0 ≤ VCM ≤ 0.9V
2.665
2.655
RL = 10kΩ to 1.35V
VIN(diff) = ±0.5V
2.630
2.615
RL = 2kΩ to 1.35V
VIN(diff) = ±0.5V
Output Current
0.060
0.075
0.061
0.085
0.105
Sourcing, VO = 0V
VIN(diff) = ±0.5V
12
5
3
Sinking, VO = 5V
V IN(diff) = ±0.5V
18
5
3
Output Impedance
0.05
IS
Supply Current
0.919
2
V
2.65
ROUT
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dB
2.68
0.033
IO
5
μV
Lifetime VOS Drift
IIN
V
mA
Ω
1.20
1.50
mA
TJ = 25°C, V+ = 2.7V, V - = 0V, VCM = 1.35V, VO = 1.35V, and RL >
Symbol
Parameter
Conditions
Min
Typ
Max
Units
GBW
Gain-Bandwidth Product
3
MHz
SR
Slew Rate
4
V/μs
θm
Phase Margin
60
Deg
Gm
Gain Margin
−14
dB
en
Input-Referred Voltage Noise
35
nV/
in
Input-Referred Current Noise
150
fA/
enp-p
Input-Referred Voltage Noise RS = 100Ω, DC to 10Hz
850
nVpp
trec
Input Overload Recovery Time
50
ms
ts
Output Settling Time
0.9
μs
1%
AV = −1, RL = 2kΩ
1V Step
0.1%
49
0.01%
100
5V DC Electrical Characteristics
Unless otherwise specified, all limits guaranteed for T J = 25°C, V+ = 5V,
V- = 0V, V CM = 2.5V, VO = 2.5V and RL > 1MΩ. Boldface limits apply at the temperature extremes.
Symbol
VOS
TCVOS
Typ
Max
Units
Input Offset Voltage
Parameter
Conditions
Min
0.12
25
35
μV
Offset Calibration Time
0.5
10
12
ms
Input Offset Voltage
0.015
μV/°C
Long-Term Offset Drift
0.006
μV/month
2.5
Input Current
-3
IOS
Input Offset Current
6
pA
RIND
Input Differential Resistance
9
MΩ
CMRR
Common Mode Rejection
Ratio
PSRR
AVOL
VO
−0.3 ≤ VCM ≤ 3.2
pA
130
100
90
dB
Power Supply Rejection Ratio 2.7V ≤ V+ ≤ 5V
120
95
90
dB
Open Loop Voltage Gain
RL = 10kΩ
130
105
100
RL = 2kΩ
132
95
90
Output Swing
0 ≤ VCM ≤ 3.2
4.96
4.95
RL = 10kΩ to 2.5V
VIN(diff) = ±0.5V
4.895
4.875
RL = 2kΩ to 2.5V
VIN(diff) = ±0.5V
Output Current
0.070
0.085
V
4.919
0.091
0.115
0.140
Sourcing, VO = 0V
VIN(diff) = ±0.5V
15
8
6
Sinking, VO = 5V
V IN(diff) = ±0.5V
17
8
6
ROUT
Output Impedance
0.05
IS
Supply Current per Channel
0.930
3
dB
4.978
0.040
IO
5
μV
Lifetime VOS Drift
IIN
V
mA
Ω
1.20
1.50
mA
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LMV2011
2.7V AC Electrical Characteristics
1MΩ. Boldface limits apply at the temperature extremes.
LMV2011
5V AC Electrical Characteristics
TJ = 25°C, V+ = 5V, V - = 0V, VCM = 2.5V, VO = 2.5V, and RL > 1MΩ.
Boldface limits apply at the temperature extremes.
Symbol
Parameter
Conditions
Min
Typ
Max
Units
GBW
Gain-Bandwidth Product
3
MHz
SR
Slew Rate
4
V/μs
θm
Phase Margin
60
deg
Gm
Gain Margin
−15
dB
en
Input-Referred Voltage Noise
35
nV/
in
Input-Referred Current Noise
150
fA/
enp-p
Input-Referred Voltage Noise RS = 100Ω, DC to 10Hz
850
nVpp
trec
Input Overload Recovery Time
ts
Output Settling Time
AV = −1, RL = 2kΩ
1V Step
50
ms
1%
0.8
us
0.1%
36
0.01%
100
Note 1: Absolute Maximum Ratings indicate limits beyond which damage may occur. Operating Ratings indicate conditions for which the device is intended to
be functional, but specific performance is not guaranteed. For guaranteed specifications and test conditions, see the Electrical Characteristics.
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4
LMV2011
Typical Performance Characteristics
TA=25C, VS= 5V unless otherwise specified.
Supply Current vs. Supply Voltage
Offset Voltage vs. Supply Voltage
20051525
20051524
Offset Voltage vs. Common Mode
Offset Voltage vs. Common Mode
20051535
20051534
Voltage Noise vs. Frequency
Input Bias Current vs. Common Mode
20051503
20051504
5
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LMV2011
PSRR vs. Frequency
PSRR vs. Frequency
20051507
20051506
Output Sourcing @ 2.7V
Output Sourcing @ 5V
20051527
20051526
Output Sinking @ 2.7V
Output Sinking @ 5V
20051528
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20051529
6
LMV2011
Max Output Swing vs. Supply Voltage
Max Output Swing vs. Supply Voltage
20051530
20051531
Min Output Swing vs. Supply Voltage
Min Output Swing vs. Supply Voltage
20051532
20051533
CMRR vs. Frequency
Open Loop Gain and Phase vs. Supply Voltage
20051508
20051505
7
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LMV2011
Open Loop Gain and Phase vs. RL @ 2.7V
Open Loop Gain and Phase vs. RL @ 5V
20051509
20051510
Open Loop Gain and Phase vs. CL @ 2.7V
Open Loop Gain and Phase vs. CL @ 5V
20051512
20051511
Open Loop Gain and Phase vs. Temperature @ 2.7V
Open Loop Gain and Phase vs. Temperature @ 5V
20051536
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20051537
8
LMV2011
THD+N vs. AMPL
THD+N vs. Frequency
20051513
20051514
0.1Hz − 10Hz Noise vs. Time
20051515
9
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LMV2011
Application Information
THE BENEFITS OF LMV2011
NO 1/f NOISE
Using patented methods, the LMV2011 eliminates the 1/f
noise present in other amplifiers. That noise, which increases
as frequency decreases, is a major source of measurement
error in all DC-coupled measurements. Low-frequency noise
appears as a constantly-changing signal in series with any
measurement being made. As a result, even when the measurement is made rapidly, this constantly-changing noise signal will corrupt the result. The value of this noise signal can
be surprisingly large. For example: If a conventional amplifier
and a noise corner of
has a flat-band noise level of 10nV/
10Hz, the RMS noise at 0.001Hz is 1µV/
. This is equivalent to a 0.50µV peak-to-peak error, in the frequency range
0.001 Hz to 1.0 Hz. In a circuit with a gain of 1000, this produces a 0.50mV peak-to-peak output error. This number of
0.001 Hz might appear unreasonably low, but when a data
acquisition system is operating for 17 minutes, it has been on
long enough to include this error. In this same time, the
LMV2011 will only have a 0.21mV output error. This is smaller
by 2.4 x. Keep in mind that this 1/f error gets even larger at
lower frequencies. At the extreme, many people try to reduce
this error by integrating or taking several samples of the same
signal. This is also doomed to failure because the 1/f nature
of this noise means that taking longer samples just moves the
measurement into lower frequencies where the noise level is
even higher.
The LMV2011 eliminates this source of error. The noise level
is constant with frequency so that reducing the bandwidth reduces the errors caused by noise.
Another source of error that is rarely mentioned is the error
voltage caused by the inadvertent thermocouples created
when the common "Kovar type" IC package lead materials are
soldered to a copper printed circuit board. These steel-based
leadframe materials can produce over 35μV/°C when soldered onto a copper trace. This can result in thermocouple
noise that is equal to the LMV2011 noise when there is a
temperature difference of only 0.0014°C between the lead
and the board!
For this reason, the lead-frame of the LMV2011 is made of
copper. This results in equal and opposite junctions which
cancel this effect. The extremely small size of the SOT-23
package results in the leads being very close together. This
further reduces the probability of temperature differences and
hence decreases thermal noise.
20051516
FIGURE 1. Overload Recovery Test
The wide bandwidth of the LMV2011 enhances performance
when it is used as an amplifier to drive loads that inject transients back into the output. ADCs (Analog-to-Digital Converters) and multiplexers are examples of this type of load. To
simulate this type of load, a pulse generator producing a 1V
peak square wave was connected to the output through a
10pF capacitor. (Figure 1) The typical time for the output to
recover to 1% of the applied pulse is 80ns. To recover to 0.1%
requires 860ns. This rapid recovery is due to the wide bandwidth of the output stage and large total GBW.
NO EXTERNAL CAPACITORS REQUIRED
The LMV2011 does not need external capacitors. This eliminates the problems caused by capacitor leakage and dielectric absorption, which can cause delays of several seconds
from turn-on until the amplifier's error has settled.
MORE BENEFITS
The LMV2011 offers the benefits mentioned above and more.
It has a rail-to-rail output and consumes only 950µA of supply
current while providing excellent DC and AC electrical performance. In DC performance, the LMC2001 achieves 130dB
of CMRR, 120dB of PSRR and 130dB of open loop gain. In
AC performance, the LMV2011 provides 3MHz of gain-bandwidth product and 4V/µs of slew rate.
HOW THE LMV2011 WORKS
The LMV2011 uses new, patented techniques to achieve the
high DC accuracy traditionally associated with chopper-stabilized amplifiers without the major drawbacks produced by
chopping. The LMV2011 continuously monitors the input offset and corrects this error. The conventional chopping process produces many mixing products, both sums and
differences, between the chopping frequency and the incoming signal frequency. This mixing causes large amounts of
distortion, particularly when the signal frequency approaches
the chopping frequency. Even without an incoming signal, the
chopper harmonics mix with each other to produce even more
trash. If this sounds unlikely or difficult to understand, look at
the plot (Figure 2), of the output of a typical (MAX432) chopper-stabilized opamp. This is the output when there is no
incoming signal, just the amplifier in a gain of -10 with the input
grounded. The chopper is operating at about 150Hz; the rest
is mixing products. Add an input signal and the noise gets
much worse. Compare this plot with Figure 3 of the LMV2011.
This data was taken under the exact same conditions. The
auto-zero action is visible at about 30kHz but note the absence of mixing products at other frequencies. As a result, the
LMV2011 has very low distortion of 0.02% and very low mixing products.
OVERLOAD RECOVERY
The LMV2011 recovers from input overload much faster than
most chopper-stabilized opamps. Recovery from driving the
amplifier to 2X the full scale output, only requires about 40ms.
Many chopper-stabilized amplifiers will take from 250ms to
several seconds to recover from this same overload. This is
because large capacitors are used to store the unadjusted
offset voltage.
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10
20051517
FIGURE 2. The Output of a Chopper Stabilized Op Amp
(MAX432)
20051518
FIGURE 4. Precision Strain Gauge Amplifier
Extending Supply Voltages and Output Swing by Using a
Composite Amplifier Configuration:
In cases where substantially higher output swing is required
with higher supply voltages, arrangements like the ones
shown in Figure 5 and Figure 6 could be used. These configurations utilize the excellent DC performance of the LMV2011
while at the same time allow the superior voltage and frequency capabilities of the LM6171 to set the dynamic performance of the overall amplifier. For example, it is possible to
achieve ±12V output swing with 300MHz of overall GBW
(AV = 100) while keeping the worst case output shift due to
VOS less than 4mV. The LMV2011 output voltage is kept at
about mid-point of its overall supply voltage, and its input
common mode voltage range allows the V- terminal to be
grounded in one case (Figure 5, inverting operation) and tied
to a small non-critical negative bias in another (Figure 6, noninverting operation). Higher closed-loop gains are also possible with a corresponding reduction in realizable bandwidth.
Table 1 shows some other closed loop gain possibilities along
with the measured performance in each case.
20051504
FIGURE 3. The Output of the LMV2011
INPUT CURRENTS
The LMV2011's input currents are different than standard
bipolar or CMOS input currents in that it appears as a current
flowing in one input and out the other. Under most operating
conditions, these currents are in the picoamp level and will
have little or no effect in most circuits. These currents tend to
increase slightly when the common-mode voltage is near the
minus supply. (See the typical curves.) At high temperatures
such as 85°C, the input currents become larger, 0.5nA typical,
and are both positive except when the VCM is near V−. If operation is expected at low common-mode voltages and high
temperature, do not add resistance in series with the inputs
to balance the impedances. Doing this can cause an increase
in offset voltage. A small resistance such as 1kΩ can provide
some protection against very large transients or overloads,
and will not increase the offset significantly.
11
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LMV2011
PRECISION STRAIN-GAUGE AMPLIFIER
This Strain-Gauge amplifier (Figure 4) provides high gain
(1006 or ~60 dB) with very low offset and drift. Using the resistors' tolerances as shown, the worst case CMRR will be
greater than 108 dB. The CMRR is directly related to the resistor mismatch. The rejection of common-mode error, at the
output, is independent of the differential gain, which is set by
R3. The CMRR is further improved, if the resistor ratio matching is improved, by specifying tighter-tolerance resistors, or
by trimming.
LMV2011
It should be kept in mind that in order to minimize the output
noise voltage for a given closed-loop gain setting, one could
minimize the overall bandwidth. As can be seen from Equation 1 above, the output noise has a square-root relationship
to the Bandwidth.
In the case of the inverting configuration, it is also possible to
increase the input impedance of the overall amplifier, by raising the value of R1, without having to increase the feed-back
resistor, R2, to impractical values, by utilizing a "Tee" network
as feedback. See the LMC6442 data sheet (Application Notes
section) for more details on this.
20051519
FIGURE 5. Composite Amplifier Configuration
20051521
TABLE 1. Composite Amplifier Measured Performance
AV
R1
(Ω)
R2
(Ω)
C2
(pF)
BW
(MHz)
50
200
10k
8
3.3
178
37
100
100
10k
10
2.5
174
70
100
1k
100k
0.67
3.1
170
70
500
200
100k
1.75
1.4
96
250
1000
100
100k
2.2
0.98
64
400
FIGURE 7. AC Coupled ADC Driver
SR
en p-p
(V/μs) (mVPP)
LMV2011 AS ADC INPUT AMPLIFIER
The LMV2011 is a great choice for an amplifier stage immediately before the input of an ADC (Analog-to-Digital Converter), whether AC or DC coupled. See Figure 7 and Figure
8. This is because of the following important characteristics:
A) Very low offset voltage and offset voltage drift over time
and temperature allow a high closed-loop gain setting
without introducing any short-term or long-term errors.
For example, when set to a closed-loop gain of 100 as the
analog input amplifier for a 12-bit A/D converter, the overall conversion error over full operation temperature and
30 years life of the part (operating at 50°C) would be less
than 5 LSBs.
B) Fast large-signal settling time to 0.01% of final value
(1.4μs) allows 12 bit accuracy at 100KHZ or more sampling rate.
C) No flicker (1/f) noise means unsurpassed data accuracy
over any measurement period of time, no matter how
long. Consider the following opamp performance, based
on a typical low-noise, high-performance commerciallyavailable device, for comparison:
Opamp flatband noise = 8nV/
1/f corner frequency = 100Hz
AV = 2000
Measurement time = 100 sec
Bandwidth = 2Hz
This example will result in about 2.2 mVPP (1.9 LSB) of
output noise contribution due to the opamp alone, compared to about 594μVPP (less than 0.5 LSB) when that
opamp is replaced with the LMV2011 which has no 1/f
contribution. If the measurement time is increased from
100 seconds to 1 hour, the improvement realized by using
the LMV2011 would be a factor of about 4.8 times
(2.86mVPP compared to 596μV when LMV2011 is used)
mainly because the LMV2011 accuracy is not compromised by increasing the observation time.
D) Copper leadframe construction minimizes any thermocouple effects which would degrade low level/high gain
In terms of the measured output peak-to-peak noise, the following relationship holds between output noise voltage, en pp, for different closed-loop gain, AV, settings, where −3dB
Bandwidth is BW:
(1)
20051520
FIGURE 6. Composite Amplifier Configuration
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12
20051522
FIGURE 8. DC Coupled ADC Driver
13
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LMV2011
E) Rail-to-Rail output swing maximizes the ADC dynamic
range in 5-Volt single-supply converter applications. Below are some typical block diagrams showing the
LMV2011 used as an ADC amplifier (Figure 7 and Figure
8).
data conversion application accuracy (see discussion under "The Benefits of the LMV2011" section above).
LMV2011
Physical Dimensions inches (millimeters) unless otherwise noted
5-Pin SOT23
NS Package Number MF0A5
8-Pin SOIC
NS Package Number M08A
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14
LMV2011
Notes
15
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LMV2011 High Precision, Rail-to-Rail Output Operational Amplifier
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