LM2694 30V, 600 mA Step Down Switching Regulator General Description The LM2694 Step Down Switching Regulator features all of the functions needed to implement a low cost, efficient, buck bias regulator capable of supplying 0.6A to the load. This buck regulator contains an N-Channel Buck Switch, and is available in the 3 x 3 thermally enhanced LLP-10 package and a TSSOP-14 package. The feedback regulation scheme requires no loop compensation, results in fast load transient response, and simplifies circuit implementation. The operating frequency remains constant with line and load variations due to the inverse relationship between the input voltage and the on-time. The valley current limit results in a smooth transition from constant voltage to constant current mode when current limit is detected, reducing the frequency and output voltage, without the use of foldback. Additional features include: VCC under-voltage lockout, thermal shutdown, gate drive under-voltage lockout, and maximum duty cycle limiter. n No loop compensation required n Ultra-Fast transient response n Operating frequency remains constant with load current and input voltage variations n Maximum Duty Cycle Limited During Start-Up n Adjustable output voltage n Valley Current Limit At 0.6A n Maximum switching frequency: 1 MHz n Precision internal reference n Low bias current n Highly efficient operation n Thermal shutdown Typical Applications n High Efficiency Point-Of-Load (POL) Regulator n Non-Isolated Telecommunication Buck Regulator n Secondary High Voltage Post Regulator Features Package n Integrated N-Channel buck switch n Integrated start-up regulator n Input Voltage Range: 8V to 30V n LLP-10 (3 mm x 3 mm) w/Exposed Pad n TSSOP-14 Basic Step Down Regulator 20187001 © 2006 National Semiconductor Corporation DS201870 www.national.com LM2694 30V, 600 mA Step Down Switching Regulator May 2006 LM2694 Connection Diagrams 20187002 10-Lead LLP 20187003 14-Lead TSSOP Ordering Information Order Number Package Type NSC Package Drawing Supplied As LM2694SD LLP-10 (3x3) SDA10A 1000 Units on Tape and Reel LM2694SDX LLP-10 (3x3) SDA10A 4500 Units on Tape and Reel LM2694MT TSSOP-14 MTC14 94 Units in Rail LM2694MTX TSSOP-14 MTC14 2500 Units on Tape and Reel www.national.com 2 LM2694 Pin Descriptions PIN NUMBER LLP-10 TSSOP-14 NAME 1 2 SW Switching Node Internally connected to the buck switch source. Connect to the inductor, free-wheeling diode, and bootstrap capacitor. 2 3 BST Boost pin for bootstrap capacitor Connect a 0.022 µF capacitor from SW to the BST pin. The capacitor is charged from VCC via an internal diode during the buck switch off-time. 3 4 ISEN Current sense During the buck switch off-time, the inductor current flows through the internal sense resistor, and out of the ISEN pin to the free-wheeling diode. The current limit is nominally set at 0.62A. 4 5 SGND Current Sense Ground Re-circulating current flows into this pin to the current sense resistor. 5 6 RTN Circuit Ground Ground return for all internal circuitry other than the current sense resistor. 6 9 FB Voltage feedback input from the regulated output Input to both the regulation and over-voltage comparators. The FB pin regulation level is 2.5V. 7 10 SS Softstart An internal current source charges the SS pin capacitor to 2.5V to soft-start the reference input of the regulation comparator. 8 11 RON/SD On-time control and shutdown An external resistor from VIN to the RON/SD pin sets the buck switch on-time. Grounding this pin shuts down the regulator. 9 12 VCC Output of the startup regulator The voltage at VCC is nominally regulated at 7V. Connect a 0.1 µF, or larger capacitor from VCC to ground, as close as possible to the pins. An external voltage can be applied to this pin to reduce internal dissipation. MOSFET body diodes clamp VCC to VIN if VCC > VIN. 10 13 VIN Input supply voltage Nominal input range is 8V to 30V. Input bypass capacitors should be located as close as possible to the VIN pin and RTN pins. 1,7,8,14 NC No connection. No internal connection. Can be connected to ground plane to improve heat dissipation. EP Exposed Pad Exposed metal pad on the underside of the LLP package. It is recommended to connect this pad to the PC board ground plane to aid in heat dissipation. EP DESCRIPTION 3 APPLICATION INFORMATION www.national.com LM2694 Absolute Maximum Ratings (Note 1) VCC to RTN 14V If Military/Aerospace specified devices are required, please contact the National Semiconductor Sales Office/ Distributors for availability and specifications. SGND to RTN -0.3V to +0.3V VIN to RTN BST to RTN SW to RTN (Steady State) -1.5V SS to RTN -0.3V to 4V All Other Inputs to RTN -0.3 to 7V 33V Storage Temperature Range -65˚C to +150˚C 47V JunctionTemperature 150˚C ESD Rating (Note 2) Human Body Model Operating Ratings (Note 1) 2kV BST to VCC 33V VIN 8.0V to 30V VIN to SW 33V Junction Temperature BST to SW 14V −40˚C to + 125˚C Electrical Characteristics Specifications with standard type are for TJ = 25˚C only; limits in boldface type apply over the full Operating Junction Temperature (TJ) range. Minimum and Maximum limits are guaranteed through test, design, or statistical correlation. Typical values represent the most likely parametric norm at TJ = 25˚C, and are provided for reference purposes only. Unless otherwise stated the following conditions apply: VIN = 24V, RON = 200kΩ. See (Note 5). Symbol Parameter Conditions Min Typ Max 7 7.4 Units Start-Up Regulator, VCC VCCReg UVLOVCC VCC regulated output 6.6 V VIN-VCC dropout voltage ICC = 0 mA, VCC = UVLOVCC + 250 mV 1.3 V 175 Ω 9 mA VCC output impedance 0 mA ≤ ICC ≤ 5 mA, VIN = 8V VCC current limit (Note 3) VCC = 0V VCC under-voltage lockout threshold VCC increasing 5.7 V UVLOVCC hysteresis VCC decreasing 150 mV UVLOVCC filter delay 100 mV overdrive IIN operating current Non-switching, FB = 3V 0.5 0.8 mA IIN shutdown current RON/SD = 0V 90 180 µA 0.5 1.0 Ω 4.4 5.5 3 µs Switch Characteristics Rds(on) Buck Switch Rds(on) ITEST = 200 mA UVLOGD Gate Drive UVLO VBST - VSW Increasing 3.0 V UVLOGD hysteresis 490 Pull-up voltage 2.5 V Internal current source 12 µA mV Softstart Pin Current Limit ILIM Threshold Current out of ISEN 0.5 0.62 0.74 A Resistance from ISEN to SGND 180 mΩ Response time 150 ns On Timer tON - 1 On-time VIN = 10V, RON = 200 kΩ tON - 2 On-time VIN = 30V, RON = 200 kΩ Shutdown threshold Voltage at RON/SD rising Threshold hysteresis Voltage at RON/SD falling 2.1 2.8 3.6 900 0.45 0.8 µs ns 1.2 V 35 mV 265 ns Off Timer tOFF Minimum Off-time Regulation and Over-Voltage Comparators (FB Pin) VREF FB regulation threshold SS pin = steady state FB over-voltage threshold www.national.com 2.440 2.5 2.9 4 2.550 V V Symbol Parameter Conditions Min FB bias current Typ Max Units 1 nA Thermal shutdown temperature 175 ˚C Thermal shutdown hysteresis 20 ˚C ˚C/W Thermal Shutdown TSD Thermal Resistance θJA θJC Junction to Ambient 0 LFPM Air Flow LLP Package 33 TSSOP Package 40 Junction to Case LLP Package 8.8 TSSOP Package 5.2 ˚C/W Note 1: Absolute Maximum Ratings are limits beyond which damage to the device may occur. Operating Ratings are conditions under which operation of the device is intended to be functional. For guaranteed specifications and test conditions, see the Electrical Characteristics. Note 2: The human body model is a 100pF capacitor discharged through a 1.5kΩ resistor into each pin. Note 3: VCC provides self bias for the internal gate drive and control circuits. Device thermal limitations limit external loading Note 4: For detailed information on soldering plastic TSSOP and LLP packages, refer to the Packaging Data Book available from National Semiconductor Corporation. Note 5: Typical specifications represent the most likely parametric norm at 25˚C operation. 5 www.national.com LM2694 Electrical Characteristics Specifications with standard type are for TJ = 25˚C only; limits in boldface type apply over the full Operating Junction Temperature (TJ) range. Minimum and Maximum limits are guaranteed through test, design, or statistical correlation. Typical values represent the most likely parametric norm at TJ = 25˚C, and are provided for reference purposes only. Unless otherwise stated the following conditions apply: VIN = 24V, RON = 200kΩ. See (Note 5). (Continued) LM2694 Typical Performance Characteristics 20187004 FIGURE 1. VCC vs VIN 20187005 FIGURE 2. VCC vs ICC 20187006 FIGURE 3. ICC vs Externally Applied VCC www.national.com 6 LM2694 Typical Performance Characteristics (Continued) 20187007 FIGURE 4. ON-Time vs VIN and RON 20187008 FIGURE 5. Voltage at RON/SD Pin 20187009 FIGURE 6. IIN vs VIN 7 www.national.com LM2694 Typical Application Circuit and Block Diagram 20187010 FIGURE 7. www.national.com 8 LM2694 Typical Application Circuit and Block Diagram (Continued) 20187011 FIGURE 8. Startup Sequence 9 www.national.com LM2694 reference - until then the inductor current remains zero, and the load current is supplied by the output capacitor (C2). In this mode the operating frequency is lower than in continuous conduction mode, and varies with load current. Conversion efficiency is maintained at light loads since the switching losses reduce with the reduction in load and frequency. The approximate discontinuous operating frequency can be calculated as follows: Functional Description The LM2694 Step Down Switching Regulator features all the functions needed to implement a low cost, efficient buck bias power converter capable of supplying at least 0.6A to the load. This high voltage regulator contains a 30V N-Channel buck switch, is easy to implement, and is available in the TSSOP-14 and the thermally enhanced LLP-10 packages. The regulator’s operation is based on a constant on-time control scheme, where the on-time is determined by VIN. This feature allows the operating frequency to remain relatively constant with load and input voltage variations. The feedback control requires no loop compensation resulting in very fast load transient response. The valley current limit detection circuit, internally set at 0.62A, holds the buck switch off until the high current level subsides. This scheme protects against excessively high currents if the output is short-circuited when VIN is high. The functional block diagram is shown in Figure 7. (3) where RL = the load resistance. The output voltage is set by two external resistors (R1, R2). The regulated output voltage is calculated as follows: VOUT = 2.5 x (R1 + R2) / R2 Output voltage regulation is based on ripple voltage at the feedback input, requiring a minimum amount of ESR for the output capacitor C2. The LM2694 requires a minimum of 25 mV of ripple voltage at the FB pin. In cases where the capacitor’s ESR is insufficient additional series resistance may be required (R3 in Figure 7). The LM2694 can be applied in numerous applications to efficiently regulate down higher voltages. Additional features include: Thermal shutdown, VCC under-voltage lockout, gate drive under-voltage lockout, and maximum duty cycle limiter. Control Circuit Overview Start-Up Regulator, VCC The LM2694 buck DC-DC regulator employs a control scheme based on a comparator and a one-shot on-timer, with the output voltage feedback (FB) compared to an internal reference (2.5V). If the FB voltage is below the reference the buck switch is turned on for a time period determined by the input voltage and a programming resistor (RON). Following the on-time the switch remains off for a minimum of 265 ns, and until the FB voltage falls below the reference. The buck switch then turns on for another on-time period. Typically, during start-up, or when the load current increases suddenly, the off-times are at the minimum of 265 ns. Once regulation is established, the off-times are longer. When in regulation, the LM2694 operates in continuous conduction mode at heavy load currents and discontinuous conduction mode at light load currents. In continuous conduction mode current always flows through the inductor, never reaching zero during the off-time. In this mode the operating frequency remains relatively constant with load and line variations. The minimum load current for continuous conduction mode is one-half the inductor’s ripple current amplitude. The operating frequency is approximately: The start-up regulator is integral to the LM2694. The input pin (VIN) can be connected directly to line voltage up to 30V, with transient capability to 33V. The VCC output regulates at 7.0V, and is current limited at 9 mA. Upon power up, the regulator sources current into the external capacitor at VCC (C3). When the voltage on the VCC pin reaches the undervoltage lockout threshold of 5.7V, the buck switch is enabled and the Softstart pin is released to allow the Softstart capacitor (C6) to charge up. The minimum input voltage is determined by the regulator’s dropout voltage, the VCC UVLO falling threshold ()5.5V), and the frequency. When VCC falls below the falling threshold the VCC UVLO activates to shut off the output. If VCC is externally loaded, the minimum input voltage increases. To reduce power dissipation in the start-up regulator, an auxiliary voltage can be diode connected to the VCC pin. Setting the auxiliary voltage to between 8V and 14V shuts off the internal regulator, reducing internal power dissipation. The sum of the auxiliary voltage and the input voltage (VCC + VIN) cannot exceed 47V. Internally, a diode connects VCC to VIN. See Figure 9. (1) The buck switch duty cycle is equal to: (2) In discontinuous conduction mode current through the inductor ramps up from zero to a peak during the on-time, then ramps back to zero before the end of the off-time. The next on-time period starts when the voltage at FB falls below the www.national.com 10 LM2694 Start-Up Regulator, VCC (Continued) 20187014 FIGURE 9. Self Biased Configuration In high frequency applications the minimum value for tON is limited by the maximum duty cycle required for regulation and the minimum off-time of 265 ns, ± 15%. The minimum off-time limits the maximum duty cycle achievable with a low voltage at VIN. The minimum allowed on-time to regulate the desired VOUT at the minimum VIN is determined from the following: Regulation Comparator The feedback voltage at FB is compared to the voltage at the Softstart pin (2.5V). In normal operation (the output voltage is regulated), an on-time period is initiated when the voltage at FB falls below 2.5V. The buck switch stays on for the programmed on-time, causing the FB voltage to rise above 2.5V. After the on-time period, the buck switch stays off until the FB voltage falls below 2.5V. Input bias current at the FB pin is less than 100 nA over temperature. (6) The LM2694 can be remotely shut down by taking the RON/SD pin below 0.8V. See Figure 10. In this mode the SS pin is internally grounded, the on-timer is disabled, and bias currents are reduced. Releasing the RON/SD pin allows normal operation to resume. The voltage at the RON/SD pin is normally between 1.5V and 3.0V, depending on VIN and the RON resistor. Over-Voltage Comparator The voltage at FB is compared to an internal 2.9V reference. If the voltage at FB rises above 2.9V the on-time pulse is immediately terminated. This condition can occur if the input voltage or the output load changes suddenly, or if the inductor (L1) saturates. The buck switch remains off until the voltage at FB falls below 2.5V. ON-Time Timer, and Shutdown The on-time for the LM2694 is determined by the RON resistor and the input voltage (VIN), and is calculated from: (4) See Figure 4. The inverse relationship with VIN results in a nearly constant frequency as VIN is varied. To set a specific continuous conduction mode switching frequency (FS), the RON resistor is determined from the following: 20187019 FIGURE 10. Shutdown Implementation (5) 11 www.national.com LM2694 Figure 11 illustrates the inductor current waveform. During normal operation the load current is Io, the average of the ripple waveform. When the load resistance decreases the current ratchets up until the lower peak reaches 0.62A. During the Current Limited portion of Figure 11, the current ramps down to 0.62A during each off-time, initiating the next on-time (assuming the voltage at FB is < 2.5V). During each on-time the current ramps up an amount equal to: ∆I = (VIN - VOUT) x tON / L1 Current Limit Current limit detection occurs during the off-time by monitoring the recirculating current through the free-wheeling diode (D1). Referring to Figure 7, when the buck switch is turned off the inductor current flows through the load, into SGND, through the sense resistor, out of ISEN and through D1. If that current exceeds 0.62A the current limit comparator output switches to delay the start of the next on-time period if the voltage at FB is below 2.5V. The next on-time starts when the current out of ISEN is below 0.62A and the voltage at FB is below 2.5V. If the overload condition persists causing the inductor current to exceed 0.62A during each ontime, that is detected at the beginning of each off-time. The operating frequency is lower due to longer-than-normal offtimes. During this time the LM2694 is in a constant current mode, with an average load current (IOCL) equal to 0.62A + ∆I/2. 20187020 FIGURE 11. Inductor Current - Current Limit Operation An internal switch grounds the SS pin if VCC is below the under-voltage lockout threshold, if a thermal shutdown occurs, or if the RON/SD pin is grounded. N - Channel Buck Switch and Driver The LM2694 integrates an N-Channel buck switch and associated floating high voltage gate driver. The peak current allowed through the buck switch is 1.5A, and the maximum allowed average current is 1A. The gate driver circuit works in conjunction with an external bootstrap capacitor and an internal high voltage diode. A 0.022 µF capacitor (C4) connected between BST and SW provides the voltage to the driver during the on-time. During each off-time, the SW pin is at approximately -1V, and C4 charges from VCC through the internal diode. The minimum off-time of 265 ns ensures a minimum time each cycle to recharge the bootstrap capacitor. Thermal Shutdown The LM2694 should be operated so the junction temperature does not exceed 125˚C. If the junction temperature increases, an internal Thermal Shutdown circuit, which activates (typically) at 175˚C, takes the controller to a low power reset state by disabling the buck switch and the on-timer, and grounding the Softstart pin. This feature helps prevent catastrophic failures from accidental device overheating. When the junction temperature reduces below 155˚C (typical hysteresis = 20˚C), the Softstart pin is released and normal operation resumes. Softstart Applications Information The softstart feature allows the converter to gradually reach a steady state operating point, thereby reducing start-up stresses and current surges. Upon turn-on, after VCC reaches the under-voltage threshold, an internal 12 µA current source charges up the external capacitor at the SS pin to 2.5V. The ramping voltage at SS (and the non-inverting input of the regulation comparator) ramps up the output voltage in a controlled manner. EXTERNAL COMPONENTS The procedure for calculating the external components is illustrated with a design example. Referring to the Block Diagram, the circuit is to be configured for the following specifications: • VOUT = 5V • www.national.com 12 VIN = 8V to 30V a higher efficiency, but with larger components. Generally, if PC board space is tight, a higher frequency is better. The resulting on-time and frequency have a ± 25% tolerance. Using equation 5 at a VIN of 8V, (Continued) • FS = 250 kHz • Minimum load current = 100 mA • Maximum load current = 600 mA • Softstart time = 5 ms. R1 and R2: These resistors set the output voltage, and their ratio is calculated from: (7) R1/R2 = (VOUT/2.5V) - 1 R1/R2 calculates to 1.0. The resistors should be chosen from standard value resistors in the range of 1.0 kΩ - 10 kΩ. A value of 2.5 kΩ will be used for R1 and for R2. RON, FS: RON can be chosen using Equation 5 to set the nominal frequency, or from Equation 4 if the on-time at a particular VIN is important. A higher frequency generally means a smaller inductor and capacitors (value, size and cost), but higher switching losses. A lower frequency means A value of 140 kΩ will be used for RON, yielding a nominal frequency of 252 kHz. L1: The guideline for choosing the inductor value in this example is that it must keep the circuit’s operation in continuous conduction mode at minimum load current. This is not a strict requirement since the LM2694 regulates correctly when in discontinuous conduction mode, although at a lower frequency. However, to provide an initial value for L1 the above guideline will be used. 20187037 FIGURE 12. Inductor Current To keep the circuit in continuous conduction mode, the maximum allowed ripple current is twice the minimum load current, or 200 mAp-p. Using this value of ripple current, the inductor (L1) is calculated using the following: IPK = ILIM + IOR(max) = 0.74A + 0.18A = 0.92A where ILIM is the maximum guaranteed current limit threshold. At the nominal maximum load current of 0.6A, the peak inductor current is 692 mA. C1: This capacitor limits the ripple voltage at VIN resulting from the source impedance of the supply feeding this circuit, and the on/off nature of the switch current into VIN. At maximum load current, when the buck switch turns on, the current into VIN steps up from zero to the lower peak of the inductor current waveform (IPK- in Figure 12), ramps up to the peak value (IPK+), then drops to zero at turn-off. The average current into VIN during this on-time is the load current. For a worst case calculation, C1 must supply this average current during the maximum on-time. The maximum on-time is calculated at VIN = 8V using Equation 4, with a 25% tolerance added: (8) where FS(min) is the minimum frequency of 189 kHz (252 kHz - 25%). This provides a minimum value for L1 - the next higher standard value (150 µH) will be used. To prevent saturation, and possible destructive current levels, L1 must be rated for the peak current which occurs if the current limit and maximum ripple current are reached simultaneously. The maximum ripple amplitude is calculated by re-arranging Equation 8 using VIN(max), FS(min), and the minimum inductor value, based on the manufacturer’s tolerance. Assume, for this exercise, the inductor’s tolerance is ± 20%. The voltage at VIN should not be allowed to drop below 7.5V in order to maintain VCC above its UVLO. (9) 13 www.national.com LM2694 Applications Information LM2694 Applications Information should be a good quality, low ESR, ceramic capacitor, physically close to the IC pins. (Continued) Normally a lower value can be used for C1 since the above calculation is a worst case calculation which assumes the power source has a high source impedance. A quality ceramic capacitor with a low ESR should be used for C1. C2 and R3: Since the LM2694 requires a minimum of 25 mVp-p of ripple at the FB pin for proper operation, the required ripple at VOUT is increased by R1 and R2, and is equal to: VRIPPLE = 25 mVp-p x (R1 + R2)/R2 = 50 mVp-p C4: The recommended value for C4 is 0.022 µF. A high quality ceramic capacitor with low ESR is recommended as C4 supplies the surge current to charge the buck switch gate at each turn-on. A low ESR also ensures a complete recharge during each off-time. This necessary ripple voltage is created by the inductor ripple current acting on C2’s ESR + R3. First, the minimum ripple current, which occurs at minimum VIN, maximum inductor value, and maximum frequency, is determined. C6: The capacitor at the SS pin determines the soft-start time, i.e. the time for the reference voltage at the regulation comparator, and the output voltage, to reach their final value. The capacitor value is determined from the following: C5: This capacitor suppresses transients and ringing due to lead inductance at VIN. A low ESR, 0.1 µF ceramic chip capacitor is recommended, located physically close to the LM2694. For a 5 ms softstart time, C6 calculates to 0.024 µF. D1: A Schottky diode is recommended. Ultra-fast recovery diodes are not recommended as the high speed transitions at the SW pin may inadvertently affect the IC’s operation through external or internal EMI. The diode should be rated for the maximum VIN (30V), the maximum load current (0.6A), and the peak current which occurs when current limit and maximum ripple current are reached simultaneously (IPK in Figure 11), previously calculated to be 0.92A. The diode’s forward voltage drop affects efficiency due to the power dissipated during the off-time. The average power dissipation in D1 is calculated from: PD1 = VF x IO x (1 - D) where IO is the load current, and D is the duty cycle. (10) The minimum ESR for C2 is then equal to: If the capacitor used for C2 does not have sufficient ESR, R3 is added in series as shown in Figure 7. The value chosen for C2 is application dependent, and it is recommended that it be no smaller than 3.3 µF. C2 affects the ripple at VOUT, and transient response. Experimentation is usually necessary to determine the optimum value for C2. C3: The capacitor at the VCC pin provides noise filtering and stability, prevents false triggering of the VCC UVLO at the buck switch on/off transitions, and limits the peak voltage at VCC when a high voltage with a short rise time is initially applied at VIN. C3 should be no smaller than 0.1 µF, and www.national.com FINAL CIRCUIT The final circuit is shown in Figure 13, and its performance is shown in Figure 14 and Figure 15. Current limit measured approximately 0.64A. 14 LM2694 Applications Information (Continued) 20187031 FIGURE 13. Example Circuit 15 www.national.com LM2694 Applications Information (Continued) Item Description Value C1 Ceramic Capacitor 3.3 µF, 50V C2 Ceramic Capacitor 22 µF, 16V C4, C6 Ceramic Capacitor 0.022 µF, 16V C3, C5 Ceramic Capacitor 0.1 µF, 50V D1 Schottky Diode 60V, 1A L1 Inductor 150 µH R1 Resistor 2.5 kΩ R2 Resistor 2.5 kΩ R3 Resistor 1.5 Ω RON Resistor 140 kΩ U1 National Semi LM2694 MINIMUM LOAD CURRENT The LM2694 requires a minimum load current of 500 µA. If the load current falls below that level, the bootstrap capacitor (C4) may discharge during the long off-time, and the circuit will either shutdown, or cycle on and off at a low frequency. If the load current is expected to drop below 500 µA in the application, R1 and R2 should be chosen low enough in value so they provide the minimum required current at nominal VOUT. LOW OUTPUT RIPPLE CONFIGURATIONS For applications where low output voltage ripple is required the output can be taken directly from the low ESR output capacitor (C2) as shown in Figure 16. However, R3 slightly degrades the load regulation. The specific component values, and the application determine if this is suitable. 20187032 FIGURE 14. Efficiency vs Load Current and VIN Circuit of Figure 13 20187034 FIGURE 16. Low Ripple Output Where the circuit of Figure 16 is not suitable for reducing output ripple, the circuits of Figure 17 or Figure 18 can be used. 20187033 FIGURE 15. Frequency vs VIN Circuit of Figure 13 20187035 FIGURE 17. Low Output Ripple Using a Feedforward Capacitor www.national.com 16 close as possible to their associated pins. The two major current loops have currents which switch very fast, and so the loops should be as small as possible to minimize conducted and radiated EMI. The first loop is that formed by C1, through the VIN to SW pins, L1, C2, and back to C1. The second loop is that formed by D1, L1, C2, and the SGND and ISEN pins. The ground connection from C2 to C1 should be as short and direct as possible, preferably without going through vias. Directly connect the SGND and RTN pin to each other, and they should be connected as directly as possible to the C1/C2 ground line without going through vias. The power dissipation within the IC can be approximated by determining the total conversion loss (PIN - POUT), and then subtracting the power losses in the free-wheeling diode and the inductor. The power loss in the diode is approximately: PD1 = IO x VF x (1-D) where Io is the load current, VF is the diode’s forward voltage drop, and D is the duty cycle. The power loss in the inductor is approximately: PL1 = IO2 x RL x 1.1 where RL is the inductor’s DC resistance, and the 1.1 factor is an approximation for the AC losses. If it is expected that the internal dissipation of the LM2694 will produce high junction temperatures during normal operation, good use of the PC board’s ground plane can help considerably to dissipate heat. The exposed pad on the LLP package bottom should be soldered to a ground plane, and that plane should both extend from beneath the IC, and be connected to exposed ground plane on the board’s other side using as many vias as possible. The exposed pad is internally connected to the IC substrate. The use of wide PC board traces at the pins, where possible, can help conduct heat away from the IC. The four No Connect pins on the TSSOP package are not electrically connected to any part of the IC, and may be connected to ground plane to help dissipate heat from the package. Judicious positioning of the PC board within the end product, along with the use of any available air flow (forced or natural convection) can help reduce the junction temperature. (Continued) In Figure 17, Cff is added across R1 to AC-couple the ripple at VOUT directly to the FB pin. This allows the ripple at VOUT to be reduced, in some cases considerably, by reducing R3. In the circuit of Figure 13, the ripple at VOUT ranged from 50 mVp-p at VIN = 8V to 100 mVp-p at VIN = 30V. By adding a 2700 pF capacitor at Cff and reducing R3 to 0.75Ω, the VOUT ripple is reduced by 50%. 20187036 FIGURE 18. Minimum Output Ripple Using Ripple Injection To reduce VOUT ripple further, the circuit of Figure 18 can be used. R3 has been removed, and the output ripple amplitude is determined by C2’s ESR and the inductor ripple current. RA and CA are chosen to generate a 40-50 mVp-p sawtooth at their junction, and that voltage is AC-coupled to the FB pin via CB. In selecting RA and CA, VOUT is considered a virtual ground as the SW pin switches between VIN and -1V. Since the on-time at SW varies inversely with VIN, the waveform amplitude at the RA/CA junction is relatively constant. Typical values for the additional components are RA = 110k, CA = 2700 pF, and CB = 0.01 µF. PC BOARD LAYOUT and THERMAL CONSIDERATIONS The LM2694 regulation, over-voltage, and current limit comparators are very fast, and will respond to short duration noise pulses. Layout considerations are therefore critical for optimum performance. The layout must be as neat and compact as possible, and all the components must be as 17 www.national.com LM2694 Applications Information LM2694 Physical Dimensions inches (millimeters) unless otherwise noted 14-Lead TSSOP-14 Package NS Package Number MTC14 www.national.com 18 LM2694 30V, 600 mA Step Down Switching Regulator Physical Dimensions inches (millimeters) unless otherwise noted (Continued) 10-Lead LLP Package NS Package Number SDA10A National does not assume any responsibility for use of any circuitry described, no circuit patent licenses are implied and National reserves the right at any time without notice to change said circuitry and specifications. For the most current product information visit us at www.national.com. LIFE SUPPORT POLICY NATIONAL’S PRODUCTS ARE NOT AUTHORIZED FOR USE AS CRITICAL COMPONENTS IN LIFE SUPPORT DEVICES OR SYSTEMS WITHOUT THE EXPRESS WRITTEN APPROVAL OF THE PRESIDENT AND GENERAL COUNSEL OF NATIONAL SEMICONDUCTOR CORPORATION. As used herein: 1. Life support devices or systems are devices or systems which, (a) are intended for surgical implant into the body, or (b) support or sustain life, and whose failure to perform when properly used in accordance with instructions for use provided in the labeling, can be reasonably expected to result in a significant injury to the user. 2. A critical component is any component of a life support device or system whose failure to perform can be reasonably expected to cause the failure of the life support device or system, or to affect its safety or effectiveness. BANNED SUBSTANCE COMPLIANCE National Semiconductor manufactures products and uses packing materials that meet the provisions of the Customer Products Stewardship Specification (CSP-9-111C2) and the Banned Substances and Materials of Interest Specification (CSP-9-111S2) and contain no ‘‘Banned Substances’’ as defined in CSP-9-111S2. Leadfree products are RoHS compliant. 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